EP2225844A2 - Synchronisation dans un système ofdm de radiodiffusion utilisant des pilotes à multiplexage temporel - Google Patents

Synchronisation dans un système ofdm de radiodiffusion utilisant des pilotes à multiplexage temporel

Info

Publication number
EP2225844A2
EP2225844A2 EP08844052A EP08844052A EP2225844A2 EP 2225844 A2 EP2225844 A2 EP 2225844A2 EP 08844052 A EP08844052 A EP 08844052A EP 08844052 A EP08844052 A EP 08844052A EP 2225844 A2 EP2225844 A2 EP 2225844A2
Authority
EP
European Patent Office
Prior art keywords
pilot
subbands
tdm
ofdm
data
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP08844052A
Other languages
German (de)
English (en)
Inventor
Fuyun Ling
Alok Kumar Gupta
Raghuraman Krishnamoorthi
Murali Ramaswamy Chari
Rajiv Vijayan
Bojan Vrcelj
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Qualcomm Inc
Original Assignee
Qualcomm Inc
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Qualcomm Inc filed Critical Qualcomm Inc
Publication of EP2225844A2 publication Critical patent/EP2225844A2/fr
Withdrawn legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2662—Symbol synchronisation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2602—Signal structure
    • H04L27/261—Details of reference signals
    • H04L27/2613—Structure of the reference signals
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/0001—Arrangements for dividing the transmission path
    • H04L5/0003—Two-dimensional division
    • H04L5/0005—Time-frequency
    • H04L5/0007—Time-frequency the frequencies being orthogonal, e.g. OFDM(A), DMT
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2602—Signal structure
    • H04L27/261—Details of reference signals
    • H04L27/2613—Structure of the reference signals
    • H04L27/26134—Pilot insertion in the transmitter chain, e.g. pilot overlapping with data, insertion in time or frequency domain
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2656—Frame synchronisation, e.g. packet synchronisation, time division duplex [TDD] switching point detection or subframe synchronisation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00—Arrangements affording multiple use of the transmission path
    • H04L5/003—Arrangements for allocating sub-channels of the transmission path
    • H04L5/0048—Allocation of pilot signals, i.e. of signals known to the receiver

Definitions

  • the present disclosure relates generally to data communication, and more specifically to synchronization in a wireless broadcast system using orthogonal frequency division multiplexing (OFDM).
  • OFDM orthogonal frequency division multiplexing
  • OFDM is a multi-carrier modulation technique that effectively partitions the overall system bandwidth into multiple (N) orthogonal frequency subbands. These subbands are also referred to as tones, sub-carriers, bins, and frequency channels. With OFDM, each subband is associated with a respective sub-carrier that may be modulated with data.
  • a transmitter processes data to obtain modulation symbols, and further performs OFDM modulation on the modulation symbols to generate OFDM symbols, as described below.
  • the transmitter then conditions and transmits the OFDM symbols via a communication channel.
  • the OFDM system may use a transmission structure whereby data is transmitted in frames, with each frame having a particular time duration. Different types of data (e.g., traffic/packet data, overhead/control data, pilot, and so on) may be sent in different parts of each frame. Pilot generically refers to data and/or transmission that are known a priori by both the transmitter and a receiver.
  • the receiver typically needs to obtain accurate frame and symbol timing in order to properly recover the data sent by the transmitter. For example, the receiver may need to know the start of each frame in order to properly recover the different types of data sent in the frame. The receiver often does not know the time at which each OFDM symbol is sent by the transmitter nor the propagation delay introduced by the communication channel. The receiver would then need to ascertain the timing of each OFDM symbol received via the communication channel in order to properly perform the complementary OFDM demodulation on the received OFDM symbol.
  • Synchronization refers to a process performed by the receiver to obtain frame and symbol timing. The receiver may also perform other tasks, such as frequency error estimation, as part of synchronization.
  • the transmitter typically expends system resources to support synchronization, and the receiver also consumes resources to perform synchronization. Since synchronization is overhead needed for data transmission, it is desirable to minimize the amount of resources used by both the transmitter and receiver for synchronization.
  • TDM time division multiplexed
  • This pilot structure results in (1) an OFDM symbol for the first TDM pilot containing at least Si identical "pilot- 1" sequences, with each pilot- 1 sequence containing Li time-domain samples, and (2) an OFDM symbol for the second TDM pilot containing at least S 2 identical "pilot-2" sequences, with each pilot-2 sequence containing L 2 time-domain samples.
  • the transmitter may also transmit a frequency division multiplexed (FDM) pilot along with data in the remaining part of each frame.
  • FDM frequency division multiplexed
  • a receiver can perform synchronization based on the first and second TDM pilots.
  • the receiver can process the first TDM pilot to obtain frame timing and frequency error estimate.
  • the receiver may compute a detection metric based on a delayed correlation between different pilot- 1 sequences for the first TDM pilot, compare the detection metric against a threshold, and declare detection of the first TDM pilot (and thus a frame) based on the comparison result.
  • the receiver can also obtain an estimate of the frequency error in the received OFDM symbol based on the pilot- 1 sequences.
  • the receiver can process the second TDM pilot to obtain symbol timing and a channel estimate.
  • the receiver may derive a channel impulse response estimate based on a received OFDM symbol for the second TDM pilot, detect the start of the channel impulse response estimate (e.g., based on the energy of the channel taps for the channel impulse response), and derive the symbol timing based on the detected start of the channel impulse response estimate.
  • the receiver may also derive a channel frequency response estimate for the N total subbands based on the channel impulse response estimate.
  • the receiver may use the first and second TDM pilots for initial synchronization and may use the FDM pilot for frequency and time tracking and for more accurate channel estimation.
  • aspects of the present disclosure are capable of operation using FFT sizes of, for example, IK, 2K and 8K to complement the existing 4K FFT size.
  • FFT sizes for example, IK, 2K and 8K to complement the existing 4K FFT size.
  • 4K or 8K could be used for deployments in VHF band; 4K or 2K could be used for deployments in L-band; 2K or IK could be used for deployments in S-band.
  • the aforementioned FFT sizes are merely illustrative examples of various OFDM systems, and the present disclosure is not limited to only IK, 2K, 4K and 8K FFT sizes.
  • FIG. 1 shows a base station and a wireless device in an OFDM system
  • FIG. 2 shows a super-frame structure for the OFDM system
  • FIGS. 3A and 3B show frequency-domain representations of TDM pilots 1 and 2, respectively;
  • FIG. 4 shows a transmit (TX) data and pilot processor
  • FIG. 5 shows an OFDM modulator
  • FIGS. 6A and 6B show time-domain representations of TDM pilots 1 and 2;
  • FIG. 7 shows a synchronization and channel estimation unit
  • FIG. 8 shows a frame detector
  • FIG. 9 shows a symbol timing detector
  • FIGS. 1OA through 1OC show processing for a pilot-2 OFDM symbol
  • FIG. 11 shows a pilot transmission scheme with TDM and FDM pilots
  • FIG. 12 shows an exemplary correspondence between OFDM subbands for different FFT sizes.
  • FIG. 13 shows a time-domain representations of TDM pilot 2 for various
  • the word "exemplary” is used herein to mean “serving as an example, instance, or illustration.” Any aspect or design described herein as “exemplary” is not necessarily to be construed as preferred or advantageous over other aspects or designs.
  • the synchronization techniques described herein may be used for various multi-carrier systems and for the downlink as well as the uplink.
  • the downlink (or forward link) refers to the communication link from the base stations to the wireless devices
  • the uplink (or reverse link) refers to the communication link from the wireless devices to the base stations. For clarity, these techniques are described below for the downlink in an OFDM system.
  • FIG. 1 shows a block diagram of a base station 110 and a wireless device 150 in an OFDM system 100.
  • Base station 110 is generally a fixed station and may also be referred to as a base transceiver system (BTS), an access point, or some other terminology.
  • Wireless device 150 may be fixed or mobile and may also be referred to as a user terminal, a mobile station, or some other terminology.
  • Wireless device 150 may also be a portable unit such as a cellular phone, a handheld device, a wireless module, a personal digital assistant (PDA), and so on.
  • PDA personal digital assistant
  • a TX data and pilot processor 120 receives different types of data (e.g., traffic/packet data and overhead/control data) and processes (e.g., encodes, interleaves, and symbol maps) the received data to generate data symbols.
  • data symbol is a modulation symbol for data
  • pilot symbol is a modulation symbol for pilot
  • a modulation symbol is a complex value for a point in a signal constellation for a modulation scheme (e.g., M-PSK, M-QAM, and so on).
  • Processor 120 also processes pilot data to generate pilot symbols and provides the data and pilot symbols to an OFDM modulator 130.
  • OFDM modulator 130 multiplexes the data and pilot symbols onto the proper subbands and symbol periods and further performs OFDM modulation on the multiplexed symbols to generate OFDM symbols, as described below.
  • a transmitter unit (TMTR) 132 converts the OFDM symbols into one or more analog signals and further conditions (e.g., amplifies, filters, and frequency upconverts) the analog signal(s) to generate a modulated signal.
  • Base station 110 then transmits the modulated signal from an antenna 134 to wireless devices in the system.
  • the transmitted signal from base station 110 is received by an antenna 152 and provided to a receiver unit (RCVR) 154.
  • Receiver unit 154 conditions (e.g., filters, amplifies, and frequency downconverts) the received signal and digitizes the conditioned signal to obtain a stream of input samples.
  • An OFDM demodulator 160 performs OFDM demodulation on the input samples to obtain received data and pilot symbols.
  • OFDM demodulator 160 also performs detection (e.g., matched filtering) on the received data symbols with a channel estimate (e.g., a frequency response estimate) to obtain detected data symbols, which are estimates of the data symbols sent by base station 110.
  • OFDM demodulator 160 provides the detected data symbols to a receive (RX) data processor 170.
  • RX receive
  • a synchronization/channel estimation unit 180 receives the input samples from receiver unit 154 and performs synchronization to determine frame and symbol timing, as described below. Unit 180 also derives the channel estimate using received pilot symbols from OFDM demodulator 160. Unit 180 provides the symbol timing and channel estimate to OFDM demodulator 160 and may provide the frame timing to RX data processor 170 and/or a controller 190. OFDM demodulator 160 uses the symbol timing to perform OFDM demodulation and uses the channel estimate to perform detection on the received data symbols.
  • RX data processor 170 processes (e.g., symbol demaps, deinterleaves, and decodes) the detected data symbols from OFDM demodulator 160 and provides decoded data.
  • RX data processor 170 and/or controller 190 may use the frame timing to recover different types of data sent by base station 110.
  • the processing by OFDM demodulator 160 and RX data processor 170 is complementary to the processing by OFDM modulator 130 and TX data and pilot processor 120, respectively, at base station 110.
  • Controllers 140 and 190 direct operation at base station 110 and wireless device 150, respectively.
  • Memory units 142 and 192 provide storage for program codes and data used by controllers 140 and 190, respectively.
  • Base station 110 may send a point-to-point transmission to a single wireless device, a multi-cast transmission to a group of wireless devices, a broadcast transmission to all wireless devices under its coverage area, or any combination thereof.
  • base station 110 may broadcast pilot and overhead/control data to all wireless devices under its coverage area.
  • Base station 110 may further transmit user- specific data to specific wireless devices, multi-cast data to a group of wireless devices, and/or broadcast data to all wireless devices.
  • FIG. 2 shows a super-frame structure 200 that may be used for OFDM system 100.
  • Data and pilot may be transmitted in super- frames, with each super- frame having a predetermined time duration.
  • a super-frame may also be referred to as a frame, a time slot, or some other terminology.
  • each super-frame includes a field 212 for a first TDM pilot (or "TDM pilot 1"), a field 214 for a second TDM pilot (or "TDM pilot 2”), a field 216 for overhead/control data, and a field 218 for traffic/packet data.
  • the four fields 212 through 218 are time division multiplexed in each super- frame such that only one field is transmitted at any given moment.
  • the four fields are also arranged in the order shown in FIG. 2 to facilitate synchronization and data recovery. Pilot OFDM symbols in fields 212 and 214, which are transmitted first in each super- frame, may be used for detection of overhead OFDM symbols in field 216, which is transmitted next in the super-frame. Overhead information obtained from field 216 may then be used for recovery of traffic/packet data sent in field 218, which is transmitted last in the super-frame.
  • field 212 carries one OFDM symbol for TDM pilot 1, and field 214 also carries one OFDM symbol for TDM pilot 2.
  • each field may be of any duration, and the fields may be arranged in any order.
  • TDM pilots 1 and 2 are broadcast periodically in each frame to facilitate synchronization by the wireless devices.
  • Overhead field 216 and/or data field 218 may also contain pilot symbols that are frequency division multiplexed with data symbols, as described below.
  • the OFDM system has an overall system bandwidth of BW MHz, which is partitioned into N orthogonal subbands using OFDM. The spacing between adjacent subbands is BW /N MHz.
  • N 4096 total subbands
  • M 4000 usable subbands (obviousnly, M scales with FFT size)
  • N - M 96 guard subbands.
  • any OFDM structure with any number of total, usable, and guard subbands may be used for the OFDM system. It is noted that this aspect operates with a 4K FFT size. However, other FFT sizes (e.g., IK, 2K or 8K) can be implemented, as described below.
  • TDM pilots 1 and 2 may be designed to facilitate synchronization by the wireless devices in the system.
  • a wireless device may use TDM pilot 1 to detect the start of each frame, obtain a coarse estimate of symbol timing, and estimate frequency error.
  • the wireless device may use TDM pilot 2 to obtain more accurate symbol timing.
  • FIG. 3A shows an aspect of TDM pilot 1 in the frequency domain.
  • TDM pilot 1 comprises Li pilot symbols that are transmitted on Li subbands, one pilot symbol per subband used for TDM pilot 1.
  • S 1 N / L 1 .
  • N 4096
  • L 1 128
  • S 1 32 .
  • TDM pilot 1 can (1) provide good performance for frame detection in various types of channel including a severe multi-path channel, (2) provide a sufficiently accurate frequency error estimate and coarse symbol timing in a severe multi-path channel, and (3) simplify the processing at the wireless devices, as described below.
  • FIG. 3B shows an aspect of TDM pilot 2 in the frequency domain.
  • TDM pilot 2 comprises L 2 pilot symbols that are transmitted on L 2 subbands, where L 2 > L 1 .
  • S 2 N / L 2 .
  • N 4096
  • L 2 2048
  • S 2 2.
  • other values may also be used for N, L 2 , and S 2 .
  • other FFT sizes e.g., IK, 2K or 8K
  • This structure for TDM pilot 2 can provide accurate symbol timing in various types of channel including a severe multi-path channel.
  • the wireless devices may also be able to (1) process TDM pilot 2 in an efficient manner to obtain symbol timing prior to the arrival of the next OFDM symbol, which is right after TDM pilot 2, and (2) apply the symbol timing to this next OFDM symbol, as described below.
  • a smaller value is used for Li so that a larger frequency error can be corrected with TDM pilot 1.
  • a larger value is used for L 2 so that the pilot-2 sequence is longer, which allows a wireless device to obtain a longer channel impulse response estimate from the pilot-2 sequence.
  • the Li subbands for TDM pilot 1 are selected such Si identical pilot- 1 sequences are generated for TDM pilot 1.
  • the L 2 subbands for TDM pilot 2 are selected such S 2 identical pilot-2 sequences are generated for TDM pilot 2.
  • FIG. 4 shows a block diagram of an aspect of TX data and pilot processor 120 at base station 110.
  • a TX data processor 410 receives, encodes, interleaves, and symbol maps traffic/packet data to generate data symbols.
  • a pseudo-random number (PN) generator 420 is used to generate data for both TDM pilots 1 and 2.
  • LFSR linear feedback shift register
  • PN generator 420 includes (1) 20 delay elements 422a through 422o coupled in series and (2) a summer 424 coupled between delay elements 422n and 422o.
  • Delay element 422o provides pilot data, which is also fed back to the input of delay element 422a and to one input of summer 424.
  • PN generator 420 may be initialized with different initial states for TDM pilots 1 and 2, e.g., to ' 11110000100000000000' for TDM pilot 1 and to ' 11110000100000000011 ' for TDM pilot 2. In general, any data may be used for TDM pilots 1 and 2.
  • the pilot data may be selected to reduce the difference between the peak amplitude and the average amplitude of a pilot OFDM symbol (i.e., to minimize the peak-to-average variation in the time-domain waveform for the TDM pilot).
  • the pilot data for TDM pilot 2 may also be generated with the same PN generator used for scrambling data.
  • the wireless devices have knowledge of the data used for TDM pilot 2 but do not need to know the data used for TDM pilot 1.
  • a bit-to-symbol mapping unit 430 receives the pilot data from PN generator 420 and maps the bits of the pilot data to pilot symbols based on a modulation scheme.
  • the same or different modulation schemes may be used for TDM pilots 1 and 2.
  • QPSK is used for both TDM pilots 1 and 2.
  • mapping unit 430 groups the pilot data into 2-bit binary values and further maps each 2-bit value to a specific pilot modulation symbol.
  • Each pilot symbol is a complex value in a signal constellation for QPSK. If QPSK is used for the TDM pilots, then mapping unit 430 maps 2L 1 pilot data bits for TDM pilot 1 to Li pilot symbols and further maps 2L 2 pilot data bits for TDM pilot 2 to L 2 pilot symbols.
  • a multiplexer (Mux) 440 receives the data symbols from TX data processor 410, the pilot symbols from mapping unit 430, and a TDM Ctrl signal from controller 140. Multiplexer 440 provides to OFDM modulator 130 the pilot symbols for the TDM pilot 1 and 2 fields and the data symbols for the overhead and data fields of each frame, as shown in FIG. 2. [0046]
  • FIG. 5 shows a block diagram of an aspect of OFDM modulator 130 at base station 110.
  • a symbol-to-subband mapping unit 510 receives the data and pilot symbols from TX data and pilot processor 120 and maps these symbols onto the proper subbands based on a Subband Mux Ctrl signal from controller 140.
  • mapping unit 510 In each OFDM symbol period, mapping unit 510 provides one data or pilot symbol on each subband used for data or pilot transmission and a "zero symbol" (which is a signal value of zero) for each unused subband. The pilot symbols designated for subbands that are not used are replaced with zero symbols. For each OFDM symbol period, mapping unit 510 provides N "transmit symbols" for the N total subbands, where each transmit symbol may be a data symbol, a pilot symbol, or a zero symbol.
  • An inverse discrete Fourier transform (IDFT) unit 520 receives the N transmit symbols for each OFDM symbol period, transforms the N transmit symbols to the time domain with an N-point IDFT, and provides a "transformed" symbol that contains N time-domain samples.
  • IDFT inverse discrete Fourier transform
  • Each sample is a complex value to be sent in one sample period.
  • An N-point inverse fast Fourier transform (IFFT) may also be performed in place of an N-point IDFT if N is a power of two, which is typically the case.
  • a parallel-to-serial (P/S) converter 530 serializes the N samples for each transformed symbol.
  • a cyclic prefix generator 540 then repeats a portion (or C samples) of each transformed symbol to form an OFDM symbol that contains N + C samples.
  • the cyclic prefix is used to combat inter-symbol interference (ISI) and intercarrier interference (ICI) caused by a long delay spread in the communication channel. Delay spread is the time difference between the earliest arriving signal instance and the latest arriving signal instance at a receiver.
  • An OFDM symbol period (or simply, a "symbol period”) is the duration of one OFDM symbol and is equal to N + C sample periods.
  • FIG. 6A shows a time-domain representation of TDM pilot 1.
  • An OFDM symbol for TDM pilot 1 (or "pilot- 1 OFDM symbol") is composed of a transformed symbol of length N and a cyclic prefix of length C. Because the Li pilot symbols for TDM pilot 1 are sent on Li subbands that are evenly spaced apart by Si subbands, and because zero symbols are sent on the remaining subbands, the transformed symbol for TDM pilot 1 contains Si identical pilot- 1 sequences, with each pilot- 1 sequence containing Li time-domain samples. Each pilot- 1 sequence may also be generated by performing an Li-point IDFT on the Li pilot symbols for TDM pilot 1.
  • the cyclic prefix for TDM pilot 1 is composed of the C rightmost samples of the transformed symbol and is inserted in front of the transformed symbol.
  • FIG. 6B shows a time-domain representation of TDM pilot 2.
  • An OFDM symbol for TDM pilot 2 (or "pilot-2 OFDM symbol") is also composed of a transformed symbol of length N and a cyclic prefix of length C.
  • the transformed symbol for TDM pilot 2 contains S 2 identical pilot-2 sequences, with each pilot-2 sequence containing L 2 time-domain samples.
  • the cyclic prefix for TDM pilot 2 would contain only a portion of the pilot-2 sequence. It is noted that this aspect operates with a 4K FFT size. However, other FFT sizes (e.g., IK, 2K or 8K) can be implemented, as described below.
  • FIG. 7 shows a block diagram of an aspect of synchronization and channel estimation unit 180 at wireless device 150.
  • a frame detector 710 receives the input samples from receiver unit 154, processes the input samples to detect for the start of each frame, and provides the frame timing.
  • a symbol timing detector 720 receives the input samples and the frame timing, processes the input samples to detect for the start of the received OFDM symbols, and provides the symbol timing.
  • a frequency error estimator 712 estimates the frequency error in the received OFDM symbols.
  • a channel estimator 730 receives an output from symbol timing detector 720 and derives the channel estimate. The detectors and estimators in unit 180 are described below.
  • FIG. 8 shows a block diagram of an aspect of frame detector 710, which performs frame synchronization by detecting for TDM pilot 1 in the input samples from receiver unit 154.
  • the communication channel is an additive white Gaussian noise (AWGN) channel.
  • AWGN additive white Gaussian noise
  • n is an index for sample period
  • X n is a time-domain sample sent by the base station in sample period n; r n is an input sample obtained by the wireless device in sample period n; and W n is the noise for sample period n.
  • frame detector 710 is implemented with a delayed correlator that exploits the periodic nature of the pilot- 1 OFDM symbol for frame detection.
  • frame detector 710 uses the following detection metric for frame detection:
  • S n is the detection metric for sample period n; " * " denotes a complex conjugate; and I x
  • a shift register 812 receives, stores, and shifts the input samples ⁇ r n ⁇ and provides input samples ⁇ r n _ L ⁇ that have been delayed by Li sample periods.
  • a sample buffer may also be used in place of shift register 812.
  • a unit 816 also receives the input samples and provides the complex- conjugated input samples ⁇ r * ⁇ .
  • a multiplier 814 multiplies the delayed input sample r n L from shift register 812 with the complex-conjugated input sample r * from unit 816 and provides a correlation result c n to a shift register 822 (of length Li) and a summer 824.
  • Lower-case C n denotes the correlation result for one input sample
  • upper-case C n denotes the accumulated correlation result for Li input samples.
  • Shift register 822 receives, stores, and delays the correlation results ⁇ c n ⁇ from multiplier 814 and provides correlation results ⁇ c n _ L ⁇ that have been delayed by Li sample periods.
  • summer 824 receives and sums the output C B _ 1 of a register 826 with the result c n from multiplier 814, further subtracts the delayed result c n _ u from shift register 822, and provides its output C n to register 826.
  • Summer 824 and register 826 form an accumulator that performs the summation operation in equation (2).
  • Shift register 822 and summer 824 are also configured to perform a running or sliding summation of the Li most recent correlation results C n through c n _ L +1 . This is achieved by summing the most recent correlation result c n from multiplier 814 and subtracting out the correlation result c n _ L from Li sample periods earlier, which is provided by shift register 822.
  • a unit 832 computes the squared magnitude of the accumulated output C n from summer 824 and provides the detection metric S n .
  • a post-processor 834 detects for the presence of the pilot- 1 OFDM symbol, and hence the start of the super-frame, based on the detection metric S n and a threshold S th , which may be a fixed or programmable value.
  • the frame detection may be based on various criteria. For example, post-processor 834 may declare the presence of a pilot- 1 OFDM symbol if the detection metric S n (1) exceeds the threshold S th , (2) remains above the threshold S th for at least a predetermined percentage of the pilot- 1 OFDM symbol duration, and (3) falls below the threshold S th for a predetermined time period (one pilot- 1 sequence) thereafter.
  • Post-processor 834 may indicate the end of the pilot- 1 OFDM symbol (denoted as Tc) as a predetermined number of sample periods prior to the trailing edge of the waveform for the detection metric S n .
  • the 834 may also set a Frame Timing signal (e.g., to logic high) at the end of the pilot- 1 OFDM symbol.
  • the time Tc may be used as a coarse symbol timing for the processing of the pilot-2 OFDM symbol.
  • Frequency error estimator 712 estimates the frequency error in the received pilot- 1 OFDM symbol. This frequency error may be due to various sources such as, for example, a difference in the frequencies of the oscillators at the base station and wireless device, Doppler shift, and so on. Frequency error estimator 712 may generate a frequency error estimate for each pilot- 1 sequence (except for the last pilot- 1 sequence), as follows:
  • Af j is the frequency error estimate for the £ -th pilot- 1 sequence.
  • the range of detectable frequency errors may be given as:
  • Equation (4) indicates that the range of detected frequency errors is dependent on, and inversely related to, the length of the pilot- 1 sequence.
  • Frequency error estimator 712 may also be implemented within postprocessor 834 since the accumulated correlation results are also available from summer 824.
  • the frequency error estimates may be used in various manners.
  • the frequency error estimate for each pilot- 1 sequence may be used to update a frequency tracking loop that attempts to correct for any detected frequency error at the wireless device.
  • the frequency tracking loop may be a phase-locked loop (PLL) that can adjust the frequency of a carrier signal used for frequency downconversion at the wireless device.
  • PLL phase-locked loop
  • the frequency error estimates may also be averaged to obtain a single frequency error estimate Af for the pilot- 1 OFDM symbol. This Af may then be used for frequency error correction either prior to or after the N-point DFT within OFDM demodulator 160.
  • the input samples may be phase rotated by the frequency error estimate Af , and the N-point DFT may then be performed on the phase-rotated samples.
  • Frame detection and frequency error estimation may also be performed in other manners based on the pilot- 1 OFDM symbol, and this is within the scope of the disclosure.
  • frame detection may be achieved by performing a direct correlation between the input samples for pilot- 1 OFDM symbol with the actual pilot- 1 sequence generated at the base station.
  • the direct correlation provides a high correlation result for each strong signal instance (or multipath). Since more than one multipath or peak may be obtained for a given base station, a wireless device would perform post-processing on the detected peaks to obtain timing information.
  • Frame detection may also be achieved with a combination of delayed correlation and direct correlation.
  • FIG. 9 shows a block diagram of an aspect of symbol timing detector 720, which performs timing synchronization based on the pilot-2 OFDM symbol.
  • a sample buffer 912 receives the input samples from receiver unit 154 and stores a "sample" window of L 2 input samples for the pilot-2 OFDM symbol. The start of the sample window is determined by a unit 910 based on the frame timing from frame detector 710.
  • FIG. 1OA shows a timing diagram of the processing for the pilot-2 OFDM symbol.
  • Frame detector 710 provides the coarse symbol timing (denoted as Tc) based on the pilot- 1 OFDM symbol.
  • the initial offset does not need to be accurate and is selected to ensure that one complete pilot-2 sequence is collected in sample buffer 912.
  • the initial offset may also be selected such that the processing for the pilot-2 OFDM symbol can be completed before the arrival of the next OFDM symbol, so that the symbol timing obtained from the pilot-2 OFDM symbol may be applied to this next OFDM symbol.
  • a DFT unit 914 performs an L 2 -point DFT on the L 2 input samples collected by sample buffer 912 and provides L 2 frequency-domain values for L 2 received pilot symbols.
  • a pilot demodulation unit 916 removes the modulation on the L 2 received pilot symbols by multiplying the received pilot symbol R k for each pilot subband k with the complex-conjugate of the known pilot symbol P k * for that subband, or R k - P k . Unit 916 also sets the received pilot symbols for the unused subbands to zero symbols.
  • An IDFT unit 918 then performs an L 2 -point IDFT on the L 2 pilot demodulated symbols and provides L 2 time-domain values, which are L 2 taps of an impulse response of the communication channel between base station 110 and wireless device 150.
  • FIG. 1OB shows the L 2 -tap channel impulse response from IDFT unit 918.
  • Each of the L 2 taps is associated with a complex channel gain at that tap delay.
  • the channel impulse response may be cyclically shifted, which means that the tail portion of the channel impulse response may wrap around and appear in the early portion of the output from IDFT unit 918.
  • a symbol timing searcher 920 may determine the symbol timing by searching for the peak in the energy of the channel impulse response.
  • the peak detection may be achieved by sliding a "detection" window across the channel impulse response, as indicated in FIG. 1OB.
  • the detection window size may be determined as described below. At each window starting position, the energy of all taps falling within the detection window is computed.
  • FIG. 1OC shows a plot of the energy of the channel taps at different window starting positions.
  • the detection window is shifted to the right circularly so that when the right edge of the detection window reaches the last tap at index L 2 , the window wraps around to the first tap at index 1. Energy is thus collected for the same number of channel taps for each window starting position.
  • the detection window size L w may be selected based on the expected delay spread of the system.
  • the delay spread at a wireless device is the time difference between the earliest and latest arriving signal components at the wireless device.
  • the delay spread of the system is the largest delay spread among all wireless devices in the system. If the detection window size is equal to or larger than the delay spread of the system, then the detection window, when properly aligned, would capture all of the energy of the channel impulse response.
  • the detection window size Lw may also be selected to be no more than half of L 2 (or L w ⁇ L 2 /2 ) to avoid ambiguity in the detection of the beginning of the channel impulse response.
  • the beginning of the channel impulse response may be detected by (1) determining the peak energy among all of the L 2 window starting positions and (2) identifying the rightmost window starting position with the peak energy, if multiple window starting positions have the same peak energy.
  • the energies for different window starting positions may also be averaged or filtered to obtain a more accurate estimate of the beginning of the channel impulse response in a noisy channel.
  • T B the beginning of the channel impulse response
  • T os T B - T w
  • Fine symbol timing may be uniquely computed once the beginning of the channel impulse response T B is determined. [0064] Referring to FIG. 1OA, the fine symbol timing is indicative of the start of the received OFDM symbol.
  • the fine symbol timing Ts may be used to accurately and properly place a "DFT" window for each subsequently received OFDM symbol.
  • the DFT window indicates the specific N input samples (from among N + C input samples) to collect for each received OFDM symbol.
  • the N input samples within the DFT window are then transformed with an N-point DFT to obtain N received data/pilot symbols for the received OFDM symbol.
  • the pilot-2 OFDM symbol may also be used to obtain a more accurate frequency error estimate.
  • the frequency error may be estimated using the pilot-2 sequences and based on equation (3). In this case, the summation is performed over L 2 samples (instead of Li samples) for the pilot-2 sequence.
  • the channel impulse response from IDFT unit 918 may also be used to derive a frequency response estimate for the communication channel between base station 110 and wireless device 150.
  • a unit 922 receives the L 2 -tap channel impulse response, circularly shifts the channel impulse response so that the beginning of the channel impulse response is at index 1 , inserts an appropriate number of zeros after the circularly-shifted channel impulse response, and provides an N-tap channel impulse response.
  • a DFT unit 924 then performs an N-point DFT on the N-tap channel impulse response and provides the frequency response estimate, which is composed of N complex channel gains for the N total subbands.
  • OFDM demodulator 160 may use the frequency response estimate for detection of received data symbols in subsequent OFDM symbols.
  • the channel estimate may also be derived in some other manner.
  • FIG. 11 shows a pilot transmission scheme with a combination of TDM and FDM pilots.
  • Base station 110 may transmit TDM pilots 1 and 2 in each super- frame to facilitate initial acquisition by the wireless devices.
  • the overhead for the TDM pilots is two OFDM symbols, which may be small compared to the size of the super- frame.
  • the base station may also transmit an FDM pilot in all, most, or some of the remaining OFDM symbols in each super- frame.
  • the FDM pilot is sent on alternating sets of subbands such that pilot symbols are sent on one set of subbands in even-numbered symbol periods and on another set of subbands in odd- numbered symbol periods.
  • Each set contains a sufficient number of (Lfd m ) subbands to support channel estimation and possibly frequency and time tracking by the wireless devices.
  • the subbands in one set may be staggered or offset with respect to the subbands in the other set, so that the subbands in the two sets are interlaced with one another.
  • N 4096
  • L fdm 512
  • S fdm 8
  • the subbands in the two sets may be staggered by four subbands.
  • a wireless device may use TDM pilots 1 and 2 for initial synchronization, e.g., frame synchronization, frequency offset estimation, and fine symbol timing acquisition (for proper placement of the DFT window for subsequent OFDM symbols).
  • the wireless device may perform initial synchronization, for example, when accessing a base station for the first time, when receiving or requesting data for the first time or after a long period of inactivity, when first powered on, and so on.
  • the wireless device may perform delayed correlation of the pilot- 1 sequences to detect for the presence of a pilot- 1 OFDM symbol and thus the start of a super- frame, as described above. Thereafter, the wireless device may use the pilot- 1 sequences to estimate the frequency error in the pilot- 1 OFDM symbol and to correct for this frequency error prior to receiving the pilot-2 OFDM symbol.
  • the pilot- 1 OFDM symbol allows for estimation of a larger frequency error and for more reliable placement of the DFT window for the next (pilot-2) OFDM symbol than conventional methods that use the cyclic prefix structure of the data OFDM symbols.
  • the pilot- 1 OFDM symbol can thus provide improved performance for a terrestrial radio channel with a large multi-path delay spread.
  • the wireless device may use the pilot-2 OFDM symbol to obtain fine symbol timing to more accurately place the DFT window for subsequent received OFDM symbols.
  • the wireless device may also use the pilot-2 OFDM symbol for channel estimation and frequency error estimation.
  • the pilot-2 OFDM symbol allows for fast and accurate determination of the fine symbol timing and proper placement of the DFT window.
  • the wireless device may use the FDM pilot for channel estimation and time tracking and possibly for frequency tracking.
  • the wireless device may obtain an initial channel estimate based on the pilot-2 OFDM symbol, as described above.
  • the wireless device may use the FDM pilot to obtain a more accurate channel estimate, particularly if the FDM pilot is transmitted across the super-frame, as shown in FIG. 11.
  • the wireless device may also use the FDM pilot to update the frequency tracking loop that can correct for frequency error in the received OFDM symbols.
  • the wireless device may further use the FDM pilot to update a time tracking loop that can account for timing drift in the input samples (e.g., due to changes in the channel impulse response of the communication channel).
  • OFDM symbol duration is approximately scaled. For example, 1 x 4K OFDM symbol ⁇ 4 x IK OFDM symbols ⁇ 2 x 2K OFDM symbols ⁇ 1 A of an 8K OFDM symbol.
  • time-domain OFDM parameters are the same when expressed in units of chips.
  • the TDM pilot 1 has the same number of samples as in the 4K mode.
  • the 8K-mode TDM pilot 1 acquisition algorithm is similar to its 4K-mode counterpart; however, the period consists of 256 samples (Li) instead of only 128 samples in the 4K mode. Further, the 8K mode TDM pilot 1 symbol consists of 18 periods (Si).
  • the 2K-mode TDM pilot 1 acquisition algorithm is similar to its 4K counterpart; however, the period is 64 samples (Li) instead of 128 samples.
  • the 2K mode TDM pilot 1 symbol consists of 72 periods (Si).
  • the TDM pilot 1 channel duration is the same for all FFT sizes. However, the number of non-zero subbands decreases in a substantially proportional manner with FFT size.
  • the TDM pilot 2 in the previously-described 4K system, consists of 2000 non-zero subbands, or 4 non-zero interlaces. For example, each interlace may be modulated by zero data symbols scrambled by a PN sequence. There is one zero subband between any two adjacent non-zero subband.
  • TDM pilot 2 is periodic with two periods (L 2 ), each of which is 2048 chips long.
  • TDM pilot 2 always consists of two periods and a guard interval. However, the period length may vary, depending on FFT size. For example, the period length will be IK, 2K, 2K and 8K for FFT sizes of IK, 2K, 4K and 8K, respectively.
  • FFT sizes are merely exemplary, and the present disclosure is not limited to FFT sizes of only IK, 2K, 4K and 8K. Note that the period lengths for the 2K and 4K systems are identical.
  • the following chart illustrates the number of slots, the flat guard interval and the OFDM symbol interval for FFT sizes of IK, 2K, 4K and 8K, respectively:
  • TDM pilot 2 contains as many non-zero subcarriers as the data symbols (all N of them), but the pilot symbol is roughly twice as long.
  • the periodicity of TDM pilot 2 is not achieved by inserting S 2 zero subbands between non-zero subbands, but by physically repeating the time-domain sequence after the IFFT at the transmitter, as a postfix.
  • TpGi cyclic prefix
  • T WG I window guard interval between OFDM symbols
  • T PF i post-fix interval
  • Tu useful part duration
  • Ts total symbol duration. Note that the duration of the postfix interval can vary; in TDM pilot 2. Obviously, different implementations and time durations are possible.
  • TDM Pilot 2 should consist of at least 2 time-domain periods, and the replication of the periods can be achieved either by inserting zero subbands (as in 4K mode), or by inserting a time- domain post-fix (as in other FFT modes described above).
  • N number of non-zero subcarriers in TDM Pilot 2
  • the number of nonzero subcarriers is a fraction of N.
  • this number is equal to N in IK, 2K and 8K mode, and is N/2 in 4K mode. Note that in case (i), repetition is achieved by explicitly inserting a post-fix, roughly of length N, if one plans on having just 2 periods (see Fig. 13), and the TDM2 duration is 2N+TFGI+TWGL.
  • a signaling parameter channel is required from the transmission side to signal to the receiving side the OFDM parameters (including the appropriate FFT size) corresponding to the transmission.
  • the SPC may use previously reserved OFDM symbols at an end of a super-frame.
  • aspects of the present disclosure are not limited to any manner of notifying the receiving side of the OFDM parameters.
  • FIG. 12 depicts, as an example, how 2K subbands would correspond to alternate 4K subbands. Similarly, 8K subbands would be packed twice as densely as the 4K subbands, and IK subbands would correspond to every fourth one of the 4K subbands.
  • the number of active subbands in a IK, 2K, 4K and 8K OFDM system would be 1000, 2000, 4000 and 8000, respectively.
  • the subband spacing ⁇ / " sc is:
  • the transmission side can commence with periodically transmitting the first pilot on a first set of frequency subbands in a time division multiplexed manner with data, and the second pilot on a second set of frequency subbands in a TDM manner with the data, wherein the second set includes more subbands than the first set.
  • the first and second pilots can be used for synchronization by receivers in the system, using the methods described herein.
  • the first pilot may be used to detect the start of each superframe
  • the second pilot may be used to determine symbol timing indicative of start of received OFDM symbols, as provided in the foregoing description for some aspects of the present disclosure.
  • the present disclosure is not limited to the specific methods of timing synchronization using TDM pilots, and one of ordinary skill in the art would realize that equivalent methods could be used without departing from the scope of the claimed invention.
  • the synchronization techniques described herein may be implemented by various means. For example, these techniques may be implemented in hardware, software, or a combination thereof.
  • the processing units at a base station used to support synchronization may be implemented within one or more application specific integrated circuits (ASICs), digital signal processors (DSPs), digital signal processing devices (DSPDs), programmable logic devices (PLDs), field programmable gate arrays (FPGAs), processors, controllers, micro-controllers, microprocessors, other electronic units designed to perform the functions described herein, or a combination thereof.
  • ASICs application specific integrated circuits
  • DSPs digital signal processors
  • DSPDs digital signal processing devices
  • PLDs programmable logic devices
  • FPGAs field programmable gate arrays
  • processors controllers, micro-controllers, microprocessors, other electronic units designed to perform the functions described herein, or a combination thereof.
  • the processing units at a wireless device used to perform synchronization e.g., synchronization and channel estimation unit 180
  • the synchronization techniques may be implemented with modules (e.g., procedures, functions, and so on) that perform the functions described herein.
  • the software codes may be stored in a memory unit (e.g., memory unit 192 in FIG. 1) and executed by a processor (e.g., controller 190).
  • the memory unit may be implemented within the processor or external to the processor.

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Abstract

Selon l'invention, dans un système OFDM, un émetteur diffuse, dans chaque trame, un premier pilote TDM dans un premier ensemble de sous-bandes, suivi d'un second pilote TDM dans un second ensemble de sous-bandes. Les sous-bandes de chaque ensemble sont choisies parmi N sous-bandes totales de telle sorte que: 1) un symbole OFDM pour le premier pilote TDM contienne au moins S1 séquences de pilote-1 identiques de longueur L1; et 2) un symbole OFDM pour le second pilote TDM contienne au moins S2 séquences de pilote-2 identiques de longueur L2, selon la relation L2 > L1, S1 • L1 = N, and S2 • L2 = N. L'émetteur peut également diffuser un premier pilote FDM. Un récepteur traite le premier pilote TDM afin d'obtenir une synchronisation de trames (p. ex. en établissant une corrélation entre différentes séquences de pilote-1); et traite ensuite le second pilote TDM afin d'obtenir une synchronisation de symboles (p. ex. en détectant le début d'une estimation de réponse impulsionnelle dans la voie émanant du second pilote TDM).
EP08844052A 2007-10-31 2008-10-31 Synchronisation dans un système ofdm de radiodiffusion utilisant des pilotes à multiplexage temporel Withdrawn EP2225844A2 (fr)

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US8477795B2 (en) * 2009-08-24 2013-07-02 Telefonaktiebolaget L M Ericsson (Publ) LDP IGP synchronization for broadcast networks
US8665976B2 (en) 2011-03-31 2014-03-04 Saankhya Labs Pvt. Ltd. Blind symbol synchronization scheme for OFDM system
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US7548506B2 (en) * 2001-10-17 2009-06-16 Nortel Networks Limited System access and synchronization methods for MIMO OFDM communications systems and physical layer packet and preamble design
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