EP1931181B1 - Ballast for a discharge lamp - Google Patents
Ballast for a discharge lamp Download PDFInfo
- Publication number
- EP1931181B1 EP1931181B1 EP07121725A EP07121725A EP1931181B1 EP 1931181 B1 EP1931181 B1 EP 1931181B1 EP 07121725 A EP07121725 A EP 07121725A EP 07121725 A EP07121725 A EP 07121725A EP 1931181 B1 EP1931181 B1 EP 1931181B1
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- Prior art keywords
- voltage
- ballast
- vout
- vignit
- winding
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- 238000004804 winding Methods 0.000 claims abstract description 79
- 239000003990 capacitor Substances 0.000 claims description 56
- 230000009466 transformation Effects 0.000 claims description 26
- 238000010586 diagram Methods 0.000 description 5
- 238000000034 method Methods 0.000 description 5
- 238000010891 electric arc Methods 0.000 description 3
- 230000003252 repetitive effect Effects 0.000 description 3
- 229910052724 xenon Inorganic materials 0.000 description 3
- FHNFHKCVQCLJFQ-UHFFFAOYSA-N xenon atom Chemical compound [Xe] FHNFHKCVQCLJFQ-UHFFFAOYSA-N 0.000 description 3
- 239000003708 ampul Substances 0.000 description 2
- 238000001914 filtration Methods 0.000 description 2
- 230000004907 flux Effects 0.000 description 2
- 238000002955 isolation Methods 0.000 description 2
- 229910052753 mercury Inorganic materials 0.000 description 2
- 230000008569 process Effects 0.000 description 2
- 230000000750 progressive effect Effects 0.000 description 2
- 229910001369 Brass Inorganic materials 0.000 description 1
- 230000003416 augmentation Effects 0.000 description 1
- 239000010951 brass Substances 0.000 description 1
- 230000015556 catabolic process Effects 0.000 description 1
- 230000003111 delayed effect Effects 0.000 description 1
- 230000005347 demagnetization Effects 0.000 description 1
- 230000001939 inductive effect Effects 0.000 description 1
- 230000005415 magnetization Effects 0.000 description 1
- QSHDDOUJBYECFT-UHFFFAOYSA-N mercury Chemical compound [Hg] QSHDDOUJBYECFT-UHFFFAOYSA-N 0.000 description 1
- 210000000056 organ Anatomy 0.000 description 1
- 244000045947 parasite Species 0.000 description 1
- 230000003071 parasitic effect Effects 0.000 description 1
- 238000011084 recovery Methods 0.000 description 1
- 230000009467 reduction Effects 0.000 description 1
- 230000004044 response Effects 0.000 description 1
- 230000002441 reversible effect Effects 0.000 description 1
- 230000011664 signaling Effects 0.000 description 1
- 238000004513 sizing Methods 0.000 description 1
- 239000007858 starting material Substances 0.000 description 1
- 230000007704 transition Effects 0.000 description 1
Images
Classifications
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- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/14—Circuit arrangements
- H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
- H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
- H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
- H05B41/2821—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a single-switch converter or a parallel push-pull converter in the final stage
- H05B41/2822—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a single-switch converter or a parallel push-pull converter in the final stage using specially adapted components in the load circuit, e.g. feed-back transformers, piezoelectric transformers; using specially adapted load circuit configurations
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- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
- H05B41/02—Details
- H05B41/04—Starting switches
- H05B41/042—Starting switches using semiconductor devices
Definitions
- the present invention relates to a lighting ballast for a discharge lamp and a fire device incorporating a lamp connected to such a ballast.
- these high voltages are produced by a power supply module, which also provides power regulation, known as "ballast".
- the most recent ballasts include in particular a DC / DC switching converter producing a high DC voltage of several hundred volts from the battery voltage for example, a DC / AC converter ensuring the supply of the lamp in steady state to from the high-voltage DC, and a high-voltage module supplying a generator producing the very high voltage necessary for lighting the lamp, the very high voltage being produced from the high DC voltage produced by the DC / DC converter.
- the DC / DC converter of such a ballast comprises a transformer comprising a main winding and two secondary windings with a transformation ratio equal to 8 with more than 20 turns in the two secondary windings and a rectifier voltage associated with each secondary winding, each rectifier comprising a diode and a capacitor.
- the main winding is connected to a switching unit connected to the power source.
- the repetitive interruption of the latter by the switching unit induces at the terminals of the two secondary windings of the transformer respectively two high voltages each rectified by the diode and filtered by the capacitor of the associated rectifier.
- the difference between these two high voltages makes it possible to obtain a voltage of 1000V. From this voltage of 1000V, an ignition voltage of about 25kV is obtained by the high voltage module connected between the DC / DC converter and the discharge lamp.
- the transformer occupies a very large volume because of the important transformation ratio.
- the leakage elements are important which can create overvoltages in the switching unit and interfere with the control of the DC / DC converter.
- the rectifying diodes must be dimensioned for a voltage of 1000V, which poses problems of realization and cost.
- the document JP 2001 284 089 discloses a discharge lamp ballast comprising a converter, a voltage multiplier and a transformer comprising a main winding, a secondary winding and an auxiliary winding.
- the present invention aims to overcome these disadvantages of the state of the art.
- the invention relates to a second object, a vehicle fire device comprising a discharge lamp to which is connected a ballast according to any one of the preceding characteristics, the ballast being able to provide a voltage to allow a lighting of the lamp for discharge.
- a BLST ballast connected to a discharge lamp LA in the context of a non-limiting application of vehicle fire FX.
- the FX fire is for example, a traffic light (night lights, codes, taillights) or lighting called projector (lighthouse).
- the term "fire" will be used indifferently to designate such lighting or signaling devices.
- the LA discharge lamp can be used for day and / or night lighting.
- ballast BLST is positioned on the same PCB type PCB ("Printed Circuit Board").
- the DC / DC converter Ccc makes it possible to adapt the power source, in this case the battery voltage Vbat, to the discharge lamp voltage by generating the continuous high voltage rectified Vout and the ignition voltage Vignit.
- the HV high voltage module of the discharge lamp LA will be able to generate a first ignition pulse Um, of the order of 25kV to turn on said lamp LA.
- the DC / DC converter Ccc may furthermore comprise a resistor R1 mounted at the output of the multiplier circuit MU to allow the charging of a capacitor of the high voltage module HV of the discharge lamp LA to be delayed as we will see in detail later.
- the secondary winding n2 is defined in such a way that the transformation ratio n2 / n1 between this winding n2 and the main winding n1 is equal to 5.
- the auxiliary winding n3 is defined in such a way that the transformation ratio n3 / n1 between this winding n3 and the main winding n1 is equal to 2.
- the number of turns in the main winding n1 is equal to 4
- the number of turns in the secondary winding n2 is equal to 20
- the number of turns in the auxiliary winding n3 is equal at 8.
- the switching member is a MOSFET transistor.
- the circuit RD comprising for this purpose a rectifying diode Dout and a filtering capacitor Cout.
- the rectifying diode Dout is connected to the node P1 between the secondary windings n2 and auxiliary winding n3 by its cathode as illustrated in FIG. Fig. 2 .
- the multiplier MU is composed of two diodes D1, D2 and two capacitors C1, C2.
- the capacitors C1 and C2 provide the ignition voltage Vignit, while the diodes D1 and D2, during the ignition phase, on the one hand to charge the capacitors C1 and C2 associated and on the other hand their avoid being discharged in a sense as we will see later.
- the DC / DC converter Ccc has the same elements as in the first embodiment but with an inverted bias of the rectifying diode Dout and the diodes of the multiplier circuit D1, D2. Moreover, the rectifier circuit RD makes it possible to rectify the induced auxiliary voltage Vn3 instead of the induced secondary voltage Vn2. At this time, the rectified voltage Vout is positive and the ignition voltage Vignit is negative.
- This converter makes it possible to make the rectified high voltage Vout alternative necessary for the operation of the steady-state discharge lamp LA, that is to say during normal operation of the lamp, from the continuous rectified voltage Vout supplied by the DC / DC converter.
- the DC / AC converter Cca comprises four transistors (not shown) mounted in complete bridge, the simultaneous opening or closing of a pair of transistors being controlled alternately with that of the another pair to make the voltage rectified.
- these transistors are NPN transistors of the IGBT type "Insulated Gate Bipolar Transistor", well adapted to the high voltages involved, both during the ignition phase and during the steady state of the lamp LA.
- control unit UC makes it possible to control, by means of control signals in response to external control commands, the width of the switching pulses of the DC / DC converter Ccc, as well as the operation of the complete bridge of the AC / DC converter whether in the ignition phase or in steady state.
- the BLST ballast provides the voltage necessary to turn on the lamp during an ignition phase, but also provides the voltage required to operate the lamp when it is on.
- the BLST ballast operates in the following manner.
- a supply voltage Vbat equal to 10 V is used.
- this battery voltage Vbat varies between 8V (for example during a start) and 12V with possible peaks at 19V (norm given by the manufacturer).
- the ballast BLST will provide on the one hand the continuous rectified voltage Vout and on the other hand the ignition voltage Vignit, the potential difference between these two voltages, to feed the high module HV lamp voltage LA to turn on said lamp.
- the switching member GMOS when closed, it allows a loading of the second capacitor C2 of the multiplier circuit MU for supplying the ignition voltage Vignit, while when it is open , it allows to charging the filter capacitor Cout for providing the DC rectified voltage Vout, and charging the first capacitor C1 MU multiplier circuit to also provide the Vignit boot voltage.
- the switching member GMOS which is controlled by cutting pulses, allows through its opening and closing repetitive gradually load the three capacitors alternately.
- the switching frequency of the GMOS switching element is 100 kHz during this ignition phase.
- the MOSFET transistor that composes the switching member GMOS comprises a gate voltage Vgs and a drain-source voltage Vds that vary as a function of the opening-closing of the MOSFET transistor also causing a variation of the main voltages Vn1, secondary induced. Vn2 and induced auxiliary Vn3 of transformer TR1.
- the evolution of these voltages Vn1, Vn2, Vn3 associated with the transformers TR1 makes it possible to charge the capacitors C1, C2, Cout supplying the continuous rectified voltage Vout and the ignition voltage Vignit.
- transformer voltages TR1 as a function of the two states (closed-open) of the MOSFET transistor is described below when the capacitors C1, C2, Cout are fully charged.
- the main winding n1 is connected directly to the power source Vbat.
- the main voltage Vn1 is equal to the battery voltage Vbat, ie is equal to 10V in the example taken.
- a main current Ip is then generated and passes through the main winding n1 of the transformer TR1.
- the induced currents ln2 and ln3 go in the opposite direction of the clockwise.
- the induced secondary voltage Vn2 is equal to 50 and the induced auxiliary voltage Vn3 is equal to 20 as illustrated in FIG. Fig. 3 .
- the righting diode Dout is then blocked. It is represented in dashed line at Fig. 4 . It is the same for the first diode D1 MU multiplier circuit.
- the second diode D2 of the multiplying circuit MU is conducting (there is approximately 0V at its terminals).
- the second capacitor C2 of the multiplier circuit MU is loaded via this second diode D2.
- the first diode D1 being blocked, the first capacitor C1 of the multiplier circuit MU discharges via the second diode D2 to the second capacitor C2.
- the second capacitor C2 is thus charged with the induced secondary voltages Vn2, induced auxiliary Vn3 and the voltage Vc1 of the first capacitor C1.
- Vignit + 630V.
- the ignition voltage Vignit is well supplied by the charging of the second capacitor C2 of the multiplier circuit MU and is well generated from the rectified voltage Vout.
- Vn2_off Vn3_off the voltages across respective windings n2 and n3 when the MOSFET is open
- Vn2_on, Vn3_on the voltages when the MOSFET is closed.
- the MOSFET transistor is open.
- the gate voltage Vgs is zero, the MOSFET transistor behaves like a diode passing from the source to the drain.
- the drain-source voltage Vds is therefore positive as illustrated in FIG. Fig. 3 .
- the opening of the MOSFET transistor prevents the main current Ip from flowing.
- the recovery diode Dout is busy, as well as the first diode D1 of the multiplier circuit MU, while the second diode D2 of the multiplier circuit MU is blocked (it is represented in dotted lines).
- the Dout rectifying diode being conducting one has about 0V at its terminals
- the filtering capacitor Cout is charged by said diode Dout.
- the GMOS switching element is controlled in such a way that the charge of the filter capacitor Cout is equal to -400V.
- a control device (not shown) which measures the charge of the filter capacitor Cout.
- Vout -400V at the end of the loading of the capacitor Cout.
- the first diode D1 being conducting (one has about 0V at its terminals), the first capacitor C1 of the multiplier circuit MU is charged through this diode D1.
- the first capacitor C1 is thus charged with the induced secondary voltages Vn2 and induced auxiliary Vn3.
- the second capacitor C2 of the multiplier circuit MU can not at this time be discharged towards the first capacitor C1 because the second diode D2 is blocked.
- the second capacitor C2 discharges into the circuit (capacitor C3) of the lamp LA as will be seen below.
- the charging time of the second capacitor C2 is around tens of microseconds (1 / 100kHz) while the discharge time is around a few milliseconds (thanks to a resistance R1 as discussed below) .
- the capacitor C2 becomes charged thereby providing the Vignit ignition voltage from the rectified voltage Vout, while when the MOSFET transistor is open, the filter capacitor Cout is charged thereby providing the rectified voltage Vout.
- the diodes D1 and D2 of the multiplier circuit MU must be sized to hold a voltage of the order of 800V.
- Vrmax is equal to Vignit.
- the first diode D1 when the first capacitor C1 is charged, the first diode D1 is conducting (therefore the voltage at its terminals is 0V), so the voltage of the second diode D2 corresponds to Vignit.
- the second diode D1 when the second capacitor C2 is charged, the second diode D1 is conducting (therefore the voltage at its terminals is 0V), so the voltage of the first diode D1 corresponds to Vignit.
- the voltage difference Vdiff is applied to the HV high voltage module as indicated in FIG. Fig. 6 .
- the gas spark gap Gz behaves like an open switch.
- the capacitor C3 is charged.
- a predetermined threshold of charging of the order of 800V in a non-limiting example, the spark gap Gz becomes abruptly conductive and creates a current pulse in the primary winding of the transformer TR2 which produces in the secondary the very high Um voltage of 25kV, thus creating a first electric arc necessary for lighting the lamp LA.
- the capacitor C3 discharges very quickly in the transformer TR2.
- This voltage is of the order of -85V steady state for a xenon lamp with mercury (Hg + ) and of the order of -42V for a mercury-free xenon lamp (Hg - ).
- control unit UC acts to activate and deactivate the transistors of the DC / AC converter so that it supplies this AC voltage from the rectified voltage Vout necessary to continue operating the lamp LA.
- This AC voltage is obtained from the DC rectified voltage Vout supplied by the DC / DC converter Ccc.
- the DC / DC converter Ccc provides the power necessary for the rectified voltage Vout is in this case equal to -85V.
- the frequency switching speed of the GMOS switching element is 300kHz in steady state.
- the MOSFET switching transistor remains open longer than steady state.
- the Fig. 7 summarizes the evolution of the voltage Ula across the discharge lamp LA during the ignition phase and during the steady state.
- the interval t0-t1 represents the ignition phase, while the interval t3-t4 represents the steady-state operating phase.
- intervals t1-t2 and t2-t3 represent transition phases.
- the rectified voltage Vout begins to decrease (the capacitor Cout of the rectifier circuit discharges) while the ignition voltage Vignit drops to -400V because the capacitor C3 discharges suddenly, its voltage Vc3 becomes zero, the rectified voltage Vout remaining at -400V.
- the rectified voltage continues Vout is made alternative by means of the DC / AC converter Cca.
- the voltage Ula of the lamp LA is equal to the rectified voltage Vout.
- the two curves Cvignit and Cvout representative respectively of the two voltages Vignit and Vout illustrate the progressive loading of capacitors C2 and Cout corresponding.
- the slope of the curve Cvignit representative of the ignition voltage Vignit is greater than that of the curve Cvout representative of the rectified voltage Vout because the filter capacitor Cout is dimensioned so as to be larger than the second capacitor C2.
- the capacitor Cout generates the greatest power to the lamp LA and corresponds to a reserve of energy. Indeed, in steady state, it is the only one to supply energy to the lamp LA.
- the Vignit ignition voltage can reach its maximum value + 630V at time t1 before the rectified voltage reaches its -400V. This could generate a voltage difference at time t1 less than 1030V, for example at about 800V, the rectified voltage Vout reaching only 200V for example. This voltage difference Vdiff can cause ignition of the lamp LA.
- the conduction threshold of the gas spark gap Gz is of the order of 800V
- the voltage difference Vdiff is at the threshold limit of the gas spark gap; also the LA lamp may not light properly.
- the resistor R1 of the BLST ballast makes it possible to delay the charging of the capacitor C3 of the lamp LA with the ignition voltage Vignit as illustrated by the curve CRvignit.
- the two voltage Vignit and Vout will reach their maximum value at the same time so as to provide a potential difference sufficient to exceed the loading threshold of the gas spark gap thus allowing a reliable ignition of the lamp LA.
- the resistor R1 makes it possible to wait for the rectified voltage Vout to be stabilized at -400V in order to make it possible to obtain a voltage difference Vdiff greater than the conduction threshold of the gas spark gap Gz so as to obtain an arc of sufficient voltage. (25kV) required for reliable ignition of the LA lamp.
- this resistor R1 prevents current peaks in the second diode D2 and thus prevents the latter from being damaged.
- the vehicle fire application was taken as an example, but of course, the described ballast can be used in other applications such as, in non-limiting examples, interior lighting building ("Interior Lighting ”) Or street lighting ("General Lighting ").
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- Circuit Arrangements For Discharge Lamps (AREA)
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Abstract
Description
La présente invention concerne un ballast d'éclairage pour lampe à décharge et un dispositif de feu incorporant une lampe reliée à un tel ballast.The present invention relates to a lighting ballast for a discharge lamp and a fire device incorporating a lamp connected to such a ballast.
Elle trouve une application particulière dans le domaine des véhicules automobiles.It finds a particular application in the field of motor vehicles.
Dans le but d'améliorer à la fois la puissance lumineuse et le rendement énergétique des sources lumineuses utilisées dans de nombreux domaines, tels que ceux des phares de véhicules ou des vidéo projecteurs, l'évolution technique actuelle conduit à remplacer les lampes à filament par des lampes à décharge gazeuse à haute intensité. A la différence des lampes à filament, qui étaient conçues pour être connectées directement à une source basse tension, comme la batterie d'un véhicule, ou moyenne tension, telle que le secteur domestique à 110 ou 220V, ces nouvelles lampes nécessitent des tensions élevées pour créer un arc électrique permettant de les allumer.In order to improve both the light output and the energy efficiency of the light sources used in many fields, such as vehicle headlights or video projectors, the current technical evolution has led to the replacement of the filament lamps with high intensity gas discharge lamps. Unlike filament lamps, which were designed to be connected directly to a low-voltage source, such as a vehicle battery, or medium voltage, such as the 110 or 220V domestic sector, these new lamps require high voltages to create an electric arc to light them.
Dans le domaine de l'automobile, par exemple, ces tensions élevées sont produites par un module d'alimentation, qui assure également la régulation de puissance, connu sous le nom de "ballast".In the automotive field, for example, these high voltages are produced by a power supply module, which also provides power regulation, known as "ballast".
Les ballasts les plus récents comportent en particulier un convertisseur continu/continu à découpage produisant une haute tension continue de plusieurs centaines de volts à partir de la tension batterie par exemple, un convertisseur continu/alternatif assurant l'alimentation de la lampe en régime permanent à partir de la haute tension continue, et un module haute tension alimentant un générateur produisant la très haute tension nécessaire à l'allumage de la lampe, la très haute tension étant produite à partir de la haute tension continue produite par le convertisseur continu/continu.The most recent ballasts include in particular a DC / DC switching converter producing a high DC voltage of several hundred volts from the battery voltage for example, a DC / AC converter ensuring the supply of the lamp in steady state to from the high-voltage DC, and a high-voltage module supplying a generator producing the very high voltage necessary for lighting the lamp, the very high voltage being produced from the high DC voltage produced by the DC / DC converter.
Selon un état de la technique connu, le convertisseur continu/continu d'un tel ballast comprend un transformateur comprenant un enroulement principal et deux enroulements secondaires avec un rapport de transformation égal à 8 avec plus de 20 spires dans les deux enroulements secondaires et un redresseur de tension associé à chaque enroulement secondaire, chaque redresseur comprenant une diode et un condensateur. L'enroulement principal est relié à une unité de commutation reliée à la source d'alimentation. L'interruption répétitive de cette dernière par l'unité de commutation induit aux bornes des deux enroulements secondaires du transformateur respectivement deux hautes tensions redressée chacune par la diode et filtrée par le condensateur du redresseur associé. La différence entre ces deux hautes tensions permet d'obtenir une tension de 1000V. A partir de cette tension de 1000V, une tension d'allumage d'environ 25kV est obtenue par le module haute tension relié entre le convertisseur continu/continu et la lampe à décharge.According to a known state of the art, the DC / DC converter of such a ballast comprises a transformer comprising a main winding and two secondary windings with a transformation ratio equal to 8 with more than 20 turns in the two secondary windings and a rectifier voltage associated with each secondary winding, each rectifier comprising a diode and a capacitor. The main winding is connected to a switching unit connected to the power source. The repetitive interruption of the latter by the switching unit induces at the terminals of the two secondary windings of the transformer respectively two high voltages each rectified by the diode and filtered by the capacitor of the associated rectifier. The difference between these two high voltages makes it possible to obtain a voltage of 1000V. From this voltage of 1000V, an ignition voltage of about 25kV is obtained by the high voltage module connected between the DC / DC converter and the discharge lamp.
Une telle solution présente les inconvénients suivants. Le transformateur occupe un volume très important du fait du rapport de transformation important. De plus, du fait de ce volume, les éléments de fuite sont importants ce qui peut créer des surtensions dans l'unité de commutation et gêner la commande du convertisseur continu/continu. Par ailleurs, les diodes de redressement doivent être dimensionnées pour une tension de 1000V, ce qui pose des problèmes de réalisation et de coût.Such a solution has the following drawbacks. The transformer occupies a very large volume because of the important transformation ratio. In addition, because of this volume, the leakage elements are important which can create overvoltages in the switching unit and interfere with the control of the DC / DC converter. Moreover, the rectifying diodes must be dimensioned for a voltage of 1000V, which poses problems of realization and cost.
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Le document
La présente invention a pour but de remédier à ces inconvénients de l'état de la technique.The present invention aims to overcome these disadvantages of the state of the art.
En effet, elle concerne selon un premier objet, un ballast pour lampe à décharge comprenant :
- un convertisseur de tension continu/continu pour fournir une tension redressée continue,
- un transformateur comprenant un enroulement principal, un enroulement secondaire et un enroulement auxiliaire, le transformateur permettant de fournir la tension redressée continue, et
- un circuit multiplieur de tension pour fournir une tension d'amorçage, la différence de potentiel entre cette tension et la tension redressée continue permettant de créer une tension d'allumage pour la lampe à décharge.
- a DC / DC voltage converter for providing a DC rectified voltage,
- a transformer comprising a main winding, a secondary winding and an auxiliary winding, the transformer for providing the DC rectified voltage, and
- a voltage multiplier circuit for providing a starting voltage, the potential difference between this voltage and the DC rectified voltage for creating an ignition voltage for the discharge lamp.
Comme on le verra en détail plus loin, le fait de combiner un circuit multiplieur avec un transformateur muni d'un enroulement secondaire et d'un enroulement auxiliaire va permettre d'obtenir une tension d'amorçage à partir d'une tension redressée continue, et par conséquent va permettre de réduire le nombre de spires dans les enroulements secondaire et auxiliaire de sorte à obtenir de faibles rapports de transformation et donc un dimensionnement du transformateur n'entraînant pas des éléments de fuite importants. Par suite, on évite un dimensionnement hors standard de composants tels que des diodes, tout en fournissant une tension en entrée d'un module haute tension de la lampe à décharge suffisamment élevée pour fournir la tension d'allumage à ladite lampe.As will be seen in detail below, the fact of combining a multiplier circuit with a transformer provided with a secondary winding and an auxiliary winding will make it possible to obtain a starting voltage from a continuous rectified voltage. and consequently will make it possible to reduce the number of turns in the secondary and auxiliary windings so as to obtain low transformation ratios and therefore a sizing of the transformer that does not lead to significant leakage elements. As a result, non-standard dimensioning of components such as diodes is avoided, while providing an input voltage of a high voltage module of the discharge lamp sufficiently high to provide the ignition voltage to said lamp.
Selon des modes de réalisation non limitatifs, le ballast comporte les caractéristiques supplémentaires suivantes :
- le circuit multiplieur de tension comporte deux condensateurs et deux diodes. Les deux condensateurs permettent de fournir la tension d'amorçage tandis que les deux diodes permettent le chargement des condensateurs pendant une phase d'allumage ;
- l'enroulement auxiliaire vient dans le prolongement de l'enroulement secondaire. Cela permet de générer la tension d'amorçage en utilisant la somme des tensions générées par l'enroulement secondaire et l'enroulement auxiliaire dont fait partie la tension redressée continue ;
- le ballast comporte en outre une résistance en sortie du circuit multiplieur de tension. Elle permet de retarder le chargement d'un condensateur fournissant la tension d'amorçage de sorte que la différence de potentiel entre cette tension et la tension redressée soit optimale pour l'allumage de la lampe ;
- le convertisseur continu/continu comprend un unique redresseur de tension. Il permet de fournir la tension redressée continue ;
- l'enroulement secondaire comporte un rapport de transformation avec l'enroulement principal de l'ordre de 5. Ainsi, le faible rapport de transformation permet de réduire le volume global du transformateur et donc les éléments de fuite ;
- l'enroulement auxiliaire comporte un rapport de transformation avec l'enroulement principal de l'ordre de 2. Ainsi, le faible rapport de transformation permet de réduire le volume global du transformateur et donc les éléments de fuite.
- the voltage multiplier circuit comprises two capacitors and two diodes. The two capacitors provide the ignition voltage while the two diodes allow charging capacitors during an ignition phase;
- the auxiliary winding comes in the extension of the secondary winding. This makes it possible to generate the ignition voltage using the sum of the voltages generated by the secondary winding and the auxiliary winding of which the DC rectified voltage is part;
- the ballast further comprises a resistance at the output of the voltage multiplier circuit. It makes it possible to delay the charging of a capacitor supplying the ignition voltage such that the potential difference between this voltage and the rectified voltage is optimal for lighting the lamp;
- the DC / DC converter comprises a single voltage rectifier. It provides the continuous rectified voltage;
- the secondary winding has a transformation ratio with the main winding of the order of 5. Thus, the low transformation ratio reduces the overall volume of the transformer and therefore the leakage elements;
- the auxiliary winding has a transformation ratio with the main winding of the order of 2. Thus, the low transformation ratio reduces the overall volume of the transformer and therefore the leakage elements.
L'invention concerne selon un deuxième objet, un dispositif de feu pour véhicule comprenant une lampe à décharge à laquelle est relié un ballast selon l'une quelconque des caractéristiques précédentes, le ballast étant apte à fournir une tension pour permettre un allumage de la lampe à décharge.The invention relates to a second object, a vehicle fire device comprising a discharge lamp to which is connected a ballast according to any one of the preceding characteristics, the ballast being able to provide a voltage to allow a lighting of the lamp for discharge.
D'autres caractéristiques et avantages de la présente invention seront mieux compris à l'aide de la description et des dessins non limitatifs parmi lesquels :
- la
Fig. 1 représente schématiquement un dispositif de feu de véhicule comprenant une lampe à décharge et un ballast selon l'invention ; - la
Fig. 2 est un schéma d'un premier mode de réalisation non limitatif d'un ballast selon l'invention ; - la
Fig. 3 est un premier diagramme de tensions fournies par des composants du ballast selon laFig. 2 ; - la
Fig. 4 représente schématiquement un convertisseur tension continu/continu du ballast de laFig. 2 selon un premier mode de fonctionnement ; - la
Fig. 5 représente schématiquement un convertisseur tension continu/continu du ballast de laFig. 2 selon un deuxième mode de fonctionnement ; - la
Fig. 6 représente une lampe à décharge reliée au ballast selon l'invention ; - la
Fig. 7 est un diagramme représentant l'évolution de la tension aux bornes de la lampe à décharge de laFig. 6 ; - la
Fig. 8 représente une partie du diagramme de laFig. 7 ; et - la
Fig. 9 est un schéma d'un deuxième mode de réalisation non limitatif d'un ballast selon l'invention.
- the
Fig. 1 schematically represents a vehicle fire device comprising a discharge lamp and a ballast according to the invention; - the
Fig. 2 is a diagram of a first non-limiting embodiment of a ballast according to the invention; - the
Fig. 3 is a first diagram of voltages provided by ballast components according to theFig. 2 ; - the
Fig. 4 schematically represents a DC / DC voltage converter of the ballast of theFig. 2 according to a first mode of operation; - the
Fig. 5 schematically represents a DC / DC voltage converter of the ballast of theFig. 2 in a second mode of operation; - the
Fig. 6 represents a discharge lamp connected to the ballast according to the invention; - the
Fig. 7 is a diagram showing the evolution of the voltage across the discharge lamp of theFig. 6 ; - the
Fig. 8 represents a part of the diagram of theFig. 7 ; and - the
Fig. 9 is a diagram of a second non-limiting embodiment of a ballast according to the invention.
A la
La lampe à décharge LA permet d'effectuer l'éclairage de jour et/ou de nuit.The LA discharge lamp can be used for day and / or night lighting.
Ainsi, un tel feu FX comporte principalement :
- une lampe à décharge LA enfermée dans un boîtier et disposée selon une configuration géométrique déterminée avec un réflecteur RL. La lampe à décharge est une lampe à arc, entre deux électrodes qui nécessite une impulsion de tension aux bornes de ses électrodes afin de créer un premier arc pour l'allumer. La lampe LA est, dans un exemple non limitatif, une lampe au xénon (avec Hg+ ou sans Hg- mercure) qui nécessite notamment une tension d'allumage Um de l'ordre de 25kV. Elle comprend une ampoule Bb et un module haute tension HV ;
- un ballast BLST relié au module haute tension HV de la lampe à décharge LA via un faisceau de fils, le ballast fournissant une tension Vdiff suffisante au module haute de tension HV de manière à ce que la lampe LA puisse s'allumer ; et
- un relais RS pour connecter le ballast BLST à une source d'alimentation Vbat.
- a discharge lamp LA encased in a housing and arranged in a geometric configuration determined with a reflector RL. The discharge lamp is an arc lamp between two electrodes that requires a voltage pulse across its electrodes to create a first arc to ignite it. The lamp LA is, in a non-limiting example, a xenon lamp (with Hg + or without Hg-mercury) which requires in particular an ignition voltage Um of the order of 25kV. It comprises a bulb Bb and a high voltage module HV;
- a BLST ballast connected to the HV high voltage module of the discharge lamp LA via a wire harness, the ballast supplying a sufficient voltage Vdiff to the high voltage module HV so that the lamp LA can light; and
- an RS relay for connecting the BLST ballast to a power source Vbat.
Un premier mode de réalisation du ballast BLST est représenté à la
- un convertisseur de tension continu/continu Ccc pour fournir à la lampe à décharge LA :
- une haute tension redressée continue Vout, et
- une tension d'amorçage Vignit, les deux tensions Vout et Vignit étant générées à partir d'une source d'alimentation Vbat, ladite source étant dans l'exemple pris la tension batterie du véhicule Vbat ;
- un convertisseur continu/alternatif Cca pour fournir à la lampe à décharge LA une haute tension alternative à partir de la tension redressée continue Vout fournie par le convertisseur continu/continu Ccc ; et
- une unité de commande UC pour piloter le convertisseur continu/continu Ccc et le convertisseur continu/alternatif Cca.
- a DC / DC voltage converter Ccc for supplying the discharge lamp LA with:
- a continuous high voltage rectified Vout, and
- a starter voltage Vignit, the two voltages Vout and Vignit being generated from a power source Vbat, said source being in the example taken the battery voltage of the vehicle Vbat;
- a DC / AC converter for supplying the discharge lamp LA with an alternating high voltage from the voltage continuous rectified Vout supplied by the DC / DC converter; and
- a control unit UC for controlling the DC / DC converter Ccc and the DC / AC converter Cca.
De façon non limitative, l'ensemble des éléments du ballast BLST est positionné sur une même carte électronique de type PCB («Printed Circuit Board»).Without limitation, all elements of the ballast BLST is positioned on the same PCB type PCB ("Printed Circuit Board").
Les éléments du ballast BLST sont décrits en détail ci-après.The elements of the BLST ballast are described in detail below.
Le convertisseur continu/continu Ccc permet d'adapter la source d'alimentation, ici la tension batterie Vbat à la tension lampe à décharge en générant la haute tension redressée continue Vout et la tension d'amorçage Vignit. Comme on le verra en détail plus loin, à partir de la différence de potentiel entre ces deux hautes tensions, le module haute tension HV de la lampe à décharge LA va pouvoir générer une première impulsion d'allumage Um, de l'ordre de 25kV, pour allumer ladite lampe LA.The DC / DC converter Ccc makes it possible to adapt the power source, in this case the battery voltage Vbat, to the discharge lamp voltage by generating the continuous high voltage rectified Vout and the ignition voltage Vignit. As will be seen in detail below, from the potential difference between these two high voltages, the HV high voltage module of the discharge lamp LA will be able to generate a first ignition pulse Um, of the order of 25kV to turn on said lamp LA.
Selon un premier mode de réalisation non limitatif à la
- un transformateur TR1 élévateur de tension;
- un organe de commutation GMOS ;
- un circuit redresseur RD ; et
- un circuit multiplieur MU.
- a step-up transformer TR1;
- a GMOS switching member;
- a rectifier circuit RD; and
- a MU multiplier circuit.
Dans un mode de réalisation non limitatif, le convertisseur continu/continu Ccc peut en outre comporter une résistance R1 montée en sortie du circuit multiplieur MU pour permettre de retarder le chargement d'un condensateur du module haute tension HV de la lampe à décharge LA comme on le verra en détail plus loin.In a non-limiting embodiment, the DC / DC converter Ccc may furthermore comprise a resistor R1 mounted at the output of the multiplier circuit MU to allow the charging of a capacitor of the high voltage module HV of the discharge lamp LA to be delayed as we will see in detail later.
Les différents composants du convertisseur Ccc sont décrits ci-après.The various components of the converter Ccc are described below.
Il comporte :
- un enroulement principal n1 relié en série à l'organe de commutation GMOS et à la source d'alimentation Vbat ;
- un enroulement secondaire n2 relié au circuit redresseur de tension RD ; et
- un enroulement auxiliaire n3 relié au circuit multiplieur MU et bobiné dans le prolongement de l'enroulement secondaire n2 (les deux enroulements n3 et n2 sont donc en série) ;
- a main winding n1 connected in series to the GMOS switching member and to the power source Vbat;
- a secondary winding n2 connected to the voltage rectifier circuit RD; and
- an auxiliary winding n3 connected to the multiplier circuit MU and wound in the extension of the secondary winding n2 (the two windings n3 and n2 are therefore in series);
Comme on va le voir en détail plus loin, le fait d'avoir l'enroulement secondaire n2 en série avec l'enroulement auxiliaire n3 va permettre de générer la tension d'amorçage Vignit en utilisant la somme des tensions générées par l'enroulement secondaire n2 et l'enroulement auxiliaire n3 dont fait partie la tension redressée continue Vout. On réduit ainsi le nombre de spires dans l'enroulement auxiliaire n3 en particulier.As will be seen in detail below, having the secondary winding n2 in series with the auxiliary winding n3 will be able to generate the Vignit ignition voltage using the sum of the voltages generated by the secondary winding. n2 and the auxiliary winding n3 which includes the DC rectified voltage Vout. This reduces the number of turns in the auxiliary winding n3 in particular.
Les relations qui existent entre la tension principale Vn1 aux bornes de l'enroulement principal n1, la tension secondaire Vn2 aux bornes de l'enroulement secondaire n2 et la tension auxiliaire Vn3 aux bornes de l'enroulement auxiliaire n3 sont les suivantes :
que ce soit lors d'une magnétisation du transformateur (lorsqu'un courant circule dans le transformateur), ou lors d'une démagnétisation, avec n2/n1, n3/n1 et n3/2 les rapports de transformations entre ces différents enroulements.The relationships that exist between the main voltage Vn1 across the main winding n1, the secondary voltage Vn2 across the secondary winding n2 and the auxiliary voltage Vn3 across the auxiliary winding n3 are as follows:
either during a magnetization of the transformer (when a current flows in the transformer), or during a demagnetization, with n2 / n1, n3 / n1 and n3 / 2 the transformation ratios between these different windings.
Dans un mode de réalisation non limitatif, l'enroulement secondaire n2 est défini de manière à ce que le rapport de transformation n2/n1 entre cet enroulement n2 et l'enroulement principal n1 soit égal à 5.In a non-limiting embodiment, the secondary winding n2 is defined in such a way that the transformation ratio n2 / n1 between this winding n2 and the main winding n1 is equal to 5.
Dans un mode de réalisation non limitatif, l'enroulement auxiliaire n3 est défini de manière à ce que le rapport de transformation n3/n1 entre cet enroulement n3 et l'enroulement principal n1 soit égal à 2.In a non-limiting embodiment, the auxiliary winding n3 is defined in such a way that the transformation ratio n3 / n1 between this winding n3 and the main winding n1 is equal to 2.
Dans un exemple non limitatif, le nombre de spires dans l'enroulement principal n1 est égal à 4, le nombre de spires dans l'enroulement secondaire n2 est égal à 20, et enfin le nombre de spires dans l'enroulement auxiliaire n3 est égal à 8.In a nonlimiting example, the number of turns in the main winding n1 is equal to 4, the number of turns in the secondary winding n2 is equal to 20, and finally the number of turns in the auxiliary winding n3 is equal at 8.
On obtient :
et :
and
Comme on le verra par la suite, ces rapports de transformation faibles ainsi que le nombre de spires associé sont suffisants pour permettre de générer une tension d'amorçage Vignit nécessaire à l'allumage de la lampe à décharge LA.As will be seen later, these low transformation ratios and the associated number of turns are sufficient to generate a Vignit ignition voltage necessary for the ignition of the discharge lamp LA.
Bien entendu, un autre nombre de spires peut être utilisé ainsi que d'autres rapports de transformation permettant d'obtenir la tension d'amorçage Vignit et la tension redressée Vout suffisantes permettre pour l'allumage de la lampe LA.Of course, another number of turns can be used as well as other transformation ratios to obtain the Vignit ignition voltage and the sufficient rectified voltage Vout allow for the ignition of the lamp LA.
II est piloté par des impulsions de découpage et son ouverture-fermeture répétitive permet d'induire la tension secondaire induite Vn2 aux bornes de l'enroulement secondaire n2 et la tension auxiliaire induite Vn3 aux bornes de l'enroulement auxiliaire n3. Dans un mode de réalisation non limitatif, l'organe de commutation est un transistor MOSFET.It is driven by switching pulses and its repetitive opening-closing makes it possible to induce the induced secondary voltage Vn2 across the secondary winding n2 and the induced auxiliary voltage Vn3 across the auxiliary winding n3. In a non-limiting embodiment, the switching member is a MOSFET transistor.
II permet de fournir la tension redressée continue Vout à partir de la tension secondaire induite Vn2, le circuit RD comprenant à cet effet une diode de redressement Dout et un condensateur de filtrage Cout. Dans un mode de réalisation non limitatif, la diode de redressement Dout est reliée au noeud P1 entre les enroulements secondaire n2 et auxiliaire n3 par sa cathode comme illustré à la
II permet de fournir la tension d'amorçage Vignit. Dans un mode de réalisation non limitatif, le multiplieur MU est composé de deux diodes D1, D2 et de deux condensateurs C1, C2. Les condensateurs C1 et C2 permettent de fournir la tension d'amorçage Vignit, tandis que les diodes D1 et D2, lors de la phase d'allumage, permettent d'une part de charger les condensateurs C1 et C2 associés et d'autre part leur évitent de se décharger dans un sens comme on va le voir plus loin.It makes it possible to supply the Vignit ignition voltage. In a non-limiting embodiment, the multiplier MU is composed of two diodes D1, D2 and two capacitors C1, C2. The capacitors C1 and C2 provide the ignition voltage Vignit, while the diodes D1 and D2, during the ignition phase, on the one hand to charge the capacitors C1 and C2 associated and on the other hand their avoid being discharged in a sense as we will see later.
Selon un deuxième mode de réalisation illustré à la
Ce convertisseur permet de rendre la haute tension redressée Vout alternative nécessaire au fonctionnement de la lampe à décharge LA en régime permanent, c'est-à-dire lors du fonctionnement normal de la lampe, à partir de la tension redressée continue Vout fournie par le convertisseur continu/continu Ccc.This converter makes it possible to make the rectified high voltage Vout alternative necessary for the operation of the steady-state discharge lamp LA, that is to say during normal operation of the lamp, from the continuous rectified voltage Vout supplied by the DC / DC converter.
De manière connue de l'homme du métier, le convertisseur continu/alternatif Cca comporte quatre transistors (non représentés) montés en pont complet, l'ouverture ou la fermeture simultanée d'une paire de transistors étant commandée en alternance avec celle de l'autre paire pour rendre la tension redressée Vout alternative. Dans un mode de réalisation non limitatif, ces transistors sont des transistors NPN de type IGBT « Insulated Gate Bipolar Transistor », bien adaptés aux hautes tensions mises en jeu, tant pendant la phase d'allumage que pendant le régime permanent de la lampe LA.In a manner known to those skilled in the art, the DC / AC converter Cca comprises four transistors (not shown) mounted in complete bridge, the simultaneous opening or closing of a pair of transistors being controlled alternately with that of the another pair to make the voltage rectified. In a non-limiting embodiment, these transistors are NPN transistors of the IGBT type "Insulated Gate Bipolar Transistor", well adapted to the high voltages involved, both during the ignition phase and during the steady state of the lamp LA.
De manière connue de l'homme du métier, l'unité de commande UC permet de contrôler, au moyen de signaux de commande en réponse à des consignes de pilotage extérieures, la largeur des impulsions de découpage du convertisseur continu/continu Ccc, ainsi que le fonctionnement du pont complet du convertisseur continu/alternatif Cca que ce soit en phase d'allumage ou en régime permanent.In a manner known to those skilled in the art, the control unit UC makes it possible to control, by means of control signals in response to external control commands, the width of the switching pulses of the DC / DC converter Ccc, as well as the operation of the complete bridge of the AC / DC converter whether in the ignition phase or in steady state.
En effet, comme on va le voir par la suite, le ballast BLST fournit la tension nécessaire pour allumer la lampe lors d'une phase d'allumage, mais également fournit la tension nécessaire pour faire fonctionner la lampe lorsqu'elle est allumée.Indeed, as we will see later, the BLST ballast provides the voltage necessary to turn on the lamp during an ignition phase, but also provides the voltage required to operate the lamp when it is on.
Ainsi, le ballast BLST fonctionne de la manière suivante.Thus, the BLST ballast operates in the following manner.
Le fonctionnement est décrit pour le premier mode de réalisation illustré à la
On prend comme exemple une tension d'alimentation Vbat égale à 10V. En général, cette tension batterie Vbat varie entre 8V (par exemple lors d'un démarrage) et 12V avec des pics possibles à 19V (norme donnée par le constructeur).As an example, a supply voltage Vbat equal to 10 V is used. In general, this battery voltage Vbat varies between 8V (for example during a start) and 12V with possible peaks at 19V (norm given by the manufacturer).
Lors de la phase d'allumage, le ballast BLST va fournir d'une part la tension redressée continue Vout et d'autre part la tension d'amorçage Vignit, la différence de potentiel entre ces deux tensions, permettant d'alimenter le module haute tension HV de la lampe LA pour allumer ladite lampe.During the ignition phase, the ballast BLST will provide on the one hand the continuous rectified voltage Vout and on the other hand the ignition voltage Vignit, the potential difference between these two voltages, to feed the high module HV lamp voltage LA to turn on said lamp.
Ces deux tensions sont fournies à partir d'un chargement de condensateurs respectifs, chaque chargement s'effectuant de manière alternative grâce à l'organe de commutation GMOS.These two voltages are provided from a loading of respective capacitors, each load being effected alternately thanks to the switching member GMOS.
Ainsi, comme on va le voir ci-après, lorsque l'organe de commutation GMOS est fermé, il permet un chargement du deuxième condensateur C2 du circuit multiplieur MU permettant de fournir la tension d'amorçage Vignit, tandis que lorsqu'il est ouvert, il permet de charger le condensateur de filtrage Cout permettant de fournir la tension redressée continue Vout, et de charger le premier condensateur C1 du circuit multiplieur MU permettant de fournir également la tension d'amorçage Vignit.Thus, as will be seen below, when the switching member GMOS is closed, it allows a loading of the second capacitor C2 of the multiplier circuit MU for supplying the ignition voltage Vignit, while when it is open , it allows to charging the filter capacitor Cout for providing the DC rectified voltage Vout, and charging the first capacitor C1 MU multiplier circuit to also provide the Vignit boot voltage.
On rappelle que le chargement d'un condensateur est progressif. En conséquence, l'organe de commutation GMOS, qui est piloté par des impulsions de découpage, permet grâce à son ouverture et fermeture répétitive de charger progressivement les trois condensateurs de manière alternative.It is recalled that the charging of a capacitor is progressive. Consequently, the switching member GMOS, which is controlled by cutting pulses, allows through its opening and closing repetitive gradually load the three capacitors alternately.
Dans un exemple non limitatif, la fréquence de commutation de l'organe de commutation GMOS est de 100kHz lors de cette phase d'allumage.In a non-limiting example, the switching frequency of the GMOS switching element is 100 kHz during this ignition phase.
On rappelle que le transistor MOSFET qui compose l'organe de commutation GMOS comporte une tension grille Vgs et une tension drain-source Vds qui varient en fonction de l'ouverture-fermeture du transistor MOSFET entraînant également une variation des tensions principale Vn1, secondaire induite Vn2 et auxiliaire induite Vn3 du transformateur TR1. L'évolution de ces tensions Vn1, Vn2, Vn3 associées aux transformateurs TR1 permet de charger les condensateurs C1, C2, Cout fournissant la tension redressée continue Vout et la tension d'amorçage Vignit.It will be recalled that the MOSFET transistor that composes the switching member GMOS comprises a gate voltage Vgs and a drain-source voltage Vds that vary as a function of the opening-closing of the MOSFET transistor also causing a variation of the main voltages Vn1, secondary induced. Vn2 and induced auxiliary Vn3 of transformer TR1. The evolution of these voltages Vn1, Vn2, Vn3 associated with the transformers TR1 makes it possible to charge the capacitors C1, C2, Cout supplying the continuous rectified voltage Vout and the ignition voltage Vignit.
La variation des tensions du transformateur TR1 en fonction des deux états (fermé-ouvert) du transistor MOSFET est décrite ci-après lorsque les condensateurs C1, C2, Cout sont complètement chargés.The variation of the transformer voltages TR1 as a function of the two states (closed-open) of the MOSFET transistor is described below when the capacitors C1, C2, Cout are fully charged.
Comme on peut le voir à la
L'enroulement principal n1 est relié directement à la source d'alimentation Vbat. La tension principale Vn1 est donc égale à la tension batterie Vbat, soit est égale à 10V dans l'exemple pris.The main winding n1 is connected directly to the power source Vbat. The main voltage Vn1 is equal to the battery voltage Vbat, ie is equal to 10V in the example taken.
Un courant principal Ip est alors généré et traverse l'enroulement principal n1 du transformateur TR1. Il en résulte une création d'un flux magnétique dans le transformateur TR1 créant un courant secondaire induit In2 et un courant auxiliaire induit In3, ces derniers induisant respectivement une tension secondaire induite Vn2 aux bornes de l'enroulement secondaire n2 et une tension auxiliaire induite Vn3 aux bornes de l'enroulement auxiliaire n3 tels qu'illustrés à la
Étant donné les rapports de transformation respectivement égaux à 5 et 2, la tension secondaire induite Vn2 est égale à 50 et la tension auxiliaire induite Vn3 est égale à 20 telles qu'illustrées à la
Étant donné le sens des courants induits ln2 et ln3 (sens illustré en pointillés sur la
Par contre la deuxième diode D2 du circuit multiplieur MU est passante (on a environ 0V à ses bornes).On the other hand, the second diode D2 of the multiplying circuit MU is conducting (there is approximately 0V at its terminals).
La deuxième diode D2 étant passante, le deuxième condensateur C2 du circuit multiplieur MU est chargé via cette deuxième diode D2. La première diode D1 étant bloquée, le premier condensateur C1 du circuit multiplieur MU se décharge via la deuxième diode D2 vers le deuxième condensateur C2.As the second diode D2 is conducting, the second capacitor C2 of the multiplier circuit MU is loaded via this second diode D2. The first diode D1 being blocked, the first capacitor C1 of the multiplier circuit MU discharges via the second diode D2 to the second capacitor C2.
Le deuxième condensateur C2 est donc chargé avec les tensions secondaires induites Vn2, auxiliaire induite Vn3 et la tension Vc1 du premier condensateur C1.The second capacitor C2 is thus charged with the induced secondary voltages Vn2, induced auxiliary Vn3 and the voltage Vc1 of the first capacitor C1.
La tension Vc2 aux bornes de le deuxième condensateur C2 du circuit multiplieur MU est donc égale à :
avec la tension Vc1 = +560V = -Vout - Vn3 provenant de l'étape où le transistor MOSFET est ouvert comme décrit plus loin.The voltage Vc2 across the second capacitor C2 of the multiplier circuit MU is therefore equal to:
with the voltage Vc1 = + 560V = -Vout - Vn3 from the step where the MOSFET transistor is open as described below.
Étant donné que la tension Vc2 est égale à la tension d'amorçage Vignit, on obtient Vignit = +630V.Since the voltage Vc2 is equal to the ignition voltage Vignit, we obtain Vignit = + 630V.
Ainsi, la tension d'amorçage Vignit est bien fournie par le chargement du deuxième condensateur C2 du circuit multiplieur MU et est bien générée à partir de la tension redressée Vout.Thus, the ignition voltage Vignit is well supplied by the charging of the second capacitor C2 of the multiplier circuit MU and is well generated from the rectified voltage Vout.
On notera que le rapport de transformation de n3/n1 = 2 permet d'obtenir une tension d'amorçage Vignit supérieure à 600V dans les pire cas d'allumage (Vout_min = 400V et Vbat_min = 8V).It will be noted that the transformation ratio of n3 / n1 = 2 makes it possible to obtain a Vignit ignition voltage greater than 600V in the worst case of ignition (Vout_min = 400V and Vbat_min = 8V).
En effet, dans ce cas, la tension d'amorçage Vignit est égale à :
- Vignit min
- = Vc1 + Vn2_on +Vn3_on
- = Vn2_off+Vn3_off+Vn2_on +Vn3_on
- = Vout_min +n3/n2*Vout_min +n2/n1*Vbat_min+n3/n1*Vbat_min
- = Vout_min *(n3+n2)/n2 + Vbat min * (n3+n2)/n1
- = 400*7/5+8*7 = 616V.
- Vignit min
- = Vc1 + Vn2_on + Vn3_on
- = Vn2_off + Vn3_off + Vn2_on + Vn3_on
- = Vout_min + n3 / n2 * Vout_min + n2 / n1 * Vbat_min + n3 / n1 * Vbat_min
- = Vout_min * (n3 + n2) / n2 + Vbat min * (n3 + n2) / n1
- = 400 * 7/5 + 8 * 7 = 616V.
Avec Vn3_off/Vn2_off = n3/n2 et Vn1 = Vbat, et Vn2_off, Vn3_off les tensions aux bornes des enroulements n2 et n3 respectif lorsque le transistor MOSFET est ouvert, et Vn2_on, Vn3_on les tensions lorsque le transistor MOSFET est fermé.With Vn3_off / Vn2_off = n3 / n2 and Vn1 = Vbat, and Vn2_off, Vn3_off the voltages across respective windings n2 and n3 when the MOSFET is open, and Vn2_on, Vn3_on the voltages when the MOSFET is closed.
Comme on peut le voir à la
La tension grille Vgs est nulle, le transistor MOSFET se comporte comme une diode passante de la source vers le drain.The gate voltage Vgs is zero, the MOSFET transistor behaves like a diode passing from the source to the drain.
La tension drain-source Vds est donc positive telle qu'illustré à la
La conservation du flux magnétique dans le transformateur TR1 provoque l'apparition des courants secondaire ln2 et auxiliaire ln3 respectivement dans l'enroulement secondaire n2 et l'enroulement auxiliaire n3 tels qu'illustrés à la
Étant donné le sens des courants induits In2 et In3 (sens illustré en pointillés sur la
La diode de redressement Dout étant passante (on a environ 0V à ses bornes), le condensateur de filtrage Cout est chargée par ladite diode Dout.The Dout rectifying diode being conducting (one has about 0V at its terminals), the filtering capacitor Cout is charged by said diode Dout.
L'organe de commutation GMOS est piloté de manière à ce que la charge du condensateur de filtrage Cout soit égale à -400V. A cet effet, il existe un dispositif de régulation (non représenté) qui mesure la charge du condensateur de filtrage Cout.The GMOS switching element is controlled in such a way that the charge of the filter capacitor Cout is equal to -400V. For this purpose, there is a control device (not shown) which measures the charge of the filter capacitor Cout.
Par conséquent Vout = -400V à la fin du chargement du condensateur Cout. Comme dans ce cas, la tension secondaire induite Vn2 est égale à la tension redressée Vout, Vn2 = -400V telle qu'illustrée à la
Étant donné le rapport de transformation n2/n1=5, la tension principale Vn1 = -400/5 = -80V.Given the transformation ratio n2 / n1 = 5, the main voltage Vn1 = -400/5 = -80V.
Étant donné le rapport de transformation n3/n1 = 2, la tension auxiliaire induite Vn3 =-80*2 = -160V.Given the transformation ratio n3 / n1 = 2, the induced auxiliary voltage Vn3 = -80 * 2 = -160V.
Par ailleurs, La première diode D1 étant passante (on a environ 0V à ses bornes), le premier condensateur C1 du circuit multiplieur MU se charge au travers de cette diode D1.Moreover, the first diode D1 being conducting (one has about 0V at its terminals), the first capacitor C1 of the multiplier circuit MU is charged through this diode D1.
Le premier condensateur C1 est donc chargé avec les tensions secondaire induite Vn2 et auxiliaire induite Vn3.The first capacitor C1 is thus charged with the induced secondary voltages Vn2 and induced auxiliary Vn3.
On obtient donc
On notera que le deuxième condensateur C2 du circuit multiplieur MU ne peut à ce moment se décharger en direction du premier condensateur C1 car la deuxième diode D2 est bloquée. Par contre, le deuxième condensateur C2 se décharge dans le circuit (condensateur C3) de la lampe LA comme on le verra plus loin.It will be noted that the second capacitor C2 of the multiplier circuit MU can not at this time be discharged towards the first capacitor C1 because the second diode D2 is blocked. On the other hand, the second capacitor C2 discharges into the circuit (capacitor C3) of the lamp LA as will be seen below.
On notera que le temps de charge du deuxième condensateur C2 se situe aux environs des dizaines de microsecondes (1/100kHz) tandis que le temps de décharge se situe aux alentours de quelques millisecondes (grâce à une résistance R1 comme on le verra plus loin).Note that the charging time of the second capacitor C2 is around tens of microseconds (1 / 100kHz) while the discharge time is around a few milliseconds (thanks to a resistance R1 as discussed below) .
Ainsi, lorsque le transistor de commutation MOSFET est fermé, le condensateur C2 se charge procurant ainsi la tension d'amorçage Vignit à partir de la tension redressée Vout, tandis que lorsque le transistor MOSFET est ouvert, le condensateur de filtrage Cout se charge procurant ainsi la tension redressée Vout.Thus, when the MOSFET switching transistor is closed, the capacitor C2 becomes charged thereby providing the Vignit ignition voltage from the rectified voltage Vout, while when the MOSFET transistor is open, the filter capacitor Cout is charged thereby providing the rectified voltage Vout.
On notera que les diodes D1 et D2 du circuit multiplieur MU doivent être dimensionnées pour tenir une tension de l'ordre de 800V. En effet, la tension maximale inverse Vrmax des diodes est égale à :
En effet, Vrmax est égal à Vignit. En effet, lorsque le premier condensateur C1 se charge, la première diode D1 est passante (donc la tension à ses bornes est de 0V), donc la tension de la deuxième diode D2 correspond à Vignit. De même, lorsque le deuxième condensateur C2 se charge, la deuxième diode D1 est passante (donc la tension à ses bornes est de 0V), donc la tension de la première diode D1 correspond à Vignit.Indeed, Vrmax is equal to Vignit. Indeed, when the first capacitor C1 is charged, the first diode D1 is conducting (therefore the voltage at its terminals is 0V), so the voltage of the second diode D2 corresponds to Vignit. Similarly, when the second capacitor C2 is charged, the second diode D1 is conducting (therefore the voltage at its terminals is 0V), so the voltage of the first diode D1 corresponds to Vignit.
Ainsi, on obtient bien une tension redressée Vout de -400V et une tension d'amorçage Vignit de +630V, la différence de potentiel Vdiff=Vignit-Vout étant égale à 1030V. Cette différence de potentiel Vdiff permet de fournir la très haute tension d'allumage Um de 25kV nécessaire à l'allumage de la lampe à décharge LA de la manière suivante.Thus, a rectified voltage Vout of -400V and a Vignit ignition voltage of + 630V are obtained, the potential difference Vdiff = Vignit-Vout being equal to 1030V. This potential difference Vdiff makes it possible to provide the very high ignition voltage Um of 25kV necessary for lighting the discharge lamp LA in the following manner.
La différence de tension Vdiff est appliquée au module haute tension HV comme indiqué à la
Ce module HV comprend :
- un condensateur C3,
- un transformateur TR2 comprenant un enroulement primaire et un enroulement secondaire et apte à fournir une tension très élevée Um, de l'ordre de 25kV, à partir de la différence de tension Vdiff fournie par le convertisseur continu/continu Ccc,
- un éclateur à gaz Gz connecté en série avec l'enroulement primaire du transformateur TR2, et
- l'ampoule Bb de la lampe à décharge LA.
- a capacitor C3,
- a transformer TR2 comprising a primary winding and a secondary winding and able to provide a very high voltage Um, of the order of 25kV, from the voltage difference Vdiff supplied by the DC / DC converter Ccc,
- a gas spark gap Gz connected in series with the primary winding of the transformer TR2, and
- the Bb bulb of the LA discharge lamp.
Lorsque la lampe LA est éteinte, l'éclateur à gaz Gz se comporte comme un interrupteur ouvert. Lorsque la différence de tension Vdiff est appliquée en entrée du module haute tension HV, le condensateur C3 se charge. Lorsqu'il atteint un seuil prédéterminé de chargement, de l'ordre de 800V dans un exemple non limitatif, l'éclateur Gz devient brusquement conducteur et crée une impulsion de courant dans l'enroulement primaire du transformateur TR2 qui produit au secondaire la très haute tension Um de 25kV, créant ainsi un premier arc électrique nécessaire à l'allumage de la lampe LA. Au même moment, lorsque l'éclateur à gaz devient passant, le condensateur C3 se décharge très vite dans le transformateur TR2.When the LA lamp is off, the gas spark gap Gz behaves like an open switch. When the voltage difference Vdiff is applied to the input of the high voltage module HV, the capacitor C3 is charged. When it reaches a predetermined threshold of charging, of the order of 800V in a non-limiting example, the spark gap Gz becomes abruptly conductive and creates a current pulse in the primary winding of the transformer TR2 which produces in the secondary the very high Um voltage of 25kV, thus creating a first electric arc necessary for lighting the lamp LA. At the same time, when the gas spark gap becomes on, the capacitor C3 discharges very quickly in the transformer TR2.
Ainsi, la lampe à décharge LA s'allume.Thus, the discharge lamp LA turns on.
Lorsque la lampe est allumée, afin de fonctionner correctement, une tension alternative est appliquée à ses bornes. Cette tension est de l'ordre de -85V en régime permanent pour une lampe à xénon avec mercure (Hg+) et de l'ordre de -42V pour une lampe à xénon sans mercure (Hg-).When the lamp is on, in order to function properly, an AC voltage is applied to its terminals. This voltage is of the order of -85V steady state for a xenon lamp with mercury (Hg + ) and of the order of -42V for a mercury-free xenon lamp (Hg - ).
Comme décrit précédemment, l'unité de commande UC agit pour activer et désactiver les transistors du convertisseur continu/alternatif Cca afin que ce dernier fournisse cette tension alternative à partir de la tension redressée Vout nécessaire pour continuer à faire fonctionner la lampe LA. Cette tension alternative est obtenue à partir de la tension redressée continue Vout fournie par le convertisseur continu/continu Ccc.As previously described, the control unit UC acts to activate and deactivate the transistors of the DC / AC converter so that it supplies this AC voltage from the rectified voltage Vout necessary to continue operating the lamp LA. This AC voltage is obtained from the DC rectified voltage Vout supplied by the DC / DC converter Ccc.
On rappelle que le convertisseur continu/continu Ccc permet de fournir la puissance nécessaire pour que la tension redressée Vout soit dans ce cas égale à -85V. Dans un exemple non limitatif, la fréquence de commutation de l'organe de commutation GMOS est de 300kHz en régime permanent.It is recalled that the DC / DC converter Ccc provides the power necessary for the rectified voltage Vout is in this case equal to -85V. In a non-limiting example, the frequency switching speed of the GMOS switching element is 300kHz in steady state.
Ainsi, on notera qu'en phase d'allumage, le transistor de commutation MOSFET reste ouvert plus longtemps qu'en régime permanent.Thus, it will be noted that in the ignition phase, the MOSFET switching transistor remains open longer than steady state.
La
On notera que l'échelle des intervalles t0-t1 , t1-t2, t2-t3, t3-t4 se situe aux alentours des millisecondes, tandis que l'échelle de l'intervalle t4-t5 et la suite se situe aux alentours des secondes.It should be noted that the scale of the intervals t0-t1, t1-t2, t2-t3, t3-t4 is around milliseconds, while the scale of the interval t4-t5 and the sequence lies around seconds.
L'intervalle t0-t1 représente la phase d'allumage, tandis que l'intervalle t3-t4 représente la phase de fonctionnement en régime permanent.The interval t0-t1 represents the ignition phase, while the interval t3-t4 represents the steady-state operating phase.
Les intervalles t1-t2 et t2-t3 représentent des phases de transition.The intervals t1-t2 and t2-t3 represent transition phases.
Au temps t0 = 0, tous les condensateurs Cout, C1, et C2 sont à 0. La tension d'amorçage Vignit et la tension redressée Vout sont à 0.At time t0 = 0, all the capacitors Cout, C1, and C2 are at 0. The ignition voltage Vignit and the rectified voltage Vout are at 0.
Dans l'intervalle t0-t1, les condensateurs Cout, C1 et C2 se chargent. La tension d'amorçage Vignit et la tension redressée Vout augmentent.In the interval t0-t1, the capacitors Cout, C1 and C2 are charged. The Vignit ignition voltage and the rectified voltage Vout increase.
Au temps t1, elles atteignent respectivement 630V et -400V, la différence étant de 1030V. La tension Ula de la lampe LA est égale à la différence de tension Vignit - Vout.At time t1, they reach respectively 630V and -400V, the difference being 1030V. The voltage Ula of the lamp LA is equal to the voltage difference Vignit - Vout.
On a atteint la fin de la phase d'allumage.We have reached the end of the ignition phase.
Entre t1 et t2, la tension redressée Vout commence à diminuer (le condensateur Cout du circuit redresseur se décharge) tandis que la tension d'amorçage Vignit chute jusqu'à -400V car le condensateur C3 se décharge brutalement, sa tension Vc3 devient nulle, la tension redressée Vout demeurant à -400V.Between t1 and t2, the rectified voltage Vout begins to decrease (the capacitor Cout of the rectifier circuit discharges) while the ignition voltage Vignit drops to -400V because the capacitor C3 discharges suddenly, its voltage Vc3 becomes zero, the rectified voltage Vout remaining at -400V.
A partir du temps t3, la tension redressée continue Vout est rendue alternative au moyen du convertisseur continu/alternatif Cca. La tension Ula de la lampe LA est égale à la tension redressée alternative Vout.From time t3, the rectified voltage continues Vout is made alternative by means of the DC / AC converter Cca. The voltage Ula of the lamp LA is equal to the rectified voltage Vout.
Au temps t3, on assiste ainsi à une première commutation des transistors de commutation du convertisseur continu/alternatif Cca. Puis à partir du temps t4, le régime permanent de la lampe à décharge LA s'installe aux alentours de -85V.At time t3, there is thus a first switching of the switching transistors of the DC / AC converter Cca. Then from time t4, the steady state of the discharge lamp LA is installed around -85V.
On notera qu'entre le temps t3 et le temps t4, il existe un temps d'attente entre la première commutation du pont complet du convertisseur continu/alternatif Cca et une seconde commutation, de l'ordre de quelques dizaines de millisecondes, afin d'éviter à la lampe à décharge de s'éteindre. En effet, l'arc électrique créé doit être maintenu suffisamment longtemps pour chauffer la première électrode de la lampe LA avant d'inverser le sens de l'arc (c'est-à-dire avant d'inverser le courant dans la lampe qui en conséquence passera par zéro), pour chauffer la deuxième électrode de la lampe LA.It will be noted that between the time t3 and the time t4, there is a waiting time between the first switching of the complete bridge of the DC / AC converter Cca and a second switching, of the order of a few tens of milliseconds, in order to prevent the discharge lamp from extinguishing. Indeed, the created electric arc must be maintained long enough to heat the first electrode of the lamp LA before reversing the direction of the arc (that is to say before reversing the current in the lamp which as a result will go through zero), to heat the second electrode of the lamp LA.
L'évolution des deux tensions d'amorçage Vignit et redressée Vout est illustrée de façon plus précise à la
Les deux courbes Cvignit et Cvout représentatives respectivement des deux tensions Vignit et Vout illustrent le chargement progressif des condensateurs C2 et Cout correspondant. Comme on peut le voir, la pente de la courbe Cvignit représentative de la tension d'amorçage Vignit est plus grande que celle de la courbe Cvout représentative de la tension redressée Vout car le condensateur Cout de filtrage est dimensionné de manière à être plus important que le deuxième condensateur C2. En effet, le condensateur Cout génère la puissance la plus importante à la lampe LA et correspond à une réserve d'énergie. En effet, en régime permanent, il est le seul à fournir l'énergie à la lampe LA.The two curves Cvignit and Cvout representative respectively of the two voltages Vignit and Vout illustrate the progressive loading of capacitors C2 and Cout corresponding. As can be seen, the slope of the curve Cvignit representative of the ignition voltage Vignit is greater than that of the curve Cvout representative of the rectified voltage Vout because the filter capacitor Cout is dimensioned so as to be larger than the second capacitor C2. Indeed, the capacitor Cout generates the greatest power to the lamp LA and corresponds to a reserve of energy. Indeed, in steady state, it is the only one to supply energy to the lamp LA.
En raison de cette différence de pente, la tension d'amorçage Vignit peut atteindre au temps t1 sa valeur maximale +630V avant que la tension redressée n'atteigne la sienne -400V. Cela pourrait engendrer une différence de tension au temps t1 inférieure à 1030V, soit par exemple aux environ de 800V, la tension redressée Vout n'ayant atteint que 200V par exemple. Cette différence de tension Vdiff peut engendrer un allumage de la lampe LA.Because of this difference in slope, the Vignit ignition voltage can reach its maximum value + 630V at time t1 before the rectified voltage reaches its -400V. This could generate a voltage difference at time t1 less than 1030V, for example at about 800V, the rectified voltage Vout reaching only 200V for example. This voltage difference Vdiff can cause ignition of the lamp LA.
Cependant étant donné que le seuil de conduction de l'éclateur à gaz Gz est de l'ordre de 800V, la différence de tension Vdiff se trouve à la limite du seuil de l'éclateur à gaz; aussi la lampe LA peut mal s'allumer.However, since the conduction threshold of the gas spark gap Gz is of the order of 800V, the voltage difference Vdiff is at the threshold limit of the gas spark gap; also the LA lamp may not light properly.
Afin de remédier à cet inconvénient, la résistance R1 du ballast BLST permet de retarder le chargement du condensateur C3 de la lampe LA avec la tension d'amorçage Vignit comme illustré par la courbe CRvignit. Ainsi, les deux tension Vignit et Vout atteindront leur valeur maximale au même moment de manière à fournir une différence de potentiel suffisante pour dépasser le seuil de chargement de l'éclateur à gaz permettant ainsi un allumage fiable de la lampe LA. Ainsi, la résistance R1 permet d'attendre que la tension redressée Vout soit stabilisée à -400V pour permettre d'obtenir une différence de tension Vdiff supérieure au seuil de conduction de l'éclateur à gaz Gz de sorte à obtenir un arc de tension suffisant (25kV) nécessaire à un allumage fiable de la lampe LA.In order to remedy this drawback, the resistor R1 of the BLST ballast makes it possible to delay the charging of the capacitor C3 of the lamp LA with the ignition voltage Vignit as illustrated by the curve CRvignit. Thus, the two voltage Vignit and Vout will reach their maximum value at the same time so as to provide a potential difference sufficient to exceed the loading threshold of the gas spark gap thus allowing a reliable ignition of the lamp LA. Thus, the resistor R1 makes it possible to wait for the rectified voltage Vout to be stabilized at -400V in order to make it possible to obtain a voltage difference Vdiff greater than the conduction threshold of the gas spark gap Gz so as to obtain an arc of sufficient voltage. (25kV) required for reliable ignition of the LA lamp.
Par ailleurs, cette résistance R1 permet d'éviter des pics de courant dans la deuxième diode D2 et évite ainsi à cette dernière de s'abîmer.Moreover, this resistor R1 prevents current peaks in the second diode D2 and thus prevents the latter from being damaged.
On notera que dans la description, l'application feu de véhicule a été pris en exemple, mais bien entendu, le ballast décrit peut être utilisé dans d'autres applications telles que, dans des exemples non limitatifs, éclairage intérieur bâtiment («Interior Lighting») ou éclairage voirie («General Lighting»).Note that in the description, the vehicle fire application was taken as an example, but of course, the described ballast can be used in other applications such as, in non-limiting examples, interior lighting building ("Interior Lighting ") Or street lighting (" General Lighting ").
En conclusion, l'invention présente les avantages suivants.
- Elle permet d'avoir des rapports de transformation (5 et 2) réduits ce qui réduit les éléments de fuite dues aux capacités et self parasites des spires d'un enroulement; il y a donc moins de risque de surtension sur le transistor de l'organe de commutation GMOS et donc moins de problème CEM (compatibilité électromagnétique).
- Du fait du faible rapport de transformation n3/n1, elle permet d'avoir des diodes D1, D2 dimensionnées pour des tensions de l'ordre de 700 à 800V maximum (pour tenir la tension d'amorçage de 630V) au lieu de 1000V pour la solution de l'état de la technique antérieur, ce qui permet d'utiliser des composants plus standard et donc de réduire le coût des composants.
- Elle permet d'obtenir des enroulements plus petits dans le transformateur TR1 et donc une longueur de fil plus petite; par conséquent le volume global du transformateur est réduit. Le fait d'avoir une longueur de fil réduite, permet de diminuer les pertes cuivres.
- Il existe moins de contrainte au niveau de l'isolement effectué entre l'enroulement secondaire et l'enroulement auxiliaire afin que ces derniers ne se touchent pas. En effet, un tel isolement doit pouvoir tenir 560V (-Vn2-Vn3 comme décrit précédemment) au lieu de 1000V dans l'état de la technique antérieur.
- Elle permet d'obtenir, grâce à la résistance R1, un allumage fiable de la lampe à décharge grâce à une différence de potentiel suffisante pour rendre passant l'éclateur à gaz.
- Le fait d'avoir réduit le volume du transformateur TR1 permet d'avoir une surface sur la carte électronique PCB réduite, et par conséquent une augmentation de la fiabilité, une réduction des coûts de test, un temps de process amélioré, et enfin un coût report sur PCB meilleur.
- La durée de vie du transformateur TR1 est augmentée puisque la tension maximum générée dans ledit transformateur est de 630V contre 1000V pour la solution de l'état de la technique antérieur. Par conséquent, le stress vu par les enroulements est réduit, c'est-à-dire que l'on obtient une meilleure tenue au claquage. Le transformateur est donc plus fiable.
- Enfin, elle permet de réduire le nombre de composants nécessaire à la fonction d'allumage uniquement, grâce au circuit multiplieur. Deux diodes D1, D2 et deux condensateurs C1, C2 suffisent pour générer la tension d'amorçage Vignit à partir des enroulements secondaire n2 et auxiliaire n3.
- It allows to have transformation ratios (5 and 2) reduced which reduces the leakage elements due to the capacitances and self parasitic turns of a winding; there is therefore less risk of overvoltage on the transistor of the switching member GMOS and therefore less problem EMC (electromagnetic compatibility).
- Because of the low transformation ratio n3 / n1, it allows to have diodes D1, D2 sized for voltages of the order of 700 to 800V maximum (to maintain the starting voltage of 630V) instead 1000V for the solution of the state of the prior art, which allows the use of more standard components and thus reduce the cost of components.
- It makes it possible to obtain smaller windings in the transformer TR1 and thus a smaller length of wire; therefore, the overall volume of the transformer is reduced. The fact of having a reduced length of wire makes it possible to reduce the brass losses.
- There is less constraint in the isolation between the secondary winding and the auxiliary winding so that they do not touch each other. Indeed, such isolation must be able to hold 560V (-Vn2-Vn3 as previously described) instead of 1000V in the state of the prior art.
- It makes it possible, thanks to the resistor R1, to reliably ignite the discharge lamp by virtue of a potential difference that is sufficient to make the spark gap open.
- Having reduced the volume of the transformer TR1 allows for a reduced surface area on the PCB PCB, and therefore an increase in reliability, a reduction in test costs, an improved process time, and finally a cost report on PCB better.
- The lifetime of the transformer TR1 is increased since the maximum voltage generated in said transformer is 630V against 1000V for the solution of the state of the prior art. As a result, the stress seen by the windings is reduced, that is to say that a better resistance to breakdown is obtained. The transformer is therefore more reliable.
- Finally, it reduces the number of components required for the ignition function only, thanks to the multiplier circuit. Two diodes D1, D2 and two capacitors C1, C2 are sufficient to generate the ignition voltage Vignit from the secondary windings n2 and auxiliary windings n3.
Claims (6)
- A ballast (BLST) for a discharge lamp (LA) comprising:a direct / direct voltage converter (Ccc) in order to provide a rectified direct voltage (Vout), and comprising:- a single voltage rectifier (RD);- a transformer (TR1) comprising a main winding (n1), a secondary winding (n2) and an auxiliary winding (n3), the transformer (TR1) making it possible to provide the rectified direct voltage (Vout); and- a voltage multiplier circuit (MU) in order to provide a starting voltage (Vignit), the difference in potential (Vdiff) between this voltage (Vignit) and the rectified direct voltage (Vout) making it possible to create a switching-on voltage (Um) for the discharge lamp (LA),characterised in that- the auxiliary winding (n3) is in series with the secondary winding (n2); and- the voltage multiplier circuit (MU) is combined with the secondary (n2) and auxiliary (n3) windings of the transformer (TR1).
- Ballast (BLST) according to claim 1, characterised in that the voltage multiplier circuit (MU) comprises two capacitors (C1, C2) and two diodes (D1, D2).
- Ballast (BLST) according to one of the preceding claims, characterised in that it additionally comprises a resistor (R1) at the output from the voltage multiplier circuit (MU).
- Ballast (BLST) according to one of the preceding claims, characterised in that the secondary winding (n2) comprises a transformation ratio (n2/n1) of approximately 5 with the main winding (n1).
- Ballast (BLST) according to one of the preceding claims, characterised in that the auxiliary winding (n3) comprises a transformation ratio (n3/n1) of approximately 2 with the main winding (n1).
- Lighting device (FX) for a vehicle, comprising a discharge lamp (LA) to which there is connected a ballast (BLST) according to any one of the preceding claims, the ballast (BLST) being able to provide a voltage (Vdiff) in order to permit switching on of the discharge lamp (LA).
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
FR0610486A FR2909510B1 (en) | 2006-11-30 | 2006-11-30 | BALLAST FOR DISCHARGE LAMP |
Publications (2)
Publication Number | Publication Date |
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EP1931181A1 EP1931181A1 (en) | 2008-06-11 |
EP1931181B1 true EP1931181B1 (en) | 2011-07-27 |
Family
ID=38068871
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
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EP07121725A Active EP1931181B1 (en) | 2006-11-30 | 2007-11-28 | Ballast for a discharge lamp |
Country Status (4)
Country | Link |
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EP (1) | EP1931181B1 (en) |
AT (1) | ATE518408T1 (en) |
ES (1) | ES2370269T3 (en) |
FR (1) | FR2909510B1 (en) |
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Publication number | Priority date | Publication date | Assignee | Title |
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DE102012204324A1 (en) * | 2012-03-15 | 2013-09-19 | Osram Gmbh | Ignition device for a high-pressure discharge lamp and operating device with such an ignition device |
Family Cites Families (5)
Publication number | Priority date | Publication date | Assignee | Title |
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US5036256A (en) * | 1990-06-21 | 1991-07-30 | Gte Products Corporation | Arc discharge ballast suitable for automotive applications |
US5051665A (en) * | 1990-06-21 | 1991-09-24 | Gte Products Corporation | Fast warm-up ballast for arc discharge lamp |
US6181084B1 (en) * | 1998-09-14 | 2001-01-30 | Eg&G, Inc. | Ballast circuit for high intensity discharge lamps |
KR100291042B1 (en) * | 1999-03-09 | 2001-05-15 | 이광연 | Electronic ballast for high-intensity discharge lamp |
JP2001284089A (en) * | 2000-03-31 | 2001-10-12 | Victor Co Of Japan Ltd | Power supply circuit for lamp |
-
2006
- 2006-11-30 FR FR0610486A patent/FR2909510B1/en not_active Expired - Fee Related
-
2007
- 2007-11-28 AT AT07121725T patent/ATE518408T1/en not_active IP Right Cessation
- 2007-11-28 ES ES07121725T patent/ES2370269T3/en active Active
- 2007-11-28 EP EP07121725A patent/EP1931181B1/en active Active
Also Published As
Publication number | Publication date |
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ATE518408T1 (en) | 2011-08-15 |
FR2909510B1 (en) | 2009-02-13 |
ES2370269T3 (en) | 2011-12-14 |
FR2909510A1 (en) | 2008-06-06 |
EP1931181A1 (en) | 2008-06-11 |
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