EP1931181B1 - EVG für Entladungslampe - Google Patents

EVG für Entladungslampe Download PDF

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Publication number
EP1931181B1
EP1931181B1 EP07121725A EP07121725A EP1931181B1 EP 1931181 B1 EP1931181 B1 EP 1931181B1 EP 07121725 A EP07121725 A EP 07121725A EP 07121725 A EP07121725 A EP 07121725A EP 1931181 B1 EP1931181 B1 EP 1931181B1
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EP
European Patent Office
Prior art keywords
voltage
ballast
vout
vignit
winding
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EP07121725A
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English (en)
French (fr)
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EP1931181A1 (de
Inventor
Philippe Clavier
Sylvain Yvon
Bruno Cassese
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Valeo Vision SAS
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Valeo Vision SAS
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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
    • H05B41/2821—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a single-switch converter or a parallel push-pull converter in the final stage
    • H05B41/2822—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a single-switch converter or a parallel push-pull converter in the final stage using specially adapted components in the load circuit, e.g. feed-back transformers, piezoelectric transformers; using specially adapted load circuit configurations
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/02—Details
    • H05B41/04—Starting switches
    • H05B41/042—Starting switches using semiconductor devices

Definitions

  • the present invention relates to a lighting ballast for a discharge lamp and a fire device incorporating a lamp connected to such a ballast.
  • these high voltages are produced by a power supply module, which also provides power regulation, known as "ballast".
  • the most recent ballasts include in particular a DC / DC switching converter producing a high DC voltage of several hundred volts from the battery voltage for example, a DC / AC converter ensuring the supply of the lamp in steady state to from the high-voltage DC, and a high-voltage module supplying a generator producing the very high voltage necessary for lighting the lamp, the very high voltage being produced from the high DC voltage produced by the DC / DC converter.
  • the DC / DC converter of such a ballast comprises a transformer comprising a main winding and two secondary windings with a transformation ratio equal to 8 with more than 20 turns in the two secondary windings and a rectifier voltage associated with each secondary winding, each rectifier comprising a diode and a capacitor.
  • the main winding is connected to a switching unit connected to the power source.
  • the repetitive interruption of the latter by the switching unit induces at the terminals of the two secondary windings of the transformer respectively two high voltages each rectified by the diode and filtered by the capacitor of the associated rectifier.
  • the difference between these two high voltages makes it possible to obtain a voltage of 1000V. From this voltage of 1000V, an ignition voltage of about 25kV is obtained by the high voltage module connected between the DC / DC converter and the discharge lamp.
  • the transformer occupies a very large volume because of the important transformation ratio.
  • the leakage elements are important which can create overvoltages in the switching unit and interfere with the control of the DC / DC converter.
  • the rectifying diodes must be dimensioned for a voltage of 1000V, which poses problems of realization and cost.
  • the document JP 2001 284 089 discloses a discharge lamp ballast comprising a converter, a voltage multiplier and a transformer comprising a main winding, a secondary winding and an auxiliary winding.
  • the present invention aims to overcome these disadvantages of the state of the art.
  • the invention relates to a second object, a vehicle fire device comprising a discharge lamp to which is connected a ballast according to any one of the preceding characteristics, the ballast being able to provide a voltage to allow a lighting of the lamp for discharge.
  • a BLST ballast connected to a discharge lamp LA in the context of a non-limiting application of vehicle fire FX.
  • the FX fire is for example, a traffic light (night lights, codes, taillights) or lighting called projector (lighthouse).
  • the term "fire" will be used indifferently to designate such lighting or signaling devices.
  • the LA discharge lamp can be used for day and / or night lighting.
  • ballast BLST is positioned on the same PCB type PCB ("Printed Circuit Board").
  • the DC / DC converter Ccc makes it possible to adapt the power source, in this case the battery voltage Vbat, to the discharge lamp voltage by generating the continuous high voltage rectified Vout and the ignition voltage Vignit.
  • the HV high voltage module of the discharge lamp LA will be able to generate a first ignition pulse Um, of the order of 25kV to turn on said lamp LA.
  • the DC / DC converter Ccc may furthermore comprise a resistor R1 mounted at the output of the multiplier circuit MU to allow the charging of a capacitor of the high voltage module HV of the discharge lamp LA to be delayed as we will see in detail later.
  • the secondary winding n2 is defined in such a way that the transformation ratio n2 / n1 between this winding n2 and the main winding n1 is equal to 5.
  • the auxiliary winding n3 is defined in such a way that the transformation ratio n3 / n1 between this winding n3 and the main winding n1 is equal to 2.
  • the number of turns in the main winding n1 is equal to 4
  • the number of turns in the secondary winding n2 is equal to 20
  • the number of turns in the auxiliary winding n3 is equal at 8.
  • the switching member is a MOSFET transistor.
  • the circuit RD comprising for this purpose a rectifying diode Dout and a filtering capacitor Cout.
  • the rectifying diode Dout is connected to the node P1 between the secondary windings n2 and auxiliary winding n3 by its cathode as illustrated in FIG. Fig. 2 .
  • the multiplier MU is composed of two diodes D1, D2 and two capacitors C1, C2.
  • the capacitors C1 and C2 provide the ignition voltage Vignit, while the diodes D1 and D2, during the ignition phase, on the one hand to charge the capacitors C1 and C2 associated and on the other hand their avoid being discharged in a sense as we will see later.
  • the DC / DC converter Ccc has the same elements as in the first embodiment but with an inverted bias of the rectifying diode Dout and the diodes of the multiplier circuit D1, D2. Moreover, the rectifier circuit RD makes it possible to rectify the induced auxiliary voltage Vn3 instead of the induced secondary voltage Vn2. At this time, the rectified voltage Vout is positive and the ignition voltage Vignit is negative.
  • This converter makes it possible to make the rectified high voltage Vout alternative necessary for the operation of the steady-state discharge lamp LA, that is to say during normal operation of the lamp, from the continuous rectified voltage Vout supplied by the DC / DC converter.
  • the DC / AC converter Cca comprises four transistors (not shown) mounted in complete bridge, the simultaneous opening or closing of a pair of transistors being controlled alternately with that of the another pair to make the voltage rectified.
  • these transistors are NPN transistors of the IGBT type "Insulated Gate Bipolar Transistor", well adapted to the high voltages involved, both during the ignition phase and during the steady state of the lamp LA.
  • control unit UC makes it possible to control, by means of control signals in response to external control commands, the width of the switching pulses of the DC / DC converter Ccc, as well as the operation of the complete bridge of the AC / DC converter whether in the ignition phase or in steady state.
  • the BLST ballast provides the voltage necessary to turn on the lamp during an ignition phase, but also provides the voltage required to operate the lamp when it is on.
  • the BLST ballast operates in the following manner.
  • a supply voltage Vbat equal to 10 V is used.
  • this battery voltage Vbat varies between 8V (for example during a start) and 12V with possible peaks at 19V (norm given by the manufacturer).
  • the ballast BLST will provide on the one hand the continuous rectified voltage Vout and on the other hand the ignition voltage Vignit, the potential difference between these two voltages, to feed the high module HV lamp voltage LA to turn on said lamp.
  • the switching member GMOS when closed, it allows a loading of the second capacitor C2 of the multiplier circuit MU for supplying the ignition voltage Vignit, while when it is open , it allows to charging the filter capacitor Cout for providing the DC rectified voltage Vout, and charging the first capacitor C1 MU multiplier circuit to also provide the Vignit boot voltage.
  • the switching member GMOS which is controlled by cutting pulses, allows through its opening and closing repetitive gradually load the three capacitors alternately.
  • the switching frequency of the GMOS switching element is 100 kHz during this ignition phase.
  • the MOSFET transistor that composes the switching member GMOS comprises a gate voltage Vgs and a drain-source voltage Vds that vary as a function of the opening-closing of the MOSFET transistor also causing a variation of the main voltages Vn1, secondary induced. Vn2 and induced auxiliary Vn3 of transformer TR1.
  • the evolution of these voltages Vn1, Vn2, Vn3 associated with the transformers TR1 makes it possible to charge the capacitors C1, C2, Cout supplying the continuous rectified voltage Vout and the ignition voltage Vignit.
  • transformer voltages TR1 as a function of the two states (closed-open) of the MOSFET transistor is described below when the capacitors C1, C2, Cout are fully charged.
  • the main winding n1 is connected directly to the power source Vbat.
  • the main voltage Vn1 is equal to the battery voltage Vbat, ie is equal to 10V in the example taken.
  • a main current Ip is then generated and passes through the main winding n1 of the transformer TR1.
  • the induced currents ln2 and ln3 go in the opposite direction of the clockwise.
  • the induced secondary voltage Vn2 is equal to 50 and the induced auxiliary voltage Vn3 is equal to 20 as illustrated in FIG. Fig. 3 .
  • the righting diode Dout is then blocked. It is represented in dashed line at Fig. 4 . It is the same for the first diode D1 MU multiplier circuit.
  • the second diode D2 of the multiplying circuit MU is conducting (there is approximately 0V at its terminals).
  • the second capacitor C2 of the multiplier circuit MU is loaded via this second diode D2.
  • the first diode D1 being blocked, the first capacitor C1 of the multiplier circuit MU discharges via the second diode D2 to the second capacitor C2.
  • the second capacitor C2 is thus charged with the induced secondary voltages Vn2, induced auxiliary Vn3 and the voltage Vc1 of the first capacitor C1.
  • Vignit + 630V.
  • the ignition voltage Vignit is well supplied by the charging of the second capacitor C2 of the multiplier circuit MU and is well generated from the rectified voltage Vout.
  • Vn2_off Vn3_off the voltages across respective windings n2 and n3 when the MOSFET is open
  • Vn2_on, Vn3_on the voltages when the MOSFET is closed.
  • the MOSFET transistor is open.
  • the gate voltage Vgs is zero, the MOSFET transistor behaves like a diode passing from the source to the drain.
  • the drain-source voltage Vds is therefore positive as illustrated in FIG. Fig. 3 .
  • the opening of the MOSFET transistor prevents the main current Ip from flowing.
  • the recovery diode Dout is busy, as well as the first diode D1 of the multiplier circuit MU, while the second diode D2 of the multiplier circuit MU is blocked (it is represented in dotted lines).
  • the Dout rectifying diode being conducting one has about 0V at its terminals
  • the filtering capacitor Cout is charged by said diode Dout.
  • the GMOS switching element is controlled in such a way that the charge of the filter capacitor Cout is equal to -400V.
  • a control device (not shown) which measures the charge of the filter capacitor Cout.
  • Vout -400V at the end of the loading of the capacitor Cout.
  • the first diode D1 being conducting (one has about 0V at its terminals), the first capacitor C1 of the multiplier circuit MU is charged through this diode D1.
  • the first capacitor C1 is thus charged with the induced secondary voltages Vn2 and induced auxiliary Vn3.
  • the second capacitor C2 of the multiplier circuit MU can not at this time be discharged towards the first capacitor C1 because the second diode D2 is blocked.
  • the second capacitor C2 discharges into the circuit (capacitor C3) of the lamp LA as will be seen below.
  • the charging time of the second capacitor C2 is around tens of microseconds (1 / 100kHz) while the discharge time is around a few milliseconds (thanks to a resistance R1 as discussed below) .
  • the capacitor C2 becomes charged thereby providing the Vignit ignition voltage from the rectified voltage Vout, while when the MOSFET transistor is open, the filter capacitor Cout is charged thereby providing the rectified voltage Vout.
  • the diodes D1 and D2 of the multiplier circuit MU must be sized to hold a voltage of the order of 800V.
  • Vrmax is equal to Vignit.
  • the first diode D1 when the first capacitor C1 is charged, the first diode D1 is conducting (therefore the voltage at its terminals is 0V), so the voltage of the second diode D2 corresponds to Vignit.
  • the second diode D1 when the second capacitor C2 is charged, the second diode D1 is conducting (therefore the voltage at its terminals is 0V), so the voltage of the first diode D1 corresponds to Vignit.
  • the voltage difference Vdiff is applied to the HV high voltage module as indicated in FIG. Fig. 6 .
  • the gas spark gap Gz behaves like an open switch.
  • the capacitor C3 is charged.
  • a predetermined threshold of charging of the order of 800V in a non-limiting example, the spark gap Gz becomes abruptly conductive and creates a current pulse in the primary winding of the transformer TR2 which produces in the secondary the very high Um voltage of 25kV, thus creating a first electric arc necessary for lighting the lamp LA.
  • the capacitor C3 discharges very quickly in the transformer TR2.
  • This voltage is of the order of -85V steady state for a xenon lamp with mercury (Hg + ) and of the order of -42V for a mercury-free xenon lamp (Hg - ).
  • control unit UC acts to activate and deactivate the transistors of the DC / AC converter so that it supplies this AC voltage from the rectified voltage Vout necessary to continue operating the lamp LA.
  • This AC voltage is obtained from the DC rectified voltage Vout supplied by the DC / DC converter Ccc.
  • the DC / DC converter Ccc provides the power necessary for the rectified voltage Vout is in this case equal to -85V.
  • the frequency switching speed of the GMOS switching element is 300kHz in steady state.
  • the MOSFET switching transistor remains open longer than steady state.
  • the Fig. 7 summarizes the evolution of the voltage Ula across the discharge lamp LA during the ignition phase and during the steady state.
  • the interval t0-t1 represents the ignition phase, while the interval t3-t4 represents the steady-state operating phase.
  • intervals t1-t2 and t2-t3 represent transition phases.
  • the rectified voltage Vout begins to decrease (the capacitor Cout of the rectifier circuit discharges) while the ignition voltage Vignit drops to -400V because the capacitor C3 discharges suddenly, its voltage Vc3 becomes zero, the rectified voltage Vout remaining at -400V.
  • the rectified voltage continues Vout is made alternative by means of the DC / AC converter Cca.
  • the voltage Ula of the lamp LA is equal to the rectified voltage Vout.
  • the two curves Cvignit and Cvout representative respectively of the two voltages Vignit and Vout illustrate the progressive loading of capacitors C2 and Cout corresponding.
  • the slope of the curve Cvignit representative of the ignition voltage Vignit is greater than that of the curve Cvout representative of the rectified voltage Vout because the filter capacitor Cout is dimensioned so as to be larger than the second capacitor C2.
  • the capacitor Cout generates the greatest power to the lamp LA and corresponds to a reserve of energy. Indeed, in steady state, it is the only one to supply energy to the lamp LA.
  • the Vignit ignition voltage can reach its maximum value + 630V at time t1 before the rectified voltage reaches its -400V. This could generate a voltage difference at time t1 less than 1030V, for example at about 800V, the rectified voltage Vout reaching only 200V for example. This voltage difference Vdiff can cause ignition of the lamp LA.
  • the conduction threshold of the gas spark gap Gz is of the order of 800V
  • the voltage difference Vdiff is at the threshold limit of the gas spark gap; also the LA lamp may not light properly.
  • the resistor R1 of the BLST ballast makes it possible to delay the charging of the capacitor C3 of the lamp LA with the ignition voltage Vignit as illustrated by the curve CRvignit.
  • the two voltage Vignit and Vout will reach their maximum value at the same time so as to provide a potential difference sufficient to exceed the loading threshold of the gas spark gap thus allowing a reliable ignition of the lamp LA.
  • the resistor R1 makes it possible to wait for the rectified voltage Vout to be stabilized at -400V in order to make it possible to obtain a voltage difference Vdiff greater than the conduction threshold of the gas spark gap Gz so as to obtain an arc of sufficient voltage. (25kV) required for reliable ignition of the LA lamp.
  • this resistor R1 prevents current peaks in the second diode D2 and thus prevents the latter from being damaged.
  • the vehicle fire application was taken as an example, but of course, the described ballast can be used in other applications such as, in non-limiting examples, interior lighting building ("Interior Lighting ”) Or street lighting ("General Lighting ").

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Circuit Arrangements For Discharge Lamps (AREA)
  • Ignition Installations For Internal Combustion Engines (AREA)

Claims (6)

  1. Vorschaltgerät (BLST) für eine Entladungslampe (LA) mit
    - einem Gleichspannungs-Gleichspannungswandler (Ccc) zum Liefern einer gleichgerichteten Gleichspannung (Vout), und mit
    - einem einzigen Spannungsgleichrichter (RD),
    - einem Transformator (TR1) mit einer Hauptwicklung (n1), einer Sekundärwicklung (n2) und einer Zusatzwicklung (n3), wobei der Transformator (TR1) die gleichgerichtete Gleichspannung (Vout) zu liefern vermag, und
    - einer Spannungsvervielfacherschaltung (MU) zum Liefern einer Durchbruchspannung (Vignit), wobei die Potentialdifferenz (Vdiff) zwischen der Spannung (Vignit) und der gleichgerichteten Gleichspannung (Vout) eine Zündspannung (Um) für die Entladungslampe (LA) zu erzeugen vermag,
    dadurch gekennzeichnet, dass
    - die Zusatzwicklung (n3) mit der Sekundärwicklung (n2) in Reihe geschaltet ist, und
    - die Spannungsvervielfacherschaltung (MU) mit der Sekundärwicklung (n2) und der Zusatzwicklung (n3) des Transformators (TR1) kombiniert ist.
  2. Vorschaltgerät (BLST) nach Anspruch 1,
    dadurch gekennzeichnet, dass die Spannungsvervielfacherschaltung (MU) zwei Kondensatoren (C1, C2) und zwei Dioden (D1, D2) umfasst.
  3. Vorschaltgerät (BLST) nach einem der vorhergehenden Ansprüche,
    dadurch gekennzeichnet, dass es ferner einen Widerstand (R1) am Ausgang der Spannungsvervielfacherschaltung (MU) aufweist.
  4. Vorschaltgerät (BLST) nach einem der vorhergehenden Ansprüche,
    dadurch gekennzeichnet, dass die Sekundärwicklung (n2) ein Transformationsverhältnis (n2/n1) zur Hauptwicklung (n1) von 5 aufweist.
  5. Vorschaltgerät (BLST) nach einem der vorhergehenden Ansprüche,
    dadurch gekennzeichnet, dass die Zusatzwicklung (n3) ein Transformationsverhältnis (n3/n1) zur Hauptwicklung (n1) von 2 aufweist.
  6. Fahrzeugscheinwerfervorrichtung (FX) mit einer Entladungslampe (LA), an die ein Vorschaltgerät (BLST) nach einem der vorhergehenden Ansprüche angeschlossen ist, wobei das Vorschaltgerät (BLST) dazu ausgeführt ist, eine Spannung (Vdiff) zum Ermöglichen einer Zündung der Entladungslampe (LA) zu liefern.
EP07121725A 2006-11-30 2007-11-28 EVG für Entladungslampe Active EP1931181B1 (de)

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
FR0610486A FR2909510B1 (fr) 2006-11-30 2006-11-30 Ballast pour lampe a decharge

Publications (2)

Publication Number Publication Date
EP1931181A1 EP1931181A1 (de) 2008-06-11
EP1931181B1 true EP1931181B1 (de) 2011-07-27

Family

ID=38068871

Family Applications (1)

Application Number Title Priority Date Filing Date
EP07121725A Active EP1931181B1 (de) 2006-11-30 2007-11-28 EVG für Entladungslampe

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EP (1) EP1931181B1 (de)
AT (1) ATE518408T1 (de)
ES (1) ES2370269T3 (de)
FR (1) FR2909510B1 (de)

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE102012204324A1 (de) * 2012-03-15 2013-09-19 Osram Gmbh Zündvorrichtung für eine Hochdruckentladungslampe und Betriebsvorrichtung mit einer derartigen Zündvorrichtung

Family Cites Families (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5051665A (en) * 1990-06-21 1991-09-24 Gte Products Corporation Fast warm-up ballast for arc discharge lamp
US5036256A (en) * 1990-06-21 1991-07-30 Gte Products Corporation Arc discharge ballast suitable for automotive applications
US6181084B1 (en) * 1998-09-14 2001-01-30 Eg&G, Inc. Ballast circuit for high intensity discharge lamps
KR100291042B1 (ko) * 1999-03-09 2001-05-15 이광연 고출력 고휘도 방전램프용 전자식 안정기
JP2001284089A (ja) * 2000-03-31 2001-10-12 Victor Co Of Japan Ltd ランプ用電源回路

Also Published As

Publication number Publication date
ES2370269T3 (es) 2011-12-14
ATE518408T1 (de) 2011-08-15
FR2909510B1 (fr) 2009-02-13
EP1931181A1 (de) 2008-06-11
FR2909510A1 (fr) 2008-06-06

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