EP1926974A2 - Procede de mesure sur la base du temps de propagation pour determiner une distance - Google Patents

Procede de mesure sur la base du temps de propagation pour determiner une distance

Info

Publication number
EP1926974A2
EP1926974A2 EP06793156A EP06793156A EP1926974A2 EP 1926974 A2 EP1926974 A2 EP 1926974A2 EP 06793156 A EP06793156 A EP 06793156A EP 06793156 A EP06793156 A EP 06793156A EP 1926974 A2 EP1926974 A2 EP 1926974A2
Authority
EP
European Patent Office
Prior art keywords
frequency
sampling
control
signal
oscillator
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
Application number
EP06793156A
Other languages
German (de)
English (en)
Inventor
Bernhard Michalski
Dominik Buser
Stefan Scherr
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Endress and Hauser SE and Co KG
Original Assignee
Endress and Hauser SE and Co KG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Endress and Hauser SE and Co KG filed Critical Endress and Hauser SE and Co KG
Publication of EP1926974A2 publication Critical patent/EP1926974A2/fr
Ceased legal-status Critical Current

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Classifications

    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01F—MEASURING VOLUME, VOLUME FLOW, MASS FLOW OR LIQUID LEVEL; METERING BY VOLUME
    • G01F23/00—Indicating or measuring liquid level or level of fluent solid material, e.g. indicating in terms of volume or indicating by means of an alarm
    • G01F23/22—Indicating or measuring liquid level or level of fluent solid material, e.g. indicating in terms of volume or indicating by means of an alarm by measuring physical variables, other than linear dimensions, pressure or weight, dependent on the level to be measured, e.g. by difference of heat transfer of steam or water
    • G01F23/28—Indicating or measuring liquid level or level of fluent solid material, e.g. indicating in terms of volume or indicating by means of an alarm by measuring physical variables, other than linear dimensions, pressure or weight, dependent on the level to be measured, e.g. by difference of heat transfer of steam or water by measuring the variations of parameters of electromagnetic or acoustic waves applied directly to the liquid or fluent solid material
    • G01F23/284—Electromagnetic waves

Definitions

  • the present invention relates to a device for detection and
  • Such devices for detection and monitoring of the level in a container are often used in the measuring devices of automation and process control technology.
  • the Applicants produce and distribute measuring instruments under the name Micropilot, Prosonic and Levelflex, which operate according to the transit time measuring method and serve to determine and / or monitor a level of a medium in a container.
  • microwaves or radar waves are transmitted via an antenna into the process space or guided along a surface waveguide which protrudes into the medium, and the reflected echo waves are received again by the antenna or transducers according to the distance-dependent transit time of the signals. From the time difference between the emission of the high-frequency signals and the reception of the reflected echo signals, the distance of the measuring device to the medium surface can be determined.
  • the transit time measurement method can essentially be divided into two basic determination methods: the time difference measurement, which requires a pulse-modulated high-frequency measurement signal for the distance covered; Another widespread method of determination is the determination of the flip-flop frequency difference of the emitted continuous high-frequency signal to the reflected, received high-frequency signal (FMCW - Frequency-Modulated Continuous Wave). Furthermore, no restriction is made to a special investigation procedure, but the generally valid transit time measurement method is used.
  • Measuring signals in the GHz range is that for the evaluation of the high-frequency total measurement signal, consisting of emitted measurement signals and reflected echo signals, high-frequency components must be used, which are designed for such high frequency ranges.
  • One solution to this problem is sequential sampling, which consists of a plurality of such high frequency sampled measurement signals, by sampling the sampled measurement signals taken at specific, periodic intervals, generating a time-expanded intermediate frequency signal.
  • This additional processing step of the high-frequency measurement signals is carried out because there are no correspondingly cost-effective data processing units, for example DSPs (Digital Signal Processors), which can reliably process high-frequency measurement signals.
  • DSPs Digital Signal Processors
  • a first approach for generating a time-extended intermediate frequency signal is the mixer principle, in which two oscillators produce two oscillations with slightly different frequencies. Due to the slight 'detuning' of the frequencies of the two oscillations, a phase shift increases linearly with each measurement period, which corresponds to a linearly increasing time delay.
  • the mixer principle is described for example in DE 31 07 444 Al by means of a high-resolution impulse radar method.
  • a generator generates first microwave pulses and emits them via an antenna at a predetermined transmission repetition frequency in the direction of the surface of the medium.
  • Another generator generates reference microwave pulses that are the same as the first microwave pulses, but slightly different from those in the retransmission frequency.
  • the echo signal and the reference signal are mixed, for example, by a frequency converter or mixer, whereby an intermediate frequency signal is produced.
  • the intermediate frequency signal has the same shape as the echo signal but is stretched by a translation factor equal to a quotient of the transmission repetition frequency and the frequency difference between the repetition frequency or pulse repetition frequency of the first microwave pulses and the repetition frequency or sampling frequency of the reference microwave pulses.
  • the frequency of the intermediate frequency signal is far below 100 kHz.
  • the advantage of the transformation to the intermediate frequency is that relatively slow and thus inexpensive electronic components are used for signal acquisition and / or signal evaluation can.
  • This sampling circuit has two oscillators, of which at least one is variable in frequency, with one oscillator controlling the transmitting generator and the other oscillator controlling the sampling pulse generator.
  • a frequency mixer forms the difference between the two frequencies, which is used to set or regulate the most constant time expansion factor possible to a desired value.
  • phase-locked loop Another device for time transformation of high-frequency measurement signals is shown in WO 2004/013584 Al.
  • the ramp principle the equidistant from sample point to sample time difference is generated with the aid of an RC element.
  • the RC element is biased by a step-shaped or linearly increasing ramp voltage, thus receives a certain offset, and is then charged and discharged in the rhythm of the transmitter repetition frequency.
  • the voltage offset increases in the RC elements, whereby the reaching of the switching threshold is delayed depending on the height of the ramp voltage.
  • the time expansion factor or the transformation factor depends largely on the ramp time principle of an RC element.
  • the dependence of the RC element on the temperature has a completely circuit-dependent effect on the scaling of the time transformation. To almost eliminate this problem, it is necessary to compensate for the temperature-induced changes via a control loop.
  • the object of the invention is to propose an apparatus and a method with a stabilized and cost-effective control circuit for generating an intermediate frequency signal with a transformation factor which can be determined with high precision.
  • an external clock input is provided, with a first Clock output of the sampling clock oscillator or is connected to a second clock output of the transmission - clock oscillator via a clock line, so that the clocking of the control / evaluation unit with the sampling signal in the sampling frequency or the pulse repetition signal with the pulse repetition frequency.
  • sampling clock oscillator is configured controllable. Due to the possibility of controlling the sampling oscillator, it is possible to establish a regulation of the difference frequency between the transmit clock oscillator and the sampling clock oscillator by, for example, the control / evaluation unit. By a control signal of the control / evaluation unit, the sampling frequency of the sampling clock oscillator is controlled so that sets the desired difference frequency between the frequencies of the transmission signal and the sampling signal.
  • a control output is provided to the control / evaluation unit, through which the control / evaluation unit controls or triggers the sampling clock oscillator via a control line with the aid of a control input to the sampling clock oscillator.
  • An expedient embodiment of the invention is that an integrating element is provided in the control line between the control input of the sampling clock oscillator and the control output of the control / evaluation unit, which forms a corresponding integral value from the digital control output signals of the control / evaluation.
  • this integrator in particular a low-pass filter, the digital control signals of the control / evaluation unit, for example, are converted into a corresponding DC voltage signal which can be used to drive a voltage-controlled oscillator VCO.
  • sampling clock oscillator is designed as a voltage-controlled oscillator.
  • VCO voltage controlled oscillators
  • a parallel to a quartz oscillator capacitance diode whose capacity can be adjusted by the applied DC voltage and thereby changes the oscillation frequency used.
  • the sampling clock oscillator is designed as a numerically controlled oscillator.
  • These types of controllable oscillators can be directly connected through the control the digital control signal of the control / evaluation unit.
  • a high-precision, stable oscillator is provided with a stable pulse repetition frequency as a send clock oscillator.
  • Time base for determining the distance which is determined from the transit time of the measuring signals and their propagation speed, created, whereby measurement accuracies of the distance in the millimeter range are possible.
  • the frequency converter is designed as an analog mixer.
  • a further advantageous embodiment of the device according to the invention is that the frequency converter is designed as a digital mixer.
  • a very advantageous variant of the device according to the invention is the fact that in the clock line between the clock input of the control / evaluation and the clock output of the sampling clock oscillator, a divider or a multiplier is configured, which changes the sampling frequency of the sampling signal according to the setting.
  • FIG. 1 is a block diagram of an embodiment of the inventive device for determining the level in a container
  • Fig. 3 is a block diagram showing the control circuit of the inventive device for generating the intermediate frequency with delay circuit and control / evaluation unit.
  • Fig. 1 an embodiment of a block diagram of the device 1 according to the invention for determining the distance d or the level e is shown on the basis of the running time t.
  • the device 1 has a transducer element 16 connected primarily to the transmitting / receiving unit 2, by means of which the high-frequency measuring signal or transmitting signal S ⁇ x is coupled into and emitted into a measuring volume 6 of the container 5 comprising the filling material 3.
  • the frequency of the pulsed transmission signal S T ⁇ is in this case, as is usual with such microwaves operating devices 1, in a frequency range of a few gigahertz, in particular in the frequency range from 0.5 GHz to 30 GHz.
  • the transducer element 16 can, as shown in Fig. 1, as an antenna 16a and in particular as a horn antenna, a rod antenna, a parabolic antenna or a planar antenna, be configured, the transmission signal S ⁇ x in the measuring volume 6 of the container. 5 radiates.
  • antennas 16a radiating into the free space of the measuring volume 6, it is also possible to use transmit signals S ⁇ x guided on surface waveguides 16b in the level-measuring device 1, although this is not explicitly shown in FIG.
  • the time domain reflectometry or the TDR measurement method for example, a high-frequency pulse is emitted along a Sommerfeld or Goubauschen surface waveguide 16b or coaxial waveguide, which at a discontinuity of the DK value (dielectric constant) of the surface waveguide 16b surrounding filling material 3 is partially reflected back. Due to impedance jumps within the measuring volume 6 of the container 5, in particular at the boundary layer between free space and filling material 3 in the container 6, the transmission signal S TX is at least partially reflected back and thus a corresponding reflection signal S RX runs on the surface waveguide 16b in the opposite direction ,
  • transceiver unit 2 In the time difference measurement of pulsed high-frequency measurement signals coupled to the transducer element 16 transceiver unit 2 is used to mutually coherent wave packets of predeterminable pulse shape and pulse width, so-called bursts, to generate and process, and by means of the bursts of to generate the level e affected, analogue time-expanded Bacfre- frequency signal S ZF .
  • the pulse shape of a single burst usually corresponds to needle-shaped or sinusoidal, half-wave pulses of predeterminable pulse width; however, if necessary, other suitable pulse shapes may be used for the bursts.
  • the circuit structure of the device 1 is composed mainly of at least one transmitting / receiving unit 2, a control / evaluation unit 7, and a filter / amplifier unit 9 together.
  • the transmitting / receiving unit 2 can turn into an RF circuit part with transmit pulse generator 14, sampling pulse generator 15, sampling circuit 20, and send / receive switch 8, in which mainly RF signals are generated and processed, and a LF circuit part with Sendetaktoszillator 18, sampling clock oscillator 17, mixer 11 and optionally an integrator 10, in which mainly NF signals are generated and processed, divide.
  • the individual circuit elements in the RF circuit part are constructed according to experience in analog circuit technology, ie analog measurement signals are generated and processed.
  • the individual circuit elements in the LF circuit part can either be based on digital circuit technology and / or analog circuit technology. From the point of view of the rapid progress of digital signal processing, it is also conceivable to carry out the HF range with digital circuit elements. There are also a variety of variations of the individual circuit elements in digital and analog circuit technology conceivable that are not explicitly performed. Therefore, the following description of one embodiment is to be considered as an example of many possible embodiments.
  • the transmitting / receiving unit 2 comprises a transmission pulse generator 14 for generating a first burst sequence serving as a transmission signal S ⁇ x.
  • the transmission signal S ⁇ x is, as usual in such devices 1, supported with a mean high frequency f HF , which is approximately in the range between 0.5 and 30 GHz, and clocked with a pulse repetition frequency f PRF or shot rate, which has a frequency range of some Megahertz, in particular a frequency range of 1 MHz to 10 MHz is set.
  • This pulse repetition frequency f PRF for driving the transmit pulse generator 14 is generated by a transmit clock oscillator 18.
  • the high frequency f HF and / or pulse repetition frequency f PRF can also, if necessary, be above the respectively specified frequency ranges.
  • the transmission signal S TX applied to the signal output of the transmission pulse generator 14 is transmitted by means of a transmitting / receiving switch 8, in particular by means of a directional coupler or a hybrid coupler, the transmitting / receiving unit 2 into the at a first signal output of the transmitting / receiving switch 8 connected transducer element 16 coupled.
  • the transmission signal S ⁇ x is also applied to the second signal output of the transmission / reception switch 8.
  • the transmit pulse generator 14 and the sampling pulse generator 15 are designed as commercially available analog RF oscillators, such as quartz oscillators, phase-locked oscillator circuits or surface acoustic wave filters (SAW).
  • the reflection measurement signals S RX generated in the manner described above in the measurement volume 6 of the container 5 are, as already mentioned, received again by the device 1 by means of the transducer element 16 and coupled out at the second signal output of the transmission / reception switch 8. Accordingly, at the second signal output of the transmit / receive switch 8 may have an overall measurement signal S T ⁇ + S RX formed by means of the transmission signal S T x and the reflection measurement signal S RX are tapped.
  • the high frequency f HF and / or the pulse repetition frequency f PRF of the transmission signal S T ⁇ set so high that a direct evaluation of the second signal output of the transmitting / receiving switch 8 applied total measuring signals S TX + S RX , in particular a direct measurement of the transit time t, practically no longer or only with a high technical complexity, eg by Use of high-frequency electronic components, is possible.
  • the transmitting / receiving unit 2 further comprises a sampling circuit 20 and a delay circuit 21, which together serve to time stretch the high-frequency-carrying total measurement signal S T ⁇ + S R ⁇ , in such a way that the high frequency f HF and the pulse repetition frequency f PRF are transformed into a lower frequency range of a few hundred kilohertz.
  • sampling circuit 20 For temporally stretching the total measurement signal S TX + S RX , this is supplied to a first signal input of the sampling circuit 20 connected to the second signal output of the transmitting / receiving switch 8.
  • the sampling circuit is simultaneously ⁇ , the total measuring signal S T ⁇ S + R 20 applied serving as a sampling signal Ss amp i burst sequence of sampling oscillator 17 at a second signal input.
  • a sampling frequency f Samp i or clock rate at which the sampling signal Ss amp i is clocked is normally set slightly smaller than the pulse repetition frequency f PRF of the transmission signal S T ⁇ .
  • the total measurement signal S T ⁇ + S RX is mapped to an intermediate frequency signal S ZF , which is temporally stretched by a transformation factor K ⁇ relative to the total measurement signal S T ⁇ + S RX .
  • This sampling circuit 20 samples due to the frequency offset between the pulse repetition frequency f PRF and the sampling frequency f Samp i the total measurement signal S TX + S I «in each period at different phase, whereby a time-expanded intermediate frequency signal S ZF with the previously described transformation factor k ⁇ is formed.
  • sampling circuit 20 an RF frequency converter or RF mixer or a fast sampling switch can be used.
  • the sampling switches are used, for example, RF diodes or fast transistors.
  • the transformation factor k ⁇ or the time expansion factor with which the total measurement signal S T ⁇ + S RX is converted into a lower-frequency intermediate frequency signal S ZF corresponds to a quotient of the pulse repetition frequency f PRF of the transmission signal S ⁇ x divided by a difference of the pulse repetition frequency f PRF of the transmission signal S ⁇ x and the sampling frequency f Samp i of the sampling signal S Samp i.
  • An intermediate frequency f ZF of the thus generated intermediate frequency signal S ZF is in such devices 1 for determining the level e usually in a frequency range of 50 to 200 kHz; if necessary, the frequency range can be selected higher or lower.
  • Empirical in the measuring instruments of the Applicant the intermediate frequency f ZF set to about 160 kHz.
  • the dependence of the intermediate frequency f ⁇ on the ratio of the sampling frequency f Samp i and the pulse repetition frequency fp R p, as shown in equation (equation 2), can be derived from equation (equation 1). [0040]
  • the intermediate frequency signal S ZF which is time-expanded relative to the total measurement signals S TX + S RX by a transformation factor k ⁇ , is suitably amplified and filtered by a filter / amplifier unit 9 as a filtered intermediate frequency signal S gefZF before it is evaluated in the rule / evaluation unit 7 or other evaluation circuits as echo curve or envelope.
  • the difference frequency f Dlff as shown in Figures 1, 2 and 3, determined by a frequency converter 11 and mixer.
  • the frequency converter 11 or mixer can be embodied either as a digital mixer 12, in particular as an XOR logic module or a D flip-flop for mixing digital measurement signals, or as an analog mixer 13, in particular as a diode ring mixer or in general a multiplier Mixing of analog measuring signals to be configured.
  • This difference frequency f Dlff is determined for two reasons; Firstly, the instantaneous triggering and triggering of the sampling clock oscillator 17 and possibly also of the send clock oscillator 18 is checked by the control / evaluation unit 7 and secondly, a transformation factor k is calculated from the quotient of the known or measured pulse repetition frequency f PRF and the difference frequency f Dlff ⁇ determined in the rule / evaluation unit 7.
  • the transit time t of the measurement signals, as well as the fill level e can also be determined by echo signal evaluation of the filtered intermediate frequency signal S gefZF and knowledge of the transformation factor k ⁇ .
  • the Sendetaktoszillator 18 is designed to determine a highly accurate exact transit time t of the measurement signals or distance d as a very stable stable stable quartz oscillator. Nevertheless, the sampling clock oscillator 17 and, under certain circumstances, the transmit clock oscillator 18 are designed to be controllable.
  • the controllable or tunable oscillators 17, 18 are in the LF circuit part of the transmitting / receiving unit 2, for example, as a voltage-controlled oscillators VCO or digitally or numerically controlled oscillators, eg NCO executed.
  • control input 29 to the voltage-controlled oscillators VCO, they can be controlled by the built-in control line 30 integrator 10, which forms the digital signal sequences a corresponding DC voltage value of the control output 28 of the control / evaluation unit 7.
  • the digital or numerically controlled oscillators, for example NCO, are controlled directly by an existing control input 29 by means of a control line 30 or a parallel control bus 30 from the control output 28 of the control / evaluation unit 7 with digital values.
  • the determination of the difference frequency f Dlff is not mandatory, since the digital generation of frequencies, for example via a counter in a phase-locked loop, via an integer divisor ratio of the input signals to the feedback signals or pulse-pause ratio of the digital signal is set. Since these digital control circuits regulate themselves and the stable desired frequency is known, the determination of the difference frequency f Dlff can be dispensed with in principle by a sequential sampling.
  • phase-locked loop An example of a digital phase-locked loop is a phase-locked loop.
  • VCO Freewheeling voltage-controlled oscillator
  • Fig. 2 and 3 a partial section of the block diagram of Fig. 1 is shown, which shows the control circuit of the device for generating the intermediate frequency with delay circuit 21 and control / off value unit 7.
  • the control loop according to the prior art is shown.
  • the differential frequency f Dlff is determined in the delay circuit 21 by the sequential scanning of the pulse repetition frequency f PRF with the sampling frequency f Samp i by means of a frequency converter 11.
  • This difference frequency f Dlff is processed as described above in the control / evaluation unit 7 and controlled according to the controllable sampling oscillator 17.
  • a control loop has been created, which sets the difference frequency f Dlff largely on the desired setpoint, for example 21.74 Hz.
  • the control / evaluation unit 7 is according to the prior art, as in Fig. 2 shown, predetermined by its own clock or processor oscillator 19 of the power stroke.
  • This clock or processor oscillator 19 can be designed as an integral part of the control / evaluation unit 7 or as an external component, for example a quartz oscillator. Due to this structure, different temperature influences or other influences on the oscillators (17, 18, 19) cause different fluctuations in the periodicity or frequency of the processor oscillator 19 and the difference frequency f Dlff of the sampling oscillator 17 and the transmit clock oscillator 18 , which leads to errors in the determination of the difference frequency f Dlff and consequently the transformation factor K x . These errors due to different changes in sampling or sampling time periods are referred to as jitter errors.
  • jitter is the phase fluctuations and thus the temporal changes of signal frequencies. This can affect both the amplitude and the frequency.
  • An example of jitter is the flaws that arise when converting analog signals into digital signals or when sequentially sampling signals through inaccurate or equal periodicity.
  • a fixed period is used in which the amplitude values are read out.
  • jitter errors arise due to differences or inaccuracies in the period duration, which results in falsified amplitude values, for example in the case of a sequential sampling of measurement signals.
  • the control circuit according to the invention for controlling the difference frequency f Dlff between two oscillators (17, 18) is shown, which overcomes the problem of different changes of the time bases in the control / evaluation unit 7 and the delay circuit 21.
  • the difference from the control circuits described above is that the control / evaluation unit 7 is clocked by means of the sampling signal S sampl provided at the first clock output 26 of the sampling clock oscillator 17 on the time base of the sampling frequency f Samp i.
  • the first clock output 26 of the sampling clock oscillator 17 via a clock line 24 to the clock input 25 of the control / evaluation unit 7 is electrically connected. Thanks to this structure can be dispensed with an external or internal processor oscillator 19, whereby a power-consuming component is saved.
  • control / evaluation unit 7 operates isochronous to the sampling clock oscillator 17, which is readjusted by this also in accordance with the determined difference frequency f Dlff via a control signal.
  • the Samp i due to external influences, such as by temperature changes or modulations of the supply voltage, or component-related statistical fluctuations, such a change in frequency affects equally the generation of the difference frequency f Dlff in the delay circuit 21 and the determination of the difference frequency f Dlff or Transformation factor k ⁇ in the control / evaluation unit 7 off.
  • the difference frequency f Dlff and the transformation factor k ⁇ is always determined correctly in the control / evaluation unit 7.
  • This Sendetaktoszillator 18 generating the pulse repetition frequency f PRF is usually executed as a highly stable clock or oscillator, since this as a reference clock for the exact determination of the distance d from the product of the transit time t and the propagation speed of the transmission signal S T ⁇ or reflection signals S RX used becomes.
  • Voltage controlled SAW oscillators VCSO - Voltage Controlled SAW Oscillators
  • Delay circuit 21 as well as by using a frequency-stable Sendetak- oscillator 18 with low jitter behavior, these properties have a positive effect on the performance, accuracy and reliability of the entire device 1 from.
  • a divider 22 or multiplier 23 can optionally be integrated into the clock line 24, which constantly changes the sampling frequency f Samp i according to a set ratio.
  • digital frequency converter digital mixer 13 analogue frequency converter, analogue mixer

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  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Thermal Sciences (AREA)
  • Fluid Mechanics (AREA)
  • General Physics & Mathematics (AREA)
  • Radar Systems Or Details Thereof (AREA)

Abstract

L'invention concerne un dispositif (1) servant à déterminer et à surveiller un niveau (e), lequel dispositif comporte une unité émettrice/réceptrice (2), un circuit de temporisation (21), constitué au moins d'un oscillateur d'horloge d'échantillonnage (17) produisant un signal d'échantillonnage (S<SUB>sampl</SUB>) à une fréquence d'échantillonnage (f<SUB>sampl</SUB>), d'un oscillateur d'horloge d'émission (18) produisant un signal de répétition (S<SUB>PRF</SUB>) à une fréquence de répétition des impulsions (f<SUB>PRF</SUB>) et d'un convertisseur de fréquence (11) produisant un signal différentiel (S<SUB>Diff</SUB>) par échantillonnage séquentiel, ainsi qu'une unité de régulation/d'évaluation (7) qui détermine le niveau (e) sur la base du temps de propagation. Selon la présente invention, une entrée d'horloge externe (25) est prévue sur l'unité de régulation/d'évaluation (7), laquelle entrée est reliée à une première sortie d'horloge (26) de l'oscillateur d'horloge d'échantillonnage (17) ou à une seconde sortie d'horloge (27) de l'oscillateur d'horloge d'émission (18) par l'intermédiaire d'une ligne d'horloge (24). L'objectif de cette invention est de fournir un circuit de régulation économique et stabilisé pour la production d'un signal à fréquence intermédiaire avec un coefficient de transformation pouvant être déterminé de manière très précise.
EP06793156A 2005-09-19 2006-09-01 Procede de mesure sur la base du temps de propagation pour determiner une distance Ceased EP1926974A2 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102005044724A DE102005044724A1 (de) 2005-09-19 2005-09-19 Laufzeitmessverfahren zur Ermittlung der Distanz
PCT/EP2006/065937 WO2007033897A2 (fr) 2005-09-19 2006-09-01 Procede de mesure sur la base du temps de propagation pour determiner une distance

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EP1926974A2 true EP1926974A2 (fr) 2008-06-04

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US (1) US8552744B2 (fr)
EP (1) EP1926974A2 (fr)
DE (1) DE102005044724A1 (fr)
WO (1) WO2007033897A2 (fr)

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* Cited by examiner, † Cited by third party
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CN107678275A (zh) * 2017-08-10 2018-02-09 深圳市海浦蒙特科技有限公司 用于吹膜机的变频器及其米克重控制方法

Families Citing this family (15)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE102010031276A1 (de) * 2010-07-13 2012-01-19 Endress + Hauser Gmbh + Co. Kg Füllstandsmessgerät zur Ermittlung und Überwachung eines Füllstandes eines im Prozessraum eines Behälters befindlichen Mediums mittels einem Mikrowellen-Laufzeitmessverfahren
DE102011007372B4 (de) * 2011-04-14 2023-05-04 Endress+Hauser SE+Co. KG Kalibrations- und/oder Überwachungsverfahren für FMCW-Radar Füllstandsmessgeräte
DE102011076838A1 (de) * 2011-05-31 2012-12-06 Endress + Hauser Flowtec Ag Meßgerät-Elektronik für ein Meßgerät-Gerät sowie damit gebildetes Meßgerät-Gerät
DE102011078060A1 (de) * 2011-06-24 2012-12-27 Endress + Hauser Gmbh + Co. Kg Vorrichtung zur Bestimmung oder Überwachung des Füllstandes eines Füllguts in einem Behälter
US9989628B2 (en) * 2012-06-29 2018-06-05 Rosemount Tank Radar Ab Pulsed level gauge system with temperature-based control of pulse repetition frequency
DE102013101103A1 (de) * 2012-12-27 2014-07-17 Endress + Hauser Gmbh + Co. Kg Verfahren zur Funktionsüberprüfung einer Messelektronik eines Feldgeräts der Prozessautomatisierungstechnik
DE102013114735A1 (de) * 2013-12-20 2015-06-25 Endress + Hauser Gmbh + Co. Kg PRF-Frequenzgenerator für ein Füllstandsmessgerät
CN106033002A (zh) * 2015-03-20 2016-10-19 唐山开诚电控设备集团有限公司 防爆高压变频器水冷系统液位检测装置
DE102016103740B3 (de) * 2016-03-02 2017-05-04 Endress+Hauser Gmbh+Co. Kg Verfahren zur Messung des Füllstands eines in einem Behälter befindlichen Füllgutes mittels Terahertz-Pulsen
TWI600884B (zh) * 2016-05-19 2017-10-01 博泰科技有限公司 具水量測量功能之杯具
DE102018123429A1 (de) * 2018-09-24 2020-03-26 Endress+Hauser SE+Co. KG Füllstandsmessgerät
DE102018127012A1 (de) * 2018-10-30 2020-04-30 Endress+Hauser SE+Co. KG Füllstandsmessgerät
EP3899455A1 (fr) * 2018-12-19 2021-10-27 Rosemount Tank Radar AB Test d'épreuve de système de jauge de niveau radar
DE102019101598A1 (de) * 2019-01-23 2020-07-23 Endress+Hauser SE+Co. KG Messgerät zur Bestimmung eines Dielektrizitätswertes
TWI789853B (zh) * 2021-07-29 2023-01-11 立積電子股份有限公司 雷達裝置及干擾抑制方法

Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE29815069U1 (de) * 1998-08-25 1998-12-24 Vega Grieshaber Kg, 77709 Wolfach Sampling-Schaltung zur Abtastung von Hochfrequenzsignalpulsen für die Verwendung in TDR-Füllstandssensoren

Family Cites Families (17)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE3107444C2 (de) * 1981-02-27 1984-01-12 Dornier System Gmbh, 7990 Friedrichshafen Hochauflösendes kohärentes Pulsradar
DE4218303C1 (de) * 1992-06-03 1994-03-03 Endress Hauser Gmbh Co Verfahren und Anordnung zur Abstandsmessung nach dem Impulslaufzeitprinzip
US5537121A (en) * 1995-04-28 1996-07-16 Trimble Navigation Limited Carrier phase multipath reduction technique
US5563605A (en) * 1995-08-02 1996-10-08 The Regents Of The University Of California Precision digital pulse phase generator
US5841666A (en) 1995-12-21 1998-11-24 Endress + Hauser Gmbh + Co. Processor apparatus and method for a process measurement signal
US6559657B1 (en) * 1999-01-13 2003-05-06 Endress+Hauser Gmbh+Co. Probe mapping diagnostic methods
US6373428B1 (en) * 1999-04-01 2002-04-16 Mcewan Technologies, Llc Self locking dual frequency clock system
DE19949992C2 (de) * 1999-10-15 2002-08-29 Endress & Hauser Gmbh & Co Kg Verfahren zur Erhöhung der Störfestigkeit eines Zeitbereichsreflektometers
US6679115B2 (en) * 2001-02-14 2004-01-20 Endress + Hauser Gmbh + Co. Apparatus for determining the filling level of a product in a container
US6868357B2 (en) * 2001-07-07 2005-03-15 Cynthia M. Furse Frequency domain reflectometry system for testing wires and cables utilizing in-situ connectors, passive connectivity, cable fray detection, and live wire testing
US6608489B2 (en) * 2001-12-17 2003-08-19 The United States Of America As Represented By The Secretary Of The Army Device, and method of its use, for concurrent real time alerting to accumulation of material upon multiple areas of a surface
US6628229B1 (en) * 2002-08-01 2003-09-30 Rosemount Inc. Stabilization of oscillators in a radar level transmitter
DE10252091A1 (de) * 2002-11-08 2004-05-19 Siemens Ag Verfahren und Anordnung für multistatische Nachdistanzradarmessungen
US7135873B2 (en) * 2003-09-05 2006-11-14 Psibor Date Systems, Inc. Digital time domain reflectometer system
EP1562051B1 (fr) * 2004-02-04 2012-08-29 VEGA Grieshaber KG Procédé pour déterminer un niveau de matériel avec une capteur radar à deux fils
CA2511112A1 (fr) 2004-06-30 2005-12-30 Her Majesty The Queen In Right Of Canada, As Represented By The Minister Of National Research Council Of Canada Synthese de copolymeres de polyarylenes contenant des chaines laterales de groupes acide sulfonique pendants et lies a une molecule de naphtalene, pouvant servir de materiaux de membrane echangeuse de protons
DE102006019191A1 (de) * 2006-04-21 2007-10-25 Endress + Hauser Gmbh + Co. Kg Verfahren zur Ermittlung und Überwachung des Füllstands eines Mediums in einem Behälter

Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE29815069U1 (de) * 1998-08-25 1998-12-24 Vega Grieshaber Kg, 77709 Wolfach Sampling-Schaltung zur Abtastung von Hochfrequenzsignalpulsen für die Verwendung in TDR-Füllstandssensoren

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN107678274A (zh) * 2017-08-10 2018-02-09 深圳市海浦蒙特科技有限公司 用于皮带秤的变频器及其定量给料控制方法
CN107678275A (zh) * 2017-08-10 2018-02-09 深圳市海浦蒙特科技有限公司 用于吹膜机的变频器及其米克重控制方法

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US8552744B2 (en) 2013-10-08
WO2007033897A3 (fr) 2007-05-18

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