EP1524722B1 - Substrat pour antenne hélicoidale et procédé de fabrication de celle-ci - Google Patents

Substrat pour antenne hélicoidale et procédé de fabrication de celle-ci Download PDF

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Publication number
EP1524722B1
EP1524722B1 EP04078530A EP04078530A EP1524722B1 EP 1524722 B1 EP1524722 B1 EP 1524722B1 EP 04078530 A EP04078530 A EP 04078530A EP 04078530 A EP04078530 A EP 04078530A EP 1524722 B1 EP1524722 B1 EP 1524722B1
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EP
European Patent Office
Prior art keywords
antenna
substrate
ground plane
support element
radiator
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Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
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EP04078530A
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German (de)
English (en)
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EP1524722A1 (fr
Inventor
Daniel Filipovic
Ali Tassoudji
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Qualcomm Inc
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Qualcomm Inc
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q11/00—Electrically-long antennas having dimensions more than twice the shortest operating wavelength and consisting of conductive active radiating elements
    • H01Q11/02—Non-resonant antennas, e.g. travelling-wave antenna
    • H01Q11/08—Helical antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/362—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith for broadside radiating helical antennas

Definitions

  • the present invention relates to an antenna and to a feed network for an antenna. More specifically, the present invention relates to a method of manufacturing a helical antenna.
  • Contemporary personal communication devices are enjoying widespread use in numerous mobile and portable applications.
  • the desire to minimize the size of the communication device has led to a moderate level of downsizing.
  • the portable, hand-held applications increase in popularity, the demand for smaller and smaller devices has increased dramatically.
  • Recent developments in processor technology, battery technology and communications technology have enabled the size and weight of the portable device to be reduced drastically over the past several years.
  • the size and weight of the antenna play an important role in downsizing the communication device.
  • the overall size of the antenna can impact the size of the device's body. Smaller diameter and shorter length antennas can allow smaller overall device sizes as well as smaller body sizes.
  • Size of the device is not the only factor that needs to be considered in designing antennas for portable applications. Another factor to be considered in designing antennas is attenuation and/or blockage effects resulting from the proximity of the user's head to the antenna during normal operations. Yet another factor is the characteristics of the communication link, such as, for example, desired radiation patterns and operating frequencies.
  • helical antenna An antenna that finds widespread usage in satellite communication systems is the helical antenna.
  • One reason for the helical antenna's popularity in satellite communication systems is its ability to produce and receive circularly-polarized radiation employed in such systems. Additionally, because the helical antenna is capable of producing a radiation pattern that is nearly hemispherical, the helical antenna is particularly well suited to applications in mobile satellite communication systems and in satellite navigational systems.
  • a common helical antenna is the quadrifilar helical antenna which utilizes four radiators spaced equally around a core and excited in phase quadrature (i.e., the radiators are excited by signals that differ in phase by one-quarter of a period or 90°).
  • the length of the radiators is typically an integer multiple of the quarter wavelength of the operating frequency of the communication device.
  • the radiation patterns are typically adjusted by varying the pitch of the radiator, the length of the radiator (in integer multiples of a quarter-wavelength), and the diameter of the core.
  • radiators of the antenna can be made using wire or strip technology.
  • strip technology the radiators of the antenna are etched or deposited onto a thin, flexible substrate.
  • the radiators are positioned such that they are parallel to each other, but at an obtuse angle to the sides (or edges) of the substrate.
  • the substrate is then formed, or rolled, into a cylindrical, conical, or other appropriate shape causing the strip radiators to form a helix.
  • This conventional helical antenna also has the characteristic that the radiator lengths are an integer multiple of one quarter wavelength of the desired resonant frequency, resulting in an overall antenna length that is longer than desired for some portable or mobile applications.
  • dual-band antennas are desirable.
  • dual-band antennas are often available only in less than desirable configurations.
  • one way in which a dual band antenna can be made is to stack two single-band quadrifilar helix antennas end-to-end, so that they form a single cylinder.
  • a disadvantage of this solution, however, is that such an antenna is longer than would otherwise be desired for portable, or hand-held applications.
  • Another technique for providing dual-band performance has been to utilize two separate single band antennas.
  • the two antennas would have to be located in close proximity to one another.
  • Two single band antennas, placed in dose proximity on a portable, or hand-held unit would cause coupling between the two antennas, leading to degraded performance as well as unwanted interference.
  • a feed network of the antenna may be implemented with a dual-band helical antenna having two sets of one or more helically wound radiators.
  • the radiators are wound, or wrapped, such that the antenna is in a cylindrical, conical, or other appropriate shape to optimize or otherwise obtain desired radiation patterns.
  • one set of radiators is provided for operation at a first frequency and the second set is provided for operation at a second frequency which preferably is different from the first frequency.
  • Each set of radiators has an associated feed network to provide the signals to drive the radiators.
  • the dual-band antenna can be described as being comprised of two single-band antennas, each single-band antenna having a radiator portion and a feed portion.
  • a tab can be provided to feed the signal to the first single-band antenna.
  • the tab extends from the feed portion of the first single-band antenna.
  • the tab is aligned with the axis of the antenna. More specifically, in a preferred embodiment, the tab extends radially inward to provide a centrally located feed structure. Thus, the tab and the feed line do not interfere with the signal patterns of the second single-band antenna.
  • the present invention is directed toward an area-efficient feed network for an antenna.
  • a portion of the feed network is provided on a radiator portion of the antenna. This decreases the area required for the feed portion of the antenna.
  • the invention can be implemented in any system for which helical antenna technology can be utilized.
  • a communication system in which users having fixed, mobile and/or portable telephones communicate with other parties through a satellite communication link.
  • the telephone is required to have an antenna tuned to the frequency satellite communication link.
  • FIGS. 1 A and 1 B are diagrams illustrating a radiator portion 100 of a conventional quadrifilar helical antenna in wire form and in strip form, respectively.
  • the radiator portion 100 illustrated in FIGS. 1 A and 1 B is that of a quadrifilar helical antenna, meaning it has four radiators 104 operating in phase quadrature.
  • radiators 104 are wound to provide circular polarization.
  • FIGS. 2 A and 2 B are diagrams illustrating planar representations of a radiator portion of conventional quadrifilar helical antennas.
  • FIGS. 2 A and 2 B illustrate the radiators as they would appear if the antenna cylinder were "unrolled" on a flat surface.
  • FIG. 2 A is a diagram illustrating a quadrifilar helical antenna which is open-circuited, or open terminated, at the far end.
  • the resonant length l of the radiators 208 is an odd integer multiple of a quarter-wavelength of the desired resonant frequency.
  • FIG. 2 B is a diagram illustrating a quadrifilar helical antenna which is short-circuited, or electrically connected, at the far end.
  • the resonant length l of radiators 208 is an even integer multiple of a quarter wavelength of the desired resonant frequency. Note that in both cases, the stated resonant length l is approximate, because a small adjustment is usually needed to compensate for non-ideal short and open terminations.
  • the strip quadrifilar helical antenna is comprised of strip radiators 104 A- 104 D etched onto a dielectric substrate 406 .
  • the substrate is a thin flexible material that is rolled into a cylindrical, conical or other appropriate shape such that radiators 104 A- 104 D are helically wound about a central axis of the cylinder.
  • FIGS. 4 - 6 illustrate the components used to fabricate a quadrifilar helical antenna 100 .
  • FIGS. 4 and 5 present a view of a far surface 400 and near surface 500 of substrate 406 , respectively.
  • the antenna 100 includes a radiator portion 404 , and a feed portion 408 .
  • the antennas are described as being made by forming the substrate into a cylindrical shape with the near surface being on the outer surface of the formed cylinder.
  • the substrate is formed into the cylindrical shape with the far surface being on the outer surface of the cylinder.
  • dielectric substrate 100 is a thin, flexible layer of polytetraflouroethalene (PTFE), a PTFE/glass composite, or other dielectric material.
  • substrate 406 is on the order of 0.005 in., or 0.13 mm thick, although other thicknesses can be chosen.
  • Signal traces and ground traces are provided using copper. In alternative embodiments, other conducting materials can be chosen in place of copper depending on cost, environmental considerations and other factors.
  • feed network 508 is etched onto feed portion 408 to provide the quadrature phase signals (i.e., the 0°, 90°, 180° and 270° signals) that are provided to radiators 104 A- 104 D.
  • Feed portion 408 of far surface 400 provides a ground plane 412 for feed circuit 508.
  • Signal traces for feed circuit 508 are etched onto near surface 500 of feed portion 408 .
  • radiator portion 404 has a first end 432 adjacent to feed portion 408 and a second end 434 (on the opposite end of radiator portion 404 ).
  • radiators 104 A- 104 D can be etched into far surface 400 of radiator portion 404 .
  • the length at which radiators 104 A- 104 D extend from first end 432 toward second end 434 is approximately an integer multiple of a quarter wavelength of the desired resonant frequency.
  • radiators 104 A- 104 D are an integer multiple of ⁇ /2
  • radiators 104 A- 104 D are electrically connected to each other (i.e., shorted, or short circuited) at second end 434 .
  • This connection can be made by a conductor across second end 434 which forms a ring 604 around the circumference of the antenna when the substrate is formed into a cylinder.
  • FIG. 6 is a diagram illustrating a perspective view of an etched substrate of a strip helical antenna having a shorting ring 604 at second end 434 .
  • the antenna described in the '831 patent is a printed circuit-board antenna having the antenna radiators etched or otherwise deposited on a dielectric substrate. The substrate is formed into a cylinder resulting in a helical configuration of the radiators.
  • U.S. Patent No. 5,255,005 to Terret et al referred to as the '005 patent.
  • the antenna described in the '005 patent is a quadrifilar helical antenna formed by two bifilar helices positioned orthogonally and excited in phase quadrature.
  • the disclosed antenna also has a second quadrifilar helix that is coaxial and electromagnetically coupled with the first helix to improve the passband of the antenna.
  • one form of helical antenna utilizes coupled multi-segment radiators that allow for resonance at a given frequency at shorter lengths than would otherwise be needed for a helical antenna with an equivalent resonant length.
  • FIGS. 7 A and 7 B are diagrams illustrating planar representations of example embodiments of coupled-segment helical antennas.
  • FIG. 7 A illustrates a coupled multi-segment radiator 706 terminated in an open-circuit according to one single-filar embodiment.
  • An antenna terminated in an open-circuit such as this may be used in a single-filar, bifilar, quadrifilar, or other x-filar implementation.
  • the embodiment illustrated in FIG. 7 A is comprised of a single radiator 706 .
  • End segments 708 , 710 are physically separate from but electromagnetically coupled to one another.
  • Intermediate segments 712 are positioned between end segments 708 , 710 and provide electromagnetic coupling between end segments 708 , 710 .
  • the length l s1 of segment 708 is an odd-integer multiple of one-quarter wavelength of the desired resonant frequency.
  • the length l s2 of segment 710 is an integer multiple of one-half the wavelength of the desired resonant frequency.
  • FIG. 7 B illustrates radiators 706 of the helical antenna when terminated in a short circuit 722 .
  • This short-circuited implementation is not suitable for a single-filar antenna, but can be used for bifilar, quadrifilar or other x-filar antennas.
  • End segments 708 , 710 are physically separate from but electromagnetically coupled to one another.
  • Intermediate segments 712 are positioned between end segments 708 , 710 and provide electromagnetic coupling between end segments 708 , 710 .
  • the length l s1 of segment 708 is an odd-integer multiple of one-quarter wavelength of the desired resonant frequency.
  • the length l s2 of segment 710 is an odd-integer multiple of one-quarter wavelength of the desired resonant frequency.
  • FIGS. 8 A and 8 B are diagrams illustrating a coupled multi-segment quadrifilar helical antenna radiator portion 800 according to one embodiment of the invention.
  • the radiator portion 800 illustrated in FIG. 8 A is a planar representation of a quadrifilar helical antenna, having four coupled radiators 804 .
  • Each coupled radiator 804 in the coupled antenna is actually comprised of two radiator segments 708 , 710 positioned in close proximity with one another such that the energy in radiator segment 708 is coupled to the other radiator segment 710 .
  • radiator portion 800 can be described in terms of having two sections 820 , 824 .
  • Section 820 is comprised of a plurality of radiator segments 708 extending from a first end 832 of the radiator portion 800 toward the second end 834 of radiator portion 800 .
  • Section 824 is comprised of a second plurality of radiator segments 710 extending from second end 834 of the radiator portion 800 toward first end 832 .
  • Toward the center area of radiator portion 800 a part of each segment 708 is in close proximity to an adjacent segment 710 such that energy from one segment is coupled into the adjacent segment in the area of proximity. This is referred to in this document as overlap.
  • the overall length of a single radiator comprising two segments 708 , 710 is defined as l tot .
  • the overall length of a radiator l tot is less than the half-wavelength length of ⁇ /2 .
  • radiator portions 800 illustrated in FIG 8 For a clearer illustration of the reduction in size gained by using the coupled configuration, compare the radiator portions 800 illustrated in FIG 8 with those illustrated in FIG. 3 .
  • the length l of radiator portion 300 of the conventional antenna is ⁇ /2
  • the length l tot of radiator portion 800 of the coupled radiator segment antenna is less than ⁇ /2 .
  • the length of each segment can be varied such that l 1 is not necessarily equal to l 2 , and such that they are not equal to ⁇ /4 .
  • the actual resonant frequency of each radiator is a function of the length of radiator segments 708 , 710 the separation distance s between radiator segments 708 , 710 and the amount by which segments 708 , 710 overlap each other.
  • lengthening l 1 such that it is slightly greater than ⁇ /4 and shortening l 2 such that it is slightly shorter than ⁇ /4 can increase the bandwidth of the antenna.
  • FIG. 8 B illustrates the actual helical configuration of a coupled multi-segment quadrifilar helical antenna according to one embodiment of the invention. This illustrates how each radiator is comprised of two segments 708 , 710 in one embodiment. Segment 708 extends in a helical fashion from first end 832 of the radiator portion toward second end 834 of the radiator portion. Segment 710 extends in a helical fashion from second end 834 of the radiator portion toward first end 832 of the radiator portion. FIG. 8 B further illustrates that a portion of segments 708 , 710 overlap such that they are electromagnetically coupled to one another.
  • FIG. 9 A is a diagram illustrating the separation s and overlap ⁇ between radiator segments 708 , 710 . Separation s is chosen such that a sufficient amount of energy is coupled between the radiator segments 708 , 710 to allow them to function as a single radiator of an effective electrical length of approximately ⁇ /2 and integer multiples thereof.
  • radiator segments 708 , 710 closer than this optimum spacing results in greater coupling between segments 708 , 710 .
  • the length of segments 708 , 710 must increase to enable resonance at the same frequency f .
  • the total length of segments 708 , 710 must equal ⁇ /2 for the antenna to resonate. Note that in this extreme case, the antenna is no longer really 'coupled' according to the usage of the term in this specification, and the resulting configuration is actually that of a conventional helical antenna such as that illustrated in FIG. 3 .
  • FIG. 9 B represents a magnitude of the current on each segment 708 , 710 .
  • Current strength indicators 911 , 928 illustrate that each segment ideally resonates at ⁇ /4 , with the maximum signal strength at the outer ends and the minimum at the inner ends.
  • AO Antenna Optimizer
  • FIG. 10 A is a diagram illustrating two point sources, A, B, where source A is radiating a signal having a magnitude equal to that of the signal of source B but lagging in phase by 90° (the e j ⁇ t convention is assumed).
  • sources A and B are separated by a distance of ⁇ /4 , the signals add in phase in the direction traveling from A to B and add out of phase in the direction from B to A. As a result, very little radiation is emitted in the direction from B to A.
  • a typical representative field pattern shown in FIG. 10 B illustrates this point.
  • the antenna is optimized for most applications. This is because it is rare that a user desires an antenna that directs signal strength toward the ground. This configuration is especially useful for satellite communications where it is desired that the majority of the signal strength be directed upward, away from the ground.
  • the point source antenna modeled in FIG.10A is not readily achievable using conventional half wavelength helical antennas.
  • the concentration of current strength at the ends of radiators 208 roughly approximates a point source.
  • radiators are twisted into a helical configuration, one end of the 90° radiator is positioned in line with the other end of the 0° radiator.
  • this approximates two point sources in a line.
  • these approximate point sources are separated by approximately ⁇ /2 as opposed to the desired ⁇ /4 configuration illustrated in FIG. 10 A.
  • the coupled radiator segment antenna embodying the invention provides an implementation where the approximated point sources are spaced at a distance closer to ⁇ /4 . Therefore, the coupled radiator segment antenna allows users to capitalize on the directional characteristics of the antenna illustrated in FIG. 10 A.
  • each segment 710 illustrated in FIG. 8 show that segment 708 is very near its associated segment 710 , yet each pair of segments 708 , 710 are relatively far from the adjacent pair of segments.
  • each segment 710 is placed equidistant from the segments 708 on either side. This embodiment is illustrated in FIG. 11 .
  • each segment is substantially equidistant from each pair of adjacent segments.
  • segment 710 A is equidistant from segments 708 A, 708 B.
  • This embodiment is counterintuitive in that it appears as if unwanted coupling would exist.
  • a segment corresponding to one phase would couple not only to the appropriate segment of the same phase, but also to the adjacent segment of the shifted phase.
  • segment 708 B the 90° segment would couple to segment 710 A (the 0° segment) and to segment 710 B (the 90° segment).
  • Such coupling is not a problem because the radiation from the top segments 710 can be thought of as two separate modes. One mode resulting from coupling to adjacent segments to the left and the other mode from coupling to adjacent segments to the right. However, both of these modes are phased to provide radiation in the same direction. Therefore, this double-coupling is not detrimental to the operation of the coupled multi-segment antenna.
  • FIG. 12 is a diagram illustrating an example implementation of a coupled radiator segment antenna.
  • the antenna comprises a radiator portion 1202 and a feed portion 1206 .
  • Radiator portion includes segments 708 , 710 .
  • Dimensions provided in FIG. 12 illustrate the contribution of segments 708 , 710 and the amount of overlap ⁇ to the overall length of radiator portion 1202 .
  • the length of segments in a direction parallel to the axis of the cylinder is illustrated as l 1 sin ⁇ for segments 708 and l 2 sin ⁇ for segments 710 , where ⁇ is the inside angle of segments 708 , 710 .
  • Segment overlap as illustrated above in FIGS. 8 A and 9 A is illustrated by the reference character ⁇ .
  • the amount of overlap in a direction parallel to the axis of the antenna is given by ⁇ sin ⁇ , as illustrated in FIG. 12 .
  • Segments 708, 710 are separated by a spacing s, which can vary as described above.
  • the distance between the end of a segment 708, 710 and the end of radiator portion 1202 is defined as the gap and illustrated by the reference characters ⁇ 1 , ⁇ 2 , respectively.
  • the gaps ⁇ 1 , ⁇ 2 can, but do not have to be, equal to each other.
  • the length of segments 708 can be varied with respect to that of segments 710 .
  • the amount of offset of a segment 710 from one end to the next is illustrated by the reference character ⁇ 0 .
  • the separation between adjacent segments 710 is illustrated by the reference character ( ⁇ s , and is determined by the helix diameter.
  • Feed portion 1206 includes an appropriate feed network to provide the quadrature phase signals to the radiator segments 708 .
  • Feed networks are well known to those of ordinary skill in the art and are thus not described in detail herein.
  • segments 708 are fed at a feed point that is positioned along each segment 708 a distance from the feed network that is chosen to optimize impedance matching. In the embodiment illustrated in FIG. 12 , this distance is illustrated by the reference characters ⁇ feed .
  • continuous line 1224 illustrates the border for a ground portion on the far surface of the substrate.
  • the ground portion opposite segments 708 on the far surface extends to the feed point.
  • the thin portion of segments 708 is on the near surface. At the feed point, the thickness of segments 708 on the near surface increases.
  • the overall length of radiator portion 1202 in the example L-Band embodiment is 2.30 inches (58.4 mm).
  • the pitch angle ⁇ is 73 degrees.
  • the length of segments 708 l 1 sin ⁇ for this embodiment is 1.73 inches (43.9 mm).
  • the length of segments 710 is equal to the length of segments 708 .
  • segment 710 is positioned substantially equidistant from its adjacent pair of segments 708 .
  • Other spacings are possible including, for example, the spacing s of segments 710 at 0.070 inches (1.8 mm) from an adjacent segment 708 .
  • radiator segments 708, 710 is 0.11 inches (2.8 mm) in this embodiment. Other widths are possible.
  • the segment offset ⁇ 0 is 0.53 inches and the segment separation ⁇ s is 0.393 inches (10.0 mm).
  • the diameter of the antenna is 4 ⁇ s / ⁇ .
  • Other feed points can be chosen to optimize impedance matching.
  • the overall length of the L-Band antenna radiator portion is reduced from that of a conventional half-wavelength L-Band antenna.
  • the length of the radiator portion is approximately 3.2 inches (i.e., ⁇ /2 (sin ⁇ )), where ⁇ is the inside angle of segments 708, 710 with respect to the horizontal), or (81.3 mm).
  • the overall length of the radiator portion 1202 is 2.3 inches (58.42 mm). This represents a substantial savings in size over the conventional antenna.
  • the present invention is directed toward a dual-band helical antenna capable of resonating at two different operating frequencies.
  • Two helical antennas are stacked end to end, with one antenna resonating at a first frequency and the other antenna resonating at a second frequency.
  • Each antenna has a radiator portion comprised of one or more helically-wound radiators.
  • Each antenna also has a feed portion comprised of a feed network and a ground plane. The two antennas are stacked such that the ground plane of one antenna is used as a shorting ring across the far end of the radiators of the other antenna.
  • FIG. 13 is a diagram illustrating planar representations of far surface 400 and near surface 500 of a dual-band helical antenna according to one embodiment of the invention.
  • the dual-band helical antenna is comprised of two single-band helical antennas: helical antenna 1304 operating at a first resonant frequency and helical antenna 1308 operating at a second resonant frequency.
  • feed network 508 , radiators 104 A- 104 D and first antenna 1304 are disposed on near surface 500 of first antenna 1304 . Also disposed on near surface 500 is the ground plane 412 for the feed network 508 of second antenna 1308 . On far surface 400 are feed network 508 and radiators 104 A- 104 D of second antenna 1308 as well as ground plane 412 for the feed portion of first antenna 1304 .
  • radiators 104 A- 104 D are an even integer multiple of a quarter-wavelength of the desired resonant frequency
  • the far end of the radiators 104 A- 104 D is shorted. As illustrated in FIG. 13 , this shorting is accomplished using ground plane 412 of first antenna 1304 . As a result of this configuration, an additional shorting ring does not need to be added to the end of radiators 104 A- 104 D.
  • first antenna 1304 is illustrated as resonating at odd integer multiples of a quarter-wavelength of the desired resonant frequency because the ends of radiators 104 A- 104 D are open circuited.
  • a shorting ring (not illustrated) could be added to the far end of radiators 104 A- 104 D of first antenna 1304 , while changing the length of these radiators 104 A- 104 D such that they are an even-integer multiple of a quarter-wavelength of the desired resonant frequency.
  • FIG. 14 is a diagram illustrating one embodiment of a dual-band helical antenna in which the feed points of radiators 104 A- 104 D are positioned at a predetermined distance from feed network 508 .
  • a feed point A of first antenna 1304 is positioned at a distance l FEED1 from feed network 508 and feed point B of second antenna 1308 is positioned at a distance l FEED2 from feed network 508 .
  • radiators 104 A- 104 D are comprised of a ground trace 1436 on a first surface of the substrate 406 , a feed trace 1438 on a second surface of substrate 406 and opposite said ground trace 1436 , and a radiator trace 1440 on the second surface of substrate 406 .
  • ground plane 412 of first antenna 1304 serves as a shorting ring for radiators 104 A- 104 D and second antenna 1308 such that the radiators of second antenna 1308 resonate at an even integer multiple of a quarter-wavelength of the desired resonant frequency.
  • radiators 104 A- 104 D of first antenna 1304 and/or second antenna 1308 as illustrated in FIGS. 13 and 14 are replaced with edge-coupled radiators as illustrated, for example, in FIG. 12 .
  • first antenna 1304 is fed by means of a tab extending from the lower area of the feed portion of first antenna 1304 .
  • FIG. 15 is a diagram illustrating such a tab used to feed first antenna 1304 .
  • a tab 1504 extends from the side of the feed portion of first antenna 1304 on substrate 406 .
  • tab 1504 is approximately "L" shaped such that it extends horizontally from the feed portion of first antenna 1304 at a given distance and is then angled axially through the center in the direction of the feed portion of second antenna 1308 .
  • 1504 is illustrated as being shaped with a right angle, other angles could be used as could curves of various radii.
  • axial component 1524 of tab 1504 is substantially along the axis of the dual-band helical antenna. Having axial component 1524 of tab 1504 coincident with the axis of the helical antenna minimizes the impact of this member on the radiation patterns of the antenna. As illustrated in FIG. 15 , in a preferred embodiment, tab 1504 extends from feed portion of first antenna 1304 at a vertical position that is as far as possible from first antenna 1304 . This is done to minimize the effect of tab 1504 on the radiation patterns of first antenna 1304 .
  • second antenna 1308 is a coupled-segment one-half wavelength antenna and the ends of radiators 104 A- 104 D of second antenna 1308 are shorted by ground plane 412 of first antenna 1304 , tab 1504 has a minimal effect on the radiation patterns of second antenna 1308 .
  • the length l gp of feed portion 1206 of first antenna 1304 can be determined by considering two factors at the appropriate operating frequency. First, it is desirable to minimize the amount of current flowing from the radiators of first antenna 1304 to second antenna 1308 , and vice versa. In other words, it is desirable to achieve isolation between the two antennas. This can be accomplished by ensuring that the length is great enough such that the currents do not extend form one set of radiators to the other at the frequency of interest.
  • Another challenge is the goal of not allowing current from radiators 104 A-D of first antenna 1304 from reaching tab 1504 .
  • Currents from first antenna 1304 are attenuated as they travel across the feed portion of first antenna 1304 toward tab 1504 .
  • Tab 1504 creates an asymmetrical discontinuity in these currents. Therefore, it is desired to minimize the magnitude of the currents reaching tab 1504 to the extent practical.
  • feed portion 1206 of appropriate length l gp based on the materials used, the frequencies of interest, the expected power levels in the antenna, and other known factors. This decision may also entail a tradeoff between size and performance.
  • tab 1504 is not non-existent in this embodiment. Because tab 1504 is close to the radiators of second antenna 1308 , some current from second antenna 1308 is coupled into tab 1504 , and, therefore, along the axis of the antenna. This current affects the radiation of second antenna 1308 , resulting in increased radiation to the sides of the antenna. For applications where the antenna is mounted vertically, this results in increased radiation in the direction of the horizon and decreased radiation in the vertical direction. As a result, this application is well-suited for satellite communication systems where low-earth-orbiting satellites are used to relay communications from or to the communication device.
  • circular polarization radiation pattern 1010 is a representation of a typical radiation pattern for a conventional helical antenna
  • radiation pattern 1020 is a representation of a radiation pattern for second antenna 1308 .
  • pattern 1020 is "flatter” and "wider” than conventional pattern 1010 .
  • tab 1504 includes a connector such as a crimp or solder connector or other connector suitable for making a connection between a feed cable and the signal trace on tab 1504 .
  • a connector such as a crimp or solder connector or other connector suitable for making a connection between a feed cable and the signal trace on tab 1504 .
  • Various types of cable or wire can be used to connect transceiver RF circuitry to the antenna at tab 1504 .
  • a low loss flexible or semi-rigid cable is utilized.
  • the radiation patterns will still be symmetric, only their gains will be lowered by the corresponding amount of reflection loss.
  • it is also important that the connector provide a sturdy mechanical connection between the cable and tab 1504 .
  • FIG. 15 Also illustrated in FIG. 15 is the outline for an example substrate shape. After reading this description, it will become apparent to a person skilled in the art how to implement the antenna with a tab 1504 utilizing substrates having other shapes.
  • FIG. 16 is a diagram illustrating one embodiment of a stacked antenna with example dimensions.
  • first antenna 1304 is an L-band antenna and second antenna 1308 is an S-band antenna.
  • S-band antenna 1308 is an edge-coupled antenna wherein each radiator 104 is comprised of two segments. Note that this embodiment is provided for example only. Alternative frequency bands can be chosen for operation. Also note that either first antenna 1304 or second antenna 1308 or both could utilize the edge-coupled technology.
  • the radiating aperture of the L-band antenna is a total axial height of 1.253 inches, while the S-band aperture is a total height of 1.400 inches.
  • the height of feed portion 412 of first antenna 1304 is 0.400 inches. This yields a total radiating aperture of 3.093 inches.
  • the inclination angle of radiators 104 A- 104 D is 65°.
  • the overall length of radiators 104 A- 104 D determines the precise resonating frequency of the antenna.
  • the resonating frequency is important because the highest average gains and the most symmetric patterns occur at the resonant frequency. If the antenna is made longer, the resonating frequency shifts down. Conversely, if the antenna is made shorter, the resonating frequency shifts up.
  • the percentage of the frequency shift is approximately proportional to the percentage that the radiators 104 A- 104 D are lengthened or shortened. At L-band operating frequencies, roughly 1 mm of length in the direction of the antenna axis corresponds to 1 MHz.
  • both first antenna 1304 and second antenna 1308 have four excited filar arms, or radiators 104 A- 104 D. Each of these radiators 104 A- 104 D are fed in phase quadrature.
  • the quadrature phase excitation of four radiators 104 A- 104 D for each antenna 1304 , 1308 is implemented using a feed network. While conventional feed networks capable of providing quadrature phase excitation can be implemented, a preferred feed network is discussed in detail below.
  • the feedpoint axial length defines the distance of the feedpoint from the feed network for embodiments where the feedpoint is positioned along radiators 104 A- 104 D as illustrated in FIG. 13 .
  • the feedpoint axial length dimension indicates the position at which the microstrip flares out to continue the radiator and is actually the feedpoint position for the entire radiator 104 .
  • the feedpoint length for first antenna 1304 is 1.133 inches.
  • the feedpoint length for second antenna 1308 is 0.638 inches.
  • the feedpoint position is shifted higher, the impedance is higher. It is important to note that when the overall radiator length is being adjusted to tune the frequency, the feedpoint position should also be shifted by a proportional amount in the direction along the axis of the antenna to maintain the correct impedance match.
  • the antenna having dimensions as illustrated in FIG. 16 is rolled into a cylinder having a diameter of 0.500 inches.
  • the helical antennas described in this document can be implemented using a mono-filar, quadrifilar, octafilar or other x-filar configuration.
  • a feed network is utilized to provide the signals to the filars at the necessary phase angle.
  • the feed network splits the signal and shifts the phase provided to each filar.
  • the configuration of the feed network is dependent on the number of filars. For example, for a quadrifilar helical antenna, the feed network provides four equal-power signals in a quadrature phase relationship (i.e., 0, 90, 180, and 270 degrees).
  • the traces of the feed network extend into one or more radiators 104 A- 104 D of the antenna.
  • the feed network is described in terms of a feed network designed to provide four equal-power signals in a quadrature phase relationship. After reading this description, it will become apparent to a person skilled in the relevant art how to implement the feed network for other x-filar configurations.
  • FIG. 17 illustrates the electrical equivalent of a conventional quadrature phase feed network.
  • the network provides four equal-power signals, each separated in phase by 90 degrees.
  • the signal is provided to the feed network via a first signal path 1704 .
  • a first signal point A (referred to as a secondary feed point)
  • the 0-degree phase signal is provided to a first radiator 104 .
  • the 90-degree phase signal is provided to a second radiator 104 .
  • the 180- and 270-degree phase signals are provided to third and fourth radiators 104 .
  • Signals A and B are combined at a point P2 to yield a 25-ohm impedance.
  • signals C and D are combined at a point P3 to yield a 25-ohm impedance.
  • These signals are combined at P1 to yield a 12.5-ohm impedance. Therefore, a 25-ohm, 90-degree transformer is placed at the input to convert this impedance to 50-ohms. Note that in the network illustrated in FIG. 17 , part of the transformer is placed before the P1 split to shorten the feed and also to decrease losses. However, because it is before the split, it must be twice the impedance after the split.
  • the conventional feed network is modified such that the traces of the feed network are disposed on portions of the substrate defined for radiators 104 A- 104 D. Specifically, in a preferred embodiment, these traces are disposed on the substrate in an area which is opposite from the ground traces of the one or more of the radiators 104 A- 104 D.
  • FIG. 18 is a diagram illustrating an example embodiment of the feed network in a quadrifilar helical antenna environment. Specifically, in the example illustrated in FIG. 18 , two feed networks are illustrated: a first feed network 1804 for implementation with first antenna 1304 ; and a second feed network 1808 for implementation with second antenna 1308 .
  • Feed networks 1804 , 1808 have points A, B, C, and D, for providing the 0, 90, 180, and 270-degree signals to radiators 104 A- 104 D.
  • the dashed lines provided on FIG. 18 approximately illustrate an outline for the ground plane of radiators 104 A- 104 D on a surface of the substrate opposite the surface on which feed networks 1804, 1808 are disposed.
  • FIG. 18 illustrates those portions of feed networks 1804, 1808 which are disposed on, or extend into, radiators 104 A- 104 D.
  • the feed network is provided on an area that is designated for the feed network and that is separate from the radiators.
  • the feed network described herein is laid out such that a portion of the feed network is deposited on the radiator portion of the antenna. As such, the feed portion of the antenna can be reduced in size in comparison to the feed portion for a conventional feed networks.
  • FIG. 19 is a diagram illustrating feed networks 1804, 1808 along with the signal traces, including the feed paths, for antennas 1304, 1308 .
  • FIG. 20 illustrates an outline for the ground plane of antennas 1304, 1308 .
  • FIG. 21 is a diagram illustrating both the ground planes and the signal traces superimposed.
  • feed networks An advantage of these feed networks is that the area required for the feed portion of the antenna to implement a feed network is reduced over conventional feeding techniques. This is because portions of the feed network which would otherwise be disposed on the feed portion of the antenna are now disposed on the radiator portion of the antenna. As a result of this, the overall length of the antenna can be reduced.
  • An additional advantage of such a feed network is that because the secondary feed point is moved closer to the feed point of the antenna, transmission line loss is decreased. Additionally, a transformer can be integrated into the routing line of the feed network for impedance matching.
  • an area-efficient network is configured such that a section of the feed network is disposed on a radiator portion of an antenna and the remainder of the feed network is disposed on a feed portion. Because part of the feed network is disposed on the radiator portion, the remainder of the feed network requires less area on the feed portion. As a result, the feed portion of the antenna can be smaller as compared to antennas having conventional feed networks.
  • the traces of the feed network that are disposed on the radiator portion are disposed opposite the ground portion of the radiators. As such, the ground portion of the radiators serves as a ground plane for this part of the feed network.
  • the area-efficient feed network can be implemented with numerous different types of antennas of varying configurations, including single-band and multi-band helical antennas. As a result of this configuration, the overall size of the antenna and the amount of loss in the feed are reduced as compared to antennas having conventional feed networks.
  • one technique for manufacturing helical antennas is to dispose radiators, feed networks and ground traces on a substrate and to wrap the substrate in an appropriate shape.
  • antenna configurations can be implemented using conventional techniques for wrapping the substrate in the appropriate shape, an improved structure and technique for wrapping the substrate is now described.
  • FIG. 22A is a diagram illustrating one embodiment of a structure used to maintain the substrate in an appropriate (e.g., cylindrical) shape. More specifically, FIG. 22 A illustrates an example structure added to an antenna having an area efficient feed network. After reading this description, it will become apparent to a person skilled in the relevant art how to implement the invention with helical antennas of other configurations.
  • FIGS. 22 B through 22 F depict cross-sectional views of an example structure used to hold the antenna in a cylindrical or other appropriate shape.
  • the example includes a metallic strip 2218 on, or as an extension of, ground plane 412 , solder material 2216 opposite metallic strip 2218 , and one or more vias 2210 .
  • Metallic strip 2218 can be comprised of a portion of ground plane 412 , or a metallic strip added to ground plane 412 .
  • metallic strip 2218 is provided by merely extending the width of ground plane 412 by a predetermined amount. In the embodiment illustrated in FIG. 22 A, this width is shown by ⁇ strip .
  • a series of vias 2210 are provided in ground plane 412 in the area of metallic strip 2218 .
  • the vias 2210 are added to radiator portions of both first antenna 1304 and second antenna 1308 .
  • the pattern chosen for vias 2210 is based on known mechanical and electrical properties of the materials used. While the invention can be implemented with only one or two vias 2210 on each ground plane 412 , to obtain a desired level of mechanical strength and electrical connection several vias 2210 may be employed. While not necessary, the portion of each ground plane 412 used can extend laterally, or circumferentially, beyond the antenna radiators.
  • vias 2210 extend completely through the material of ground plane 412 and through support substrate 406 ( 100 ) from one surface to the next.
  • the vias are manufactured as metallized or metal coated vias using well known techniques in the art.
  • a relatively small portion or region of an opposite edge 2214 of ground plane 412 is coated with solder material 2216 .
  • FIGS. 22 B and 22 D include a small metallic strip 2218 formed on substrate 406 on the opposite side from ground plane 412 , but adjacent to first edge 2212 .
  • the vias extend through the substrate to metallic strip 2218 .
  • metallic strip 2218 is not necessary in all applications, it will be readily apparent to those skilled in the art that metallic strip 2218 facilitates solder flow and improved mechanical bonding.
  • a specific material for manufacturing metallic strip 2218 is chosen according to known principles based on the ground plane material being used, the solder chosen, and so forth.
  • edges 2212 and 2214 are brought into close proximity with one another as illustrated in FIG. 22 D.
  • Vias 2210 and metallic strip 2218 (if provided) are positioned to overlap solder material 2216 on opposite ground plane edge 2214 . Heat is applied using well known soldering techniques and equipment while strip 2218 is held in contact with solder material 2216 .
  • solder material 2216 As solder material 2216 is melted, it flows into vias 2210 and onto metallic strip 2218 . The heat is then reduced or removed, and the solder forms a permanent, but removable or serviceable, joint or bond between the two outer edges or ends of ground plane 412 .
  • the antenna support substrate 406 and the antenna components deposited thereon are now mechanically held in the desired cylindrical form without requiring other materials such as dielectric tape, adhesives, or the like. This reduces the time, cost, and labor previously required to assemble a helical antenna of this type. This may also allow increased automation of this operation and provide more; readily reproducible antenna dimensions.
  • one edge of ground plane 412 is now electrically connected to the other edge, providing a continuous conductive ring from the ground plane, as desired. This electrical connection is accomplished without complicated soldering or connecting wires.
  • a series of one or more metallic pads or strips 2220 can be deposited at spaced apart locations along the length of one or both sets of antenna radiators. As seen in FIG. 22 E, the metallic pads or strips 2220 are positioned adjacent one or more radiators 104 A-D but on the opposite side of support substrate 406 ( 100 ). These pads or strips are positioned so that when the antenna substrate is rolled or curved to produce the desired antenna, as seen in FIG. 22 F, metallic pads or strips 2220 are positioned over a portion of radiators 104 A-D on the opposite edge of the support substrate. Specifically, in one embodiment, metallic pads or strips 220 are positioned over a ground trace 1436 of radiators 104 A-D. Metallized vias may be formed in pads 2220 where desired for the application or to improve transfer of heat to melt the solder.
  • solder 2226 If a small amount of solder 2226 is previously applied to a mating portion on the surface of ground trace 1436 , it can be used to join these radiators to the strips. This provides additional joints or bonding points which efficiently hold the antenna structure together in the desired form.
  • metallized vias can be formed in the pads or strips which extend through to the opposite side. These pads can be used in conjunction with or without the strips previously discussed for the ground planes. Such a structure is especially useful where very long radiators, or multiple stacks of antenna radiators are contemplated which result in tall antenna structures.
  • FIGS. 23 A - 23 C illustrate a series of views of an example embodiment of a form 2310 used for rolling substrate 406 into the desired shape.
  • the example illustrated in FIG. 23 is a form 2310 of cylindrical shape used in rolling the antenna and to provide continued support and rigidity for the antenna structure.
  • form 2310 can be provided with a series of prongs or teeth 2312 extending radially outward from an outer surface of form 2310 .
  • a series of "tooling" or assembly guide” holes or passages 2230 are provided in substrate 406 for mating with teeth 2312 .
  • tooling holes 2230 are illustrated as being positioned within ground planes 412 .
  • the metallic material of ground plane 412 acts to reinforce the holes and prevent deformation and movement when a relatively soft support substrate material is used. This assists with alignment accuracy for the antenna structure.
  • holes 2230 there is no requirement for holes 2230 to be placed within a metallic layer.
  • substrate 406 is shown positioned to engage a support form 2310 by mating teeth 2312 with holes 2230 .
  • holes 2230 engage teeth 2312 which help position substrate 406 in place against or on support from 2310 .
  • FIG. 23 C substrate 406 is illustrated as having been wrapped around support form 2310 until it overlaps itself so that strips 2218 , 2220 engage solder 2216 , 2226 as described above.
  • substrate 406 does not need to overlap on support form 2310 .
  • support form 2310 extend the entire length of the antenna(s), radiators 104 A-D or substrate 406 .
  • some or all of the portions of the antenna may be self supporting, without the need for a form 2310 . This feature can be advantageous, for example, to minimize the impact of the form 2310 on radiation patterns at certain frequencies.
  • FIGS. 23 A - 23 C For purposes of clarity and ease of illustration, in FIGS. 23 A - 23 C, only substrate 406 is shown, without material layers for ground planes, radiators, feeds, feed networks, and so forth. It will also be readily apparent to those skilled in the relevant art how to size holes 2230 to match the dimensions of teeth 2312 .
  • Form 2310 can be constructed using a solid or hollow structure formed in a cylindrical or other desired shape, with teeth or prongs 2312 protruding therefrom.
  • form 2310 can be thought of, for example, as a variation of the toothed drum found in many music boxes.
  • alternative structures can be implemented to provide form 2310 including an axle/spoke arrangement, an axle/sprocket arrangement, or other appropriate configuration.
  • the spacing of the prongs 2312 . or spokes may not be symmetrical about the support element. That is, the spacing may be larger in some portions in order to impart a greater amount of consistent tension in rolling, and smaller in some areas to better control substrate positioning where the substrate edges overlap.
  • tooth spacing is chosen such that teeth 2312 apply a certain amount of tension to hold substrate 406 in place and to make the entire assembly a more rigid structure.
  • holes 2230 and teeth 2312 provide improved manufacturing capabilities through position and assembly automation, and in precision placement or positioning of the substrate on a form that can be mounted within an antenna radome. This allows more precise structural definition and positioning of the antenna assembly, resulting in more precise control and compensation for the impact of the radome on radiation patterns.
  • metallic strips 2218 , solder material 2216 , and vias 2210 are provided by way of example. After reading this description, it would be apparent to a person skilled in the art how these components could be placed in alternative locations depending on the configuration desired. For example, these components can be positioned such that the antenna can be rolled to have right-hand or left-hand circular polarization and to have the radiators 104 A-D on either the inside or the outside of the shape.

Landscapes

  • Details Of Aerials (AREA)
  • Variable-Direction Aerials And Aerial Arrays (AREA)
  • Support Of Aerials (AREA)
  • Inorganic Insulating Materials (AREA)

Claims (13)

  1. Procédé de fabrication d'une antenne en hélice comprenant un substrat (406), le procédé étant caractérisé par les opérations consistant à :
    former des premier et deuxième plans de masse (412) sur ledit substrat (406), ledit deuxième plan de masse (412) étant distant dudit premier plan de masse (412) ;
    pratiquer une série de trous (2230) à travers ledit substrat (406) et ledit premier plan de masse (412) et à travers ledit substrat (406) et ledit deuxième plan de masse (412) ;
    positionner ledit substrat (406) pour le mettre en contact avec un élément de support (2310), ledit élément de support (2310) comprenant une première et une deuxième série de dents (2312) s'étendant radialement vers l'extérieur depuis une surface extérieure de celui-ci et agencées de telle façon que la première série de dents (2312) s'accouple avec lesdits trous (2230) dudit substrat (406) et dudit premier plan de masse (412) et ladite deuxième série de dents (2312) s'accouple avec lesdits trous (2230) dudit substrat (406) et dudit deuxième plan de masse (412),
    dans lequel lesdites dents (2312) sont agencées de telle manière que lors de la rotation de l'élément de support (2310) autour de son axe principal, ledit substrat (406) est enroulé autour de l'élément de support (2310).
  2. Procédé selon la revendication 1, dans lequel lesdites dents (2312) et lesdits trous (2230) sont agencés de telle manière que :
    avant la rotation de l'élément de support (2310), au moins une dent (2312) s'accouple avec au moins un trou correspondant parmi lesdits trous (2230) ; et
    lors de la rotation, ladite au moins une dent (2312) ou au moins une dent supplémentaire (2312) s'accouple avec au moins un trou supplémentaire (2230).
  3. Procédé selon la revendication 1 ou 2, comprenant le fait de choisir l'espacement entre lesdites dents (2312) pour appliquer une traction prédéterminée au substrat (406) lors de la rotation de l'élément de support (2310).
  4. Procédé selon l'une quelconque des revendications précédentes, dans lequel lesdites dents (2312) sont espacées de façon asymétrique autour de l'élément de support (2310).
  5. Procédé selon l'une quelconque des revendications précédentes, dans lequel ledit élément de support (2310) comprend un organe creux substantiellement cylindrique.
  6. Procédé selon la revendication 1, dans lequel :
    ladite antenne en hélice comprend une bande métallique (2218) sur la surface dudit substrat (406) à l'opposé de la surface sur laquelle ledit premier plan de masse est formé mais adjacente à un premier bord (2212) du premier plan de masse (412) ; et
    lors de la rotation dudit élément de support (2310), ledit substrat se chevauche lui-même, de sorte que ladite bande métallique (2218) est proche d'un deuxième bord dudit premier plan de masse (2214) et de ladite surface sur laquelle ledit premier plan de masse est formé.
  7. Procédé selon l'une quelconque des revendications précédentes, comprenant le fait de pratiquer un trou d'interconnexion (2210) dans ledit premier plan de masse (412) à proximité de ladite bande métallique (2218).
  8. Procédé selon la revendication 7, dans lequel ledit trou d'interconnexion s'étend complètement à travers ledit premier plan de masse (412) et ledit substrat (412).
  9. Procédé selon la revendication 8, dans lequel ledit trou d'interconnexion (2210) s'étend en outre à travers ladite bande métallique (2218).
  10. Procédé selon la revendication 6, comprenant le fait de revêtir une partie dudit substrat (406) d'un matériau de brasure (2216) dans la région du deuxième bord (2214) du premier plan de masse (412), de sorte que lors de la rotation de l'élément de support (2310), le matériau de brasure (2216) est proche de la bande métallique (2218).
  11. Procédé selon la revendication 9 ou 10, comprenant le fait d'appliquer de la chaleur pendant que la bande métallique (2218) est maintenue en contact avec le matériau de brasure (2216).
  12. Procédé selon la revendication 10 ou 11, comprenant les opérations consistant à :
    positionner un contact métallique (2220) sur une partie d'un radiateur (104) de ladite antenne en hélice ;
    appliquer un matériau de brasure (2226) sur une partie correspondante de la surface d'un ruban de masse (1436),
    dans lequel ledit matériau de brasure (2226) est positionné de façon à joindre le radiateur (104) au contact métallique (2220).
  13. Procédé selon l'une quelconque des revendications précédentes, dans lequel ledit premier plan de masse (412) forme un anneau conducteur continu après que ledit substrat (406) a été enroulé autour dudit élément de support (2310).
EP04078530A 1997-03-27 1998-03-25 Substrat pour antenne hélicoidale et procédé de fabrication de celle-ci Expired - Lifetime EP1524722B1 (fr)

Applications Claiming Priority (3)

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US82630997A 1997-03-27 1997-03-27
US826309 1997-03-27
EP98915162A EP0970540B1 (fr) 1997-03-27 1998-03-25 Antenne et reseau d'alimentation d'antenne

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EP98915162A Division EP0970540B1 (fr) 1997-03-27 1998-03-25 Antenne et reseau d'alimentation d'antenne

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EP1524722A1 EP1524722A1 (fr) 2005-04-20
EP1524722B1 true EP1524722B1 (fr) 2007-06-27

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EP98915162A Expired - Lifetime EP0970540B1 (fr) 1997-03-27 1998-03-25 Antenne et reseau d'alimentation d'antenne
EP04078530A Expired - Lifetime EP1524722B1 (fr) 1997-03-27 1998-03-25 Substrat pour antenne hélicoidale et procédé de fabrication de celle-ci

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JP (2) JP4477145B2 (fr)
KR (1) KR20010005605A (fr)
CN (1) CN1199320C (fr)
AT (2) ATE286308T1 (fr)
AU (1) AU6941198A (fr)
CA (1) CA2284673A1 (fr)
DE (2) DE69828389T2 (fr)
ES (1) ES2289429T3 (fr)
HK (2) HK1026306A1 (fr)
TW (1) TW428342B (fr)
WO (1) WO1998044590A1 (fr)

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US8248323B2 (en) * 2008-05-30 2012-08-21 Motorola Solutions, Inc. Antenna and method of forming same
JP6222103B2 (ja) 2012-11-12 2017-11-01 日本電気株式会社 アンテナ及び無線通信装置

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ATE365986T1 (de) 2007-07-15
KR20010005605A (ko) 2001-01-15
DE69838008D1 (de) 2007-08-09
HK1026306A1 (en) 2000-12-08
TW428342B (en) 2001-04-01
AU6941198A (en) 1998-10-22
CA2284673A1 (fr) 1998-10-08
ATE286308T1 (de) 2005-01-15
DE69838008T2 (de) 2008-03-06
HK1077404A1 (en) 2008-01-25
JP2007306585A (ja) 2007-11-22
DE69828389T2 (de) 2005-12-15
CN1199320C (zh) 2005-04-27
JP4477145B2 (ja) 2010-06-09
WO1998044590A1 (fr) 1998-10-08
EP1524722A1 (fr) 2005-04-20
EP0970540B1 (fr) 2004-12-29
JP4955461B2 (ja) 2012-06-20
ES2289429T3 (es) 2008-02-01
EP0970540A1 (fr) 2000-01-12
JP2001518252A (ja) 2001-10-09
DE69828389D1 (de) 2005-02-03
CN1263641A (zh) 2000-08-16

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