EP1055264A1 - Broadband microstrip to parallel-plate-waveguide transition - Google Patents

Broadband microstrip to parallel-plate-waveguide transition

Info

Publication number
EP1055264A1
EP1055264A1 EP99966071A EP99966071A EP1055264A1 EP 1055264 A1 EP1055264 A1 EP 1055264A1 EP 99966071 A EP99966071 A EP 99966071A EP 99966071 A EP99966071 A EP 99966071A EP 1055264 A1 EP1055264 A1 EP 1055264A1
Authority
EP
European Patent Office
Prior art keywords
parallel
waveguide
microstrip
recited
transition
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP99966071A
Other languages
German (de)
French (fr)
Other versions
EP1055264B1 (en
Inventor
Hashemi-Yeganeh S.
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Raytheon Co
Original Assignee
Raytheon Co
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Raytheon Co filed Critical Raytheon Co
Publication of EP1055264A1 publication Critical patent/EP1055264A1/en
Application granted granted Critical
Publication of EP1055264B1 publication Critical patent/EP1055264B1/en
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/08—Coupling devices of the waveguide type for linking dissimilar lines or devices
    • H01P5/10—Coupling devices of the waveguide type for linking dissimilar lines or devices for coupling balanced lines or devices with unbalanced lines or devices

Definitions

  • the present invention relates generally to waveguide transitions, and more particularly, to a broadband microstrip to parallel-plate-waveguide transition.
  • the present invention comprises a broadband transition for use between a shielded microstrip and a parallel-plate waveguide.
  • the broadband transition comprises a metallic taper that is electrically connected to a conductive strip of the microstrip at one end and to a wall of the waveguide at the other end.
  • the metallic taper may be optimized to tune out, over a broad operating frequency band, reflections caused by the discontinuity between the two largely disparate transmission media comprising the microstrip and parallel-plate waveguide.
  • the broadband transition provides for a low VSWR transition with wide operating bandwidth and wide-angle scanning capability between a linear array of shielded microstrip circuits (e.g., phase shifters) and a parallel-plate waveguide structure (e.g., a continuous transverse stub array antenna).
  • the shielded microstrip lines minimize cross-coupling between adjacent circuits, thereby allowing their individual amplitude and phase excitations to be imposed on a line source along the parallel-plate waveguide interface.
  • the metallic taper is also suitable for construction of a planar, in-line transition between microstrip and rectangular waveguide with full-band coverage of the fundamental waveguide mode. No description of this particular type of transition has been found in the technical literature.
  • the present invention may be used in applications that require a low-VSWR, broadband, planar, inline transition between microstrip and parallel-plate or rectangular waveguide structures.
  • the present invention provides a capability to transition between a linear array of microstrip circuits (e.g., RF feed networks, ferrite or PIN-diode phase shifters, microwave amplifiers or mixers, etc.) and the line feed for parallel-plate or overmoded waveguide.
  • the present invention may be used to provide low-cost, two-dimensional scanning capability by combining this type electronic scanning line feed in one plane with mechanical rotation in an orthogonal plane.
  • Fig. 1 illustrates an exemplary broadband microstrip to parallel-plate waveguide transition in accordance with the principles of the present invention
  • Fig. 2 shows a solid-dielectric continuous transverse stub array antenna as an example of the planar antenna
  • Fig. 3 shows a section of the transition for three adjacent elements;
  • Fig 4 is a graph showing computed VSWR for an exemplary 32-element continuous transverse stub array antenna
  • Fig. 5 illustrates an exemplary broadband transition that may be used as a low-
  • Fig. 6 shows the profile defined by points illustrated in Table 1.
  • Fig. 1 illustrates the use of a broadband microstrip to parallel-plate waveguide transition 20 in accordance with the principles of the present invention in an antenna system 10.
  • Fig. 1 illustrates a simplified block diagram of the antenna system 10 showing a typical application of the broadband transition 20.
  • the antenna system 10 comprises a planar antenna 30 with which the transition 20 is used.
  • the planar antenna 30 has a line feed input including a parallel-plate or overmoded waveguide section.
  • the planar antenna 30 also comprises a linear array of phase shifters 13 that each have a microstrip RF port 13a.
  • the broadband transition 20 provides an RF interface between the phase shifters 13 and the antenna 30
  • a combiner/divider 12 for receiving input signals at an RF input 1 1 establishes an amplitude distribution along a line-feed input 30a of the antenna, and the linear array of phase shifters 13 may be adjusted to produce the appropriate phase front to scan the beam output by the antenna 30 at its radiating aperture at a desired angle.
  • Fig. 2 shows a solid-dielectric continuous transverse stub array antenna 30 as a representative example of the planar antenna 30.
  • the continuous transverse stub array antenna 30 has a parallel-plate waveguide horizontal line feed 31.
  • An eight-way vertical corporate feed 32 located behind an aperture plate 33, feeds eight continuous transverse stub radiators 34.
  • the horizontal aperture distribution which is provided by the n-way combiner/divider 12 and phase shifters 13 shown in Fig. I , is imposed onto the parallel-plate line feed 30a along the rear of the antenna 30.
  • a section of the present broadband transition 20 used for three adjacent elements is shown in Fig. 3.
  • a 0.140 inch high, dielectric-filled, parallel -plate waveguide 21 (shown on the left-hand side of Fig. 3) corresponds to the parallel-plate line feed 30a of the continuous transverse stub array antenna 30.
  • a plurality of microstrip circuits 22 each comprising a shielded microstrip feed line 24 (shown on the right-hand side of Fig. 3), comprise output circuits for three phase shifters 13, and are the same height as the parallel-plate waveguide 12 in order to minimize the physical discontinuity at the interface.
  • the plurality of microstrip circuits 22 are fabricated on a substrate 23, such as a 0 025 inch thick Rexolite* substrate 23, which is preferably the same dielectric material from which both the parallel-plate waveguide 21 and continuous transverse stub array antenna 30 are made.
  • a section of the top wall of the broadband transition 20 is cut away in Fig. 3 so that one of a plurality of metallic tapers 26 can be seen.
  • the tapers 26 may be fabricated either as a separate part, or fabricated as part of the parallel-plate region by forming the required shape m the dielectric material and subsequently metalizing the cavity walls
  • the metallic taper 26 is electrically connected to the microstrip feed line 24 ot the microstrip circuit 22 at one end and to a wall (shown as the upper or top wall) of the waveguide 21 at the other end. While the broadband transition 20 has the capability of low VSWR performance over multi-octave bandwidths, a design tradeoff may be imposed by the requirement to avoid grating lobes appearing in real space at the upper band edge for large scan angles.
  • sin ⁇ max j This relationship is given by the formula: : r Equation (1) ⁇ h l +
  • s spacing between adjacent elements
  • ⁇ wavelength at the highest operating frequency
  • n number of elements
  • ⁇ max maximum scan angle from broadside.
  • a broadband transition 20 for a 32- element continuous transverse stub array antenna 30 was modeled using a Hewlett- Packard High Frequency Structures Simulator (HFSS) computer program.
  • the array antenna 30 was designed to operate over the 6 to 18 GHz frequency band and scan to ⁇ 60 degrees without grating lobes. Equation (1) gives the maximum allowable element spacing as 0.340 inch, and thus a spacing of 0.325 inch was cho.sen to provide some margin for fabrication tolerances.
  • Fig. 4 shows the computed magnitude of reflection 1S, ,I and transmission IS 21 I coefficients versus frequency.
  • the computed VSWR shown in Fig 4, is below 1.50: 1 from 7 to above 24 GHz.
  • grating lobes occur above 22.7 GHz if the array is scanned to ⁇ 60 degrees.
  • the array may be scanned only to ⁇ 27.8 degrees without grating lobes.
  • the element spacing may be increased slightly (e.g., 0.350 inch) to give the desired low-VSWR performance down to 6 GHz, but then ⁇ 60 degrees scan coverage without grating lobes would be achievable only up to 17.5 GHz.
  • the usable scan sector would become progressively smaller, as expressed by Equation (1).
  • the broadband transition 20 of the present invention may also be used as a low- VSWR transition between microstrip circuits 22 and rectangular waveguide 21, as is shown in Fig. 5.
  • the wideband capability of this particular broadband transition 20, however, is limited by cutoff of the fundamental mode at the low frequency end and the propagation of higher-order modes at the high end.
  • the methodology used to the design the metallic taper 26 includes the following steps.
  • the width (Y direction) of the taper 26 is chosen to be equal to the line width of the microstrip circuit 22. This avoids the necessity of matching in the Y direction, and this option is available for special design requirements.
  • the length of each taper 26 is determined by the operational bandwidth, desired
  • Tapers 26 are typically several wavelengths long at the lowest frequency for the respective medium. In the example design, tapers 26 less than a wavelength long were dictated by physical constraints.
  • the curves of the tapers 26, which are initially parabolic, are optimized numerically to minimize reflection coefficient across the desired band. Alternately, optimization routines may be used to compute the curves.
  • Table 1 gives the X and Z coordinates for the lower and upper surfaces of the metallic taper 26, while Fig. 6 shows the profile defined by these points.

Landscapes

  • Waveguide Aerials (AREA)

Abstract

A broadband transmission (20) for use between a shielded microstrip (24) and a parallel-plate waveguide (21). The broadband transition comprises a metallic taper (26) that is electrically connected to a microstrip feed line (24) of the microstrip circuit at one end and to a wall of the waveguide at the other end. The metallic taper may be optimized to tune out reflections caused by the discontinuity between the microstrip circuit and parallel-plate waveguide over a broad operating frequency band. An antenna system (10) employing the broadband transition is also disclosed.

Description

BROADBAND MICROSTRIP TO PARALLEL- PLATE-WAVEGUIDE TRANSITION
BACKGROUND
The present invention relates generally to waveguide transitions, and more particularly, to a broadband microstrip to parallel-plate-waveguide transition.
Conventional microwave transitions relate to the present invention involve that use of a waveguide operating in a fundamental mode rather than a parallel-plate or overmoded waveguide. Therefore, the prior art waveguide transition designs cannot achieve a broadband and low-VSWR capability as is provided by the present invention.
It would be therefore be advantageous to have a broadband microstrip to parallel-plate-waveguide transition that improves upon conventional waveguide transition.
SUMMARY OF THE INVENTION
The present invention comprises a broadband transition for use between a shielded microstrip and a parallel-plate waveguide. The broadband transition comprises a metallic taper that is electrically connected to a conductive strip of the microstrip at one end and to a wall of the waveguide at the other end. The metallic taper may be optimized to tune out, over a broad operating frequency band, reflections caused by the discontinuity between the two largely disparate transmission media comprising the microstrip and parallel-plate waveguide. The broadband transition provides for a low VSWR transition with wide operating bandwidth and wide-angle scanning capability between a linear array of shielded microstrip circuits (e.g., phase shifters) and a parallel-plate waveguide structure (e.g., a continuous transverse stub array antenna). The shielded microstrip lines minimize cross-coupling between adjacent circuits, thereby allowing their individual amplitude and phase excitations to be imposed on a line source along the parallel-plate waveguide interface. The metallic taper is also suitable for construction of a planar, in-line transition between microstrip and rectangular waveguide with full-band coverage of the fundamental waveguide mode. No description of this particular type of transition has been found in the technical literature.
The present invention may be used in applications that require a low-VSWR, broadband, planar, inline transition between microstrip and parallel-plate or rectangular waveguide structures. In particular, the present invention provides a capability to transition between a linear array of microstrip circuits (e.g., RF feed networks, ferrite or PIN-diode phase shifters, microwave amplifiers or mixers, etc.) and the line feed for parallel-plate or overmoded waveguide. The present invention may be used to provide low-cost, two-dimensional scanning capability by combining this type electronic scanning line feed in one plane with mechanical rotation in an orthogonal plane.
BRIEF DESCRIPTION OF THE DRAWINGS
The various features and advantages of the present invention may be more readily understood with reference to the following detailed description taken in conjunction with the accompanying drawing, wherein like reference numerals designate like structural elements, and in which:
Fig. 1 illustrates an exemplary broadband microstrip to parallel-plate waveguide transition in accordance with the principles of the present invention; Fig. 2 shows a solid-dielectric continuous transverse stub array antenna as an example of the planar antenna;
Fig. 3 shows a section of the transition for three adjacent elements; Fig 4 is a graph showing computed VSWR for an exemplary 32-element continuous transverse stub array antenna Fig. 5 illustrates an exemplary broadband transition that may be used as a low-
VSWR transition between microstrip and rectangular waveguide; and
Fig. 6 shows the profile defined by points illustrated in Table 1.
DETAILED DESCRIPTION Referring to the drawing figures, Fig. 1 illustrates the use of a broadband microstrip to parallel-plate waveguide transition 20 in accordance with the principles of the present invention in an antenna system 10. Fig. 1 illustrates a simplified block diagram of the antenna system 10 showing a typical application of the broadband transition 20.
The antenna system 10 comprises a planar antenna 30 with which the transition 20 is used. The planar antenna 30 has a line feed input including a parallel-plate or overmoded waveguide section. The planar antenna 30 also comprises a linear array of phase shifters 13 that each have a microstrip RF port 13a. The broadband transition 20 provides an RF interface between the phase shifters 13 and the antenna 30 A combiner/divider 12 for receiving input signals at an RF input 1 1 establishes an amplitude distribution along a line-feed input 30a of the antenna, and the linear array of phase shifters 13 may be adjusted to produce the appropriate phase front to scan the beam output by the antenna 30 at its radiating aperture at a desired angle.
Fig. 2 shows a solid-dielectric continuous transverse stub array antenna 30 as a representative example of the planar antenna 30. The continuous transverse stub array antenna 30 has a parallel-plate waveguide horizontal line feed 31. An eight-way vertical corporate feed 32, located behind an aperture plate 33, feeds eight continuous transverse stub radiators 34. The horizontal aperture distribution, which is provided by the n-way combiner/divider 12 and phase shifters 13 shown in Fig. I , is imposed onto the parallel-plate line feed 30a along the rear of the antenna 30.
A section of the present broadband transition 20 used for three adjacent elements is shown in Fig. 3. A 0.140 inch high, dielectric-filled, parallel -plate waveguide 21 (shown on the left-hand side of Fig. 3) corresponds to the parallel-plate line feed 30a of the continuous transverse stub array antenna 30. A plurality of microstrip circuits 22 each comprising a shielded microstrip feed line 24 (shown on the right-hand side of Fig. 3), comprise output circuits for three phase shifters 13, and are the same height as the parallel-plate waveguide 12 in order to minimize the physical discontinuity at the interface. The plurality of microstrip circuits 22 are fabricated on a substrate 23, such as a 0 025 inch thick Rexolite* substrate 23, which is preferably the same dielectric material from which both the parallel-plate waveguide 21 and continuous transverse stub array antenna 30 are made. A section of the top wall of the broadband transition 20 is cut away in Fig. 3 so that one of a plurality of metallic tapers 26 can be seen. The tapers 26 may be fabricated either as a separate part, or fabricated as part of the parallel-plate region by forming the required shape m the dielectric material and subsequently metalizing the cavity walls The metallic taper 26 is electrically connected to the microstrip feed line 24 ot the microstrip circuit 22 at one end and to a wall (shown as the upper or top wall) of the waveguide 21 at the other end. While the broadband transition 20 has the capability of low VSWR performance over multi-octave bandwidths, a design tradeoff may be imposed by the requirement to avoid grating lobes appearing in real space at the upper band edge for large scan angles. This relationship is given by the formula: : r Equation (1) λh l + |sin θmaxj where: s = spacing between adjacent elements; λ^ = wavelength at the highest operating frequency; n = number of elements; and θmax = maximum scan angle from broadside. As an example of the present invention, a broadband transition 20 for a 32- element continuous transverse stub array antenna 30 was modeled using a Hewlett- Packard High Frequency Structures Simulator (HFSS) computer program. The array antenna 30 was designed to operate over the 6 to 18 GHz frequency band and scan to ±60 degrees without grating lobes. Equation (1) gives the maximum allowable element spacing as 0.340 inch, and thus a spacing of 0.325 inch was cho.sen to provide some margin for fabrication tolerances.
Fig. 4 shows the computed magnitude of reflection 1S, ,I and transmission IS21I coefficients versus frequency. The computed VSWR, shown in Fig 4, is below 1.50: 1 from 7 to above 24 GHz. However, grating lobes occur above 22.7 GHz if the array is scanned to ±60 degrees. At 24 GHz, the array may be scanned only to ±27.8 degrees without grating lobes. The element spacing may be increased slightly (e.g., 0.350 inch) to give the desired low-VSWR performance down to 6 GHz, but then ±60 degrees scan coverage without grating lobes would be achievable only up to 17.5 GHz. At higher frequencies, the usable scan sector would become progressively smaller, as expressed by Equation (1).
The broadband transition 20 of the present invention may also be used as a low- VSWR transition between microstrip circuits 22 and rectangular waveguide 21, as is shown in Fig. 5. The wideband capability of this particular broadband transition 20, however, is limited by cutoff of the fundamental mode at the low frequency end and the propagation of higher-order modes at the high end.
The methodology used to the design the metallic taper 26 includes the following steps. The width (Y direction) of the taper 26 is chosen to be equal to the line width of the microstrip circuit 22. This avoids the necessity of matching in the Y direction, and this option is available for special design requirements. The length of each taper 26 is determined by the operational bandwidth, desired
VSWR and space limitations. Tapers 26 are typically several wavelengths long at the lowest frequency for the respective medium. In the example design, tapers 26 less than a wavelength long were dictated by physical constraints.
The curves of the tapers 26, which are initially parabolic, are optimized numerically to minimize reflection coefficient across the desired band. Alternately, optimization routines may be used to compute the curves.
Table 1 gives the X and Z coordinates for the lower and upper surfaces of the metallic taper 26, while Fig. 6 shows the profile defined by these points.
Table 1 Lower SurfaceUpper Surface
X (inch) Z (inch) X finch Z (inch)
-0.660 0.140 -0.660 0.140
-0.600 0.132 -0.600 0.140
-0.540 0.1 18 -0.540 0. 140
-0.480 0.100 -0.480 0. 140
-0.420 0.084 -0.420 0. 140
-0.360 0.070 -0.360 0. 140
-0.300 0.058 -0.300 0.140
-0.240 0.048 -0.240 0.140
-0. 1 80 0.040 -0.180 0.140
-0.120 0.033 -0.120 0. 140
-0.060 0.028 -0.060 0.140
0 0.025 0 0. 140
0.100 0.025 0.100 0. 140
0.200 0.025 0.200 0.140
0.300 0.025 0.300 0.140
0.400 0.025 0.400 0. 140
0.500 0.025 0.500 0. 140
0.580 0.025 0.580 0. 1 18
0.660 0.025 0.660 0.100
0.740 0.025 0,740 0.084
0.820 0.025 0.820 0.070
0.900 0. 025 0.900 0.058
0.980 0.025 0.980 0.048
1.060 0.025 1.060 0.040
1 . 140 0.025 1.140 0.033
1.220 0.025 1 .220 0.028
1.300 0.025 1.300 0.025 Thus, a broadband microstrip to parallel-plate-waveguide transition has been disclosed. It is to be understood that the above-described embodiment is merely illustrative of some of the many specific embodiments that represent applications of the principles of the present invention. Clearly, numerous and other arrangements can be readily devised by those skilled in the art without departing from the scope of the invention.

Claims

CLAIMSWhat is claimed is:
1. A broadband microstrip to parallel-plate-waveguide transition (20) for coupling RF energy to a planar antenna 30, comprising: a parallel-plate waveguide (21 ); a plurality of microstrip circuits (22) that each comprise a shielded microstrip feed line (24) disposed on a substrate (23); and a plurality of metallic tapers (26) that each have a first end that is coupled to one of the plurality of microstrip feed lines and that each have a second end disposed adjacent to the waveguide.
2. The transition (20) recited in Claim 1 wherein the parallel-plate waveguide (21 ) comprises a dielectric -filled, parallel -pi ate waveguide (21 ).
3. The transition (20) recited in Claim 1 wherein the metallic tapers (26) comprise separate metal parts.
4. The transition (20) recited in Claim 1 wherein the metallic tapers (26) comprise metallized tapered dielectric material.
5. The transition (20) recited in Claim 1 wherein the width (Y direction) of each metallic taper (26) is equal to the line width of the microstrip circuit (22), the length of each taper is determined by the operational bandwidth, desired VSWR and space limitations, and curves of the tapers are optimized to minimize the reflection coefficient across the desired band.
6. An antenna system ( 10) comprising: an RF input (1 1); a combiner/divider ( 12) coupled to the RF input; a linear array of phase shifters (13) that each have a microstrip RF port (13a) coupled to the combiner/divider; a planar antenna (30) having a hne feed input and a waveguide section; and a broadband microstrip to parallel-plate-waveguide transition (20) coupled between the linear array of phase shifters and the planar antenna that comprises: a parallel-plate waveguide (21); a plurality of microstrip circuits (22) that each comprise a shielded microstrip feed line (24) disposed on a substrate (23); and a plurality of metallic tapers (26) that each have a first end that is coupled to one of the plurality of microstrip feed lines and that each have a second end disposed adjacent to the waveguide.
7. The antenna system ( 10) recited in Claim 6 wherein the planar antenna (30) has a parallel-plate waveguide section.
8. The antenna system ( 10) recited m Claim 6 wherein the planar antenna (30) has an overmoded waveguide section.
9. The antenna system (.10) recited in Claim 6 wherein the planar antenna (30) comprises a solid -dielectric continuous transverse stub array antenna (30).
10. The antenna system (10) recited in Claim 6 wherein the continuous transverse stub array antenna (30) comprises a parallel-plate waveguide horizontal line feed (31 ).
1 1. The antenna system ( 0) recited in Claim 6 wherein the broadband transition (20) comprises a dielectric-filled, parallel-plate waveguide (21).
12. The system (10) recited in Claim 6 wherein the parallel-plate waveguide (21 ) comprises a dielectric-filled, parallel-plate waveguide (21 ).
13. The system (10) recited in Claim 6 wherein the metallic tapers (26) comprise separate metal parts.
14. The system (10) recited in Claim 6 wherein the metallic tapers (26) comprise metallized tapered dielectric material.
15. The system ( 10) recited in Claim 6 wherein the width (Y direction) of each metallic taper (26) is equal to the line width of the microstrip circuit (22), the length of each taper is determined by the operational bandwidth, desired VSWR and space limitations, and curves of the tapers are optimized to minimize the reflection coefficient across the desired band.
EP99966071A 1998-12-10 1999-12-09 Broadband microstrip to parallel-plate-waveguide transition Expired - Lifetime EP1055264B1 (en)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
US209123 1994-03-08
US20912398A 1998-12-10 1998-12-10
PCT/US1999/029184 WO2000035044A1 (en) 1998-12-10 1999-12-09 Broadband microstrip to parallel-plate-waveguide transition

Publications (2)

Publication Number Publication Date
EP1055264A1 true EP1055264A1 (en) 2000-11-29
EP1055264B1 EP1055264B1 (en) 2007-01-24

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JP (1) JP2002532928A (en)
DE (1) DE69934968T2 (en)
DK (1) DK1055264T3 (en)
WO (1) WO2000035044A1 (en)

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US7612733B2 (en) 2007-03-12 2009-11-03 The Regents Of The University Of Colorado Transition region for use with an antenna-integrated electron tunneling device and method
DE102010014916B4 (en) * 2010-04-14 2012-10-31 Aeromaritime Systembau Gmbh Phased array antenna

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JPH0640601B2 (en) * 1984-12-17 1994-05-25 日本電信電話株式会社 Waveguide converter
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Cited By (2)

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Publication number Priority date Publication date Assignee Title
US20090210594A1 (en) * 2006-08-04 2009-08-20 Alistair Crone Bruce Bus interconnect device and a data processing apparatus including such a bus interconnect device
US8171191B2 (en) * 2006-08-04 2012-05-01 Arm Limited Bus interconnect device and a data processing apparatus including such a bus interconnect device

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Publication number Publication date
DE69934968T2 (en) 2007-11-22
JP2002532928A (en) 2002-10-02
DE69934968D1 (en) 2007-03-15
DK1055264T3 (en) 2007-04-30
WO2000035044A1 (en) 2000-06-15
EP1055264B1 (en) 2007-01-24

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