EP1028606A2 - Circuit for operating at least one low-pressure discharge lamp - Google Patents

Circuit for operating at least one low-pressure discharge lamp Download PDF

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Publication number
EP1028606A2
EP1028606A2 EP00100767A EP00100767A EP1028606A2 EP 1028606 A2 EP1028606 A2 EP 1028606A2 EP 00100767 A EP00100767 A EP 00100767A EP 00100767 A EP00100767 A EP 00100767A EP 1028606 A2 EP1028606 A2 EP 1028606A2
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EP
European Patent Office
Prior art keywords
capacitor
diode
harmonic filter
voltage output
voltage
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Granted
Application number
EP00100767A
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German (de)
French (fr)
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EP1028606A3 (en
EP1028606B1 (en
Inventor
Bernd Rudolph
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Osram GmbH
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Patent Treuhand Gesellschaft fuer Elektrische Gluehlampen mbH
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Publication of EP1028606A3 publication Critical patent/EP1028606A3/en
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Publication of EP1028606B1 publication Critical patent/EP1028606B1/en
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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S315/00—Electric lamp and discharge devices: systems
    • Y10S315/07—Starting and control circuits for gas discharge lamp using transistors

Definitions

  • the invention relates to a circuit arrangement for operating at least one low-pressure discharge lamp according to the preamble of claim 1.
  • Such a circuit arrangement is for example in the European patent EP 0 253 224 B1.
  • This patent describes a circuit arrangement for high-frequency operation of low-pressure discharge lamps.
  • the Circuit arrangement has a mains voltage rectifier, an inverter, a load circuit designed as a series resonance circuit and a harmonic filter, which is intended to reduce the mains current harmonic content.
  • the harmonic filter has a series connection of two diodes, which in the forward direction on Mains voltage rectifiers are connected to a capacitor which is the center tap connects between the diodes and the voltage output of the inverter, and another capacitor, the center tap between the diodes connects with a tap in the series resonance circuit. It also has Harmonic filter two more diodes that are parallel to the two diodes of the harmonic filter are switched and their center tap with the voltage output of the Inverter is connected.
  • the circuit arrangement according to the invention has a mains voltage rectifier, one parallel to the DC voltage output of the mains voltage rectifier switched capacitor, an inverter with a downstream, as Series resonant circuit designed load circuit, one parallel to the DC voltage input the smoothing capacitor switched by the inverter and a harmonic filter, that has at least one diode and a capacitor.
  • a first connection of the at least one capacitor of the harmonic filter with the resonance capacitor of the series resonance circuit with a first electrode the at least one diode of the harmonic filter and with the DC voltage output of the mains voltage rectifier.
  • the parallel to the DC voltage output of the mains voltage rectifier switched capacitor dimensioned so that its capacity is at least 0.33 times the capacitance of the resonance capacitor.
  • This advantageous dimensioning the capacitance values of the aforementioned capacitors is even for the case that the voltage drop across the at least one low-pressure discharge lamp exceeds the voltage drop across the smoothing capacitor an almost sinusoidal mains current draw and a correspondingly low harmonic content guaranteed.
  • the Capacity of the parallel to the DC voltage output of the mains voltage rectifier switched capacitor advantageously at most as large as the capacity of the resonance capacitor.
  • the figure shows a schematic representation of the invention Circuit arrangement according to a preferred embodiment of the Invention.
  • This circuit arrangement has a mains voltage input j1, j2 and a filter circuit connected to the mains voltage input j1, j2, which off a current-compensated filter choke L1, a non-current-compensated filter choke L2 and a capacitor C1, and one downstream of the filter circuit Mains voltage rectifier GL.
  • Parallel to the DC voltage output of the mains voltage rectifier GL is at the junction points j3, j4 Support capacitor C2 switched.
  • To the positive output of the mains voltage rectifier GL is connected to the anode of a diode D1 via junction j3.
  • the cathode of the diode D1 is with the positive connection of a smoothing capacitor C3 connected.
  • the negative terminal of the smoothing capacitor C3 is across junction j4 with the negative output of the line rectifier GL connected.
  • the smoothing capacitor C3 serves as a DC voltage source for a free-swinging half-bridge inverter that by two transistors Q1, Q2, its control device N1, N2, N3, L3, L4, R1, R2, R4, R5 and the emitter resistors R3, R6 and two freewheeling diodes D2, D3, each parallel to the collector-emitter path of one of the transistors Q1 or Q2 are switched, is formed.
  • the DC input of the half-bridge inverter Q1, Q2 from the collector terminal of transistor Q1 and the emitter terminal of the transistor Q2 and the emitter resistor R5 are formed is arranged in parallel to the smoothing capacitor C3.
  • a load circuit designed as a series resonance circuit is connected to the voltage output, that is, at the center tap M.
  • the load circuit the primary winding N1 of the toroidal transformer belonging to the control device, a coupling capacitor C4, a lamp inductor L5 and one Resonance capacitor C6, all of which are connected in series.
  • the center tap M of the half-bridge inverter Q1, Q2 is via the primary winding N1, the coupling capacitor C4, the lamp inductor L5 and the resonance capacitor C6 with the Anode of the diode D1 and connected to the junction j3.
  • the circuit arrangement also has a trapezoidal capacitor C7, the first connection with the anode of the diode D1 and with the branch point j3 and its second connection with the center tap M of the half-bridge inverter Q1, Q2 connected is.
  • the circuit arrangement has a starting device, the from a diac DC, a starting capacitor C9, a resistor R7 and one Diode D4 exists, and connections j5, j6, j7, j8 for two low-pressure discharge lamps connected in series LP1, LP2, and an auxiliary ignition capacitor C8.
  • the auxiliary ignition capacitor C8 is arranged parallel to the second low-pressure discharge lamp LP2.
  • a first connection of the auxiliary ignition capacitor C8 is via a node in the load circuit with the resonance capacitor C6 and with the lamp choke L5 connected.
  • the second connection of the auxiliary ignition capacitor C8 is connected to the second Electrode of the first low-pressure discharge lamp LP1 and with the first electrode connected to the second low-pressure discharge lamp LP2.
  • the first electrode of the First low pressure discharge lamp LP1 is connected to the cathode via connection j5 the diode D1, with the collector of the transistor Q1 and with the positive terminal of the smoothing capacitor C3 and via the connection j6, the resistor R7 and the starting capacitor C9 with the connection j4 and with the negative Terminal of the smoothing capacitor C3 connected.
  • the second electrode of the second low-pressure discharge lamp LP2 is connected to the lamp inductor via connection j8 L5, the resonance capacitor C6 and with the auxiliary ignition capacitor C8 connected.
  • the starting device is used to start the half-bridge inverter Q1, Q2.
  • the Diac DC generates trigger pulses after switching on the control gear for the base of transistor Q2.
  • a connection of the Diacs DC is for this purpose with one arranged between the resistor R7 and the starting capacitor C9 Tap connected while the other connection of the DC DC via the base series resistor R4 is connected to the base of transistor Q2.
  • the inverter is a free-swinging half-bridge inverter with two Bipolar transistors Q1, Q2 are formed.
  • the inverter is controlled essentially by means of the toroidal transformer N1, N2, N3, whose primary winding N1 is arranged in the load circuit and its secondary windings N2, N3 in each case in a base circuit of one of the two inverter transistors Q1, Q2 are arranged.
  • the control device has for both transistors Q1, Q2 each have a basic series resistor R1 or R4, an inductor L3 or L4 and a resistor R2 connected in parallel with the base-emitter junction or R5, which improves the switching behavior of the inverter transistors Q1, Q2.
  • the supporting capacitor C2 is connected the mains voltage rectified by the mains voltage rectifier GL.
  • the start capacitor C9 is connected to the Breakdown voltage of the diac DC is charged so that the diac DC trigger pulses generated for driving the base electrode of transistor Q2 and thereby the oscillation of the half-bridge inverter Q1, Q2 triggers.
  • the base electrodes of the transistors Q1, Q2 are driven in such a way that the transistors Q1, Q2 switch alternately.
  • the starting capacitor C9 is turned on after the transistor Q2 is turned on via the diode D4 Switching path of transistor Q2 and discharged so far via emitter resistor R6 that the diac DC no longer generates any further trigger pulses.
  • the Load circuit and a high-frequency flows through the lamps LP1, LP2 connected in series AC, whose frequency is determined by the switching clock of transistors Q1, Q2 is determined.
  • a DC voltage is built up on the smoothing capacitor C3, whose value is approximately 1.4 times to 1.5 times the peak value of the mains voltage corresponds.
  • the coupling capacitor C4 is about half of the am Smoothing capacitor C3 applied voltage applied.
  • the transistors Q1, Q2 By alternating Switching the transistors Q1, Q2 becomes the center tap alternately with the negative one and the positive terminal of the smoothing capacitor C3 and the potential of the center tap correspondingly reduced or increased. Thereby flows in the load circuit determined by the transistor switching clock, high-frequency Alternating current. During the switching breaks of the transistors Q1, Q2, during the block both transistors Q1, Q2, holds the one stored in the lamp choke L5 Energy maintains the current flow through the corresponding freewheeling diode D2 or D3.
  • the lamp choke L5 forms a series resonance circuit with the resonance capacitor C6.
  • the electrical components of the circuit arrangement are dimensioned so that for igniting a gas discharge in the low-pressure discharge lamps LP1, LP2 on the resonance capacitor C6 and on the auxiliary ignition capacitor C8 a resonance-exaggerated Voltage is provided. After the gas discharge has ignited the series resonance circuit C6, L5 by the impedance of the discharge paths the low-pressure discharge lamps LP1, LP2 are damped.
  • the diode D1, the backup capacitor C2, the trapezoidal capacitor C7 and the resonance capacitor C6 form a harmonic filter that is in the switching cycle of the inverter Q1, Q2 and small amounts of charge proportional to the mains voltage in the smoothing capacitor C3 feeds.
  • the support capacitor C2, the resonance capacitor C6, the trapezoidal capacitor C7 and the diode D1 act together as a charge pump.
  • the trapezoidal capacitor C7 will then correspond to the potential difference caused by the difference the instantaneous value of the voltage at the support capacitor C2 and the potential at Center tap M is determined, loaded. There is a pulsating capacitor C2 DC voltage whose frequency is twice the mains voltage frequency is. If the mains voltage is just passing its apex, the Trapezoidal capacitor C7 charged to approximately 1.4 times the mains voltage value.
  • the trapezoidal capacitor C7 thereby receives a higher potential than the smoothing capacitor C3 and can therefore be Discharge diode D1 into smoothing capacitor C3.
  • the nominal value of the Capacitance of the support capacitor C2 at least 0.33 times the nominal value the capacitance of the resonance capacitor C6.
  • the nominal value of the capacitance of the support capacitor C2 should be the nominal value the capacitance of the resonance capacitor C6.
  • Suitable dimensioning of the electrical components is preferred in Table I. Specified embodiment.
  • the circuit arrangement according to the invention can have additional components, such as, for example, a device for preheating the electrode filaments of the low-pressure discharge lamps LP1, LP2 or a safety shutdown which switches off the inverter in the event of defective lamps.
  • the harmonic filter can have at least one further diode which is polarized in the forward direction, a first electrode of this diode having the direct voltage output of the mains voltage rectifier and the second electrode having a branch point with the capacitor connected in parallel with the direct voltage output of the mains voltage rectifier, with the resonance capacitor, with the at least one Capacitor of the harmonic filter and is connected to the at least one diode of the harmonic filter.

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  • Circuit Arrangements For Discharge Lamps (AREA)
  • Inverter Devices (AREA)

Abstract

The circuit has a mains voltage rectifier (GL), a capacitor (C2) parallel to the rectifier's d.c. output, a static converter (Q1,Q2), a series resonant load circuit (C6,L5), a smoothing capacitor (C3) and a harmonic filter (D1,C7). A first connection of at least one harmonic filter capacitor is connected to a resonant capacitor, an electrode of a filter diode and the rectifier output; its second connection is connected to the static converter output. The second electrode of the filter diode is connected to the smoothing capacitor.

Description

Die Erfindung betrifft eine Schaltungsanordnung zum Betrieb mindestens einer Niederdruckentladungslampe gemäß dem Oberbegriff des Patentanspruchs 1.The invention relates to a circuit arrangement for operating at least one low-pressure discharge lamp according to the preamble of claim 1.

I. Stand der Technik I. State of the art

Eine derartige Schaltungsanordnung ist beispielsweise in der europäischen Patentschrift EP 0 253 224 B1 offenbart. Diese Patentschrift beschreibt eine Schaltungsanordnung zum hochfrequenten Betrieb von Niederdruckentladungslampen. Die Schaltungsanordnung besitzt einen Netzspannungsgleichrichter, einen Wechselrichter, einen als Serienresonanzkreis ausgebildeten Lastkreis und ein Oberwellenfilter, das zur Reduktion des Netzstrom-Oberwellengehaltes vorgesehen ist. Das Oberwellenfilter weist eine Reihenschaltung von zwei Dioden, die in Durchlaßrichtung am Netzspannungsgleichrichter angeschlossen sind, einen Kondensator, der den Mittenabgriff zwischen den Dioden mit dem Spannungsausgang des Wechselrichters verbindet, und einen weiteren Kondensator, der den Mittenabgriff zwischen den Dioden mit einem Abgriff im Serienresonanzkreis verbindet, auf. Außerdem besitzt das Oberwellenfilter zwei weitere Dioden, die parallel zu den beiden Dioden des Oberwellenfilters geschaltet sind und deren Mittenabgriff mit dem Spannungsausgang des Wechselrichters verbunden ist.Such a circuit arrangement is for example in the European patent EP 0 253 224 B1. This patent describes a circuit arrangement for high-frequency operation of low-pressure discharge lamps. The Circuit arrangement has a mains voltage rectifier, an inverter, a load circuit designed as a series resonance circuit and a harmonic filter, which is intended to reduce the mains current harmonic content. The harmonic filter has a series connection of two diodes, which in the forward direction on Mains voltage rectifiers are connected to a capacitor which is the center tap connects between the diodes and the voltage output of the inverter, and another capacitor, the center tap between the diodes connects with a tap in the series resonance circuit. It also has Harmonic filter two more diodes that are parallel to the two diodes of the harmonic filter are switched and their center tap with the voltage output of the Inverter is connected.

In der europäischen Patentanmeldung EP 0 679 046 A1 ist eine Schaltungsanordnung zum Betrieb von Niederdruckentladungslampen mit vergleichsweise hohen Brennspannungen beschrieben. Diese Schaltungsanordnung besitzt eine Hochfrequenz-Gleichrichterbrücke, die die Aufladung des den Wechselrichter speisenden Glättungskondensators im Schaltrhythmus des Wechselrichters unterbricht und dadurch, im Zusammenspiel mit einer der Hochfrequenz-Gleichrichterbrücke vorgeschalteten Speicherdrossel und einem am Ausgang des Netzspannungsgleichrichters angeordneten Kondensator, in Wechselwirkung mit einem Stützkondensator und einem Gegenkopplungskondensator eine nahezu sinusförmige Netzstromentnahme mit einem Netzleistungsfaktor größer als 0,98 erlaubt.In the European patent application EP 0 679 046 A1 there is a circuit arrangement for operating low-pressure discharge lamps with comparatively high operating voltages described. This circuit arrangement has a high-frequency rectifier bridge, the charging of the smoothing capacitor feeding the inverter interrupts the switching rhythm of the inverter and in conjunction with one upstream of the high-frequency rectifier bridge Storage choke and one arranged at the output of the mains voltage rectifier Capacitor, interacting with a backup capacitor and a negative feedback capacitor an almost sinusoidal mains current draw with a Grid power factor greater than 0.98 allowed.

II. Darstellung der Erfindung II. Presentation of the invention

Es ist die Aufgabe der Erfindung, eine Schaltungsanordnung zum Betrieb mindestens einer Niederdruckentladungslampe bereitzustellen, die ein vereinfachtes Oberwellenfilter mit einer geringeren Anzahl von elektrischen Bauteilen besitzt.It is the object of the invention at least one circuit arrangement for operation to provide a low pressure discharge lamp, which is a simplified harmonic filter with a smaller number of electrical components.

Diese Aufgabe wird erfindungsgemäß durch die kennzeichnenden Merkmale des Patentanspruchs 1 gelöst. Besonders vorteilhafte Ausführungen der Erfindung sind in den Unteransprüchen beschrieben.This object is achieved by the characterizing features of Claim 1 solved. Particularly advantageous embodiments of the invention are shown in described the subclaims.

Die erfindungsgemäße Schaltungsanordnung weist einen Netzspannungsgleichrichter, einen parallel zum Gleichspannungsausgang des Netzspannungsgleichrichters geschalteten Kondensator, einen Wechselrichter mit einem nachgeschalteten, als Serienresonanzkreis ausgebildeten Lastkreis, einen parallel zum Gleichspannungseingang des Wechselrichters geschalteten Glättungskondensator und ein Oberwellenfilter, das mindestens eine Diode und einen Kondensator besitzt, auf. Erfindungsgemäß ist ein erster Anschluß des mindestens einen Kondensators des Oberwellenfilters mit dem Resonanzkondensator des Serienresonanzkreises, mit einer ersten Elektrode der mindestens einen Diode des Oberwellenfilters und mit dem Gleichspannungsausgang des Netzspannungsgleichrichters verbunden. Außerdem ist der zweite Anschluß des mindestens einen Kondensators des Oberwellenfilters mit dem Spannungsausgang des Wechselrichters und die zweite Elektrode der mindestens einen Diode des Oberwellenfilters mit dem Glättungskondensator verbunden.The circuit arrangement according to the invention has a mains voltage rectifier, one parallel to the DC voltage output of the mains voltage rectifier switched capacitor, an inverter with a downstream, as Series resonant circuit designed load circuit, one parallel to the DC voltage input the smoothing capacitor switched by the inverter and a harmonic filter, that has at least one diode and a capacitor. According to the invention is a first connection of the at least one capacitor of the harmonic filter with the resonance capacitor of the series resonance circuit, with a first electrode the at least one diode of the harmonic filter and with the DC voltage output of the mains voltage rectifier. In addition, the second Connection of the at least one capacitor of the harmonic filter to the voltage output of the inverter and the second electrode of the at least one Diode of the harmonic filter connected to the smoothing capacitor.

Auf diese Weise wird eine Schaltungsanordnung mit einem im Vergleich zum Stand der Technik vereinfachten und kostengünstigeren Oberwellenfilter, das aus einer verringerten Anzahl von elektrischen Bauteilen besteht, bereitgestellt. Vorteilhafterweise ist der parallel zum Gleichspannungsausgang des Netzspannungsgleichrichters geschaltete Kondensator so dimensioniert, daß seine Kapazität mindestens das 0,33-fache der Kapazität des Resonanzkondensators beträgt. Durch diese vorteilhafte Dimensionierung der Kapazitätswerte der vorgenannten Kondensatoren ist selbst für den Fall, daß der Spannungsabfall über der mindestens einen Niederdruckentladungslampe den Spannungsabfall an dem Glättungskondensator überschreitet, noch eine nahezu sinusförmige Netzstromentnahme und ein entsprechend geringer Oberwellengehalt gewährleistet. Um unerwünscht hohe Ladeströme für die Kondensatoren und damit eine hohe Belastung der elektrischen Bauteile zu vermeiden, ist die Kapazität des parallel zum Gleichspannungsausgang des Netzspannungsgleichrichters geschalteten Kondensators vorteilhafterweise höchstens so groß wie die Kapazität des Resonanzkondensators.In this way, a circuit arrangement with a compared to the state the technology simplified and less expensive harmonic filter, which from a reduced number of electrical components is provided. Advantageously is the parallel to the DC voltage output of the mains voltage rectifier switched capacitor dimensioned so that its capacity is at least 0.33 times the capacitance of the resonance capacitor. This advantageous dimensioning the capacitance values of the aforementioned capacitors is even for the case that the voltage drop across the at least one low-pressure discharge lamp exceeds the voltage drop across the smoothing capacitor an almost sinusoidal mains current draw and a correspondingly low harmonic content guaranteed. To undesirably high charging currents for the capacitors and thus to avoid high stress on the electrical components is the Capacity of the parallel to the DC voltage output of the mains voltage rectifier switched capacitor advantageously at most as large as the capacity of the resonance capacitor.

III. Beschreibung des bevorzugten Ausführungsbeispiels III. Description of the preferred embodiment

Nachstehend wird die Erfindung anhand eines bevorzugten Ausführungsbeispiels näher erläutert. Die Figur zeigt eine schematische Darstellung der erfindungsgemäßen Schaltungsanordnung entsprechend eines bevorzugten Ausführungsbeispiels der Erfindung. Diese Schaltungsanordnung besitzt einen Netzspannungseingang j1, j2 und eine an den Netzspannungseingang j1, j2 angeschlossene Filterschaltung, die aus einer stromkompensierten Filterdrossel L1, einer nicht-stromkompensierten Filterdrossel L2 und einem Kondensator C1 besteht, sowie einen der Filterschaltung nachgeschalteten Netzspannungsgleichrichter GL. Parallel zum Gleichspannungsausgang des Netzspannungsgleichrichters GL ist, an den Verzweigungspunkten j3, j4, ein Stützkondensator C2 geschaltet. An den positiven Ausgang des Netzspannungsgleichrichters GL ist über den Verzweigungspunkt j3 die Anode einer Diode D1 angeschlossen. Die Kathode der Diode D1 ist mit dem positiven Anschluß eines Glättungskondensators C3 verbunden. Der negative Anschluß des Glättungskondensators C3 ist über den Verzweigungspunkt j4 mit dem negativen Ausgang des Netzspannungsgleichrichters GL verbunden. Der Glättungskondensator C3 dient als Gleichspannungsquelle für einen freischwingenden Halbbrückenwechselrichter, der von zwei Transistoren Q1, Q2, seiner Ansteuerungsvorrichtung N1, N2, N3, L3, L4, R1, R2, R4, R5 und den Emitterwiderständen R3, R6 sowie von zwei Freilaufdioden D2, D3, die jeweils parallel zur Kollektor-Emitter-Strecke eines der Transistoren Q1 bzw. Q2 geschaltet sind, gebildet wird. Der Gleichspannungseingang des Halbbrückenwechselrichters Q1, Q2, der von dem Kollektoranschluß des Transistors Q1 und dem Emitteranschluß des Transistors Q2 bzw. dem Emitterwiderstand R5 gebildet wird, ist parallel zum Glättungskondensator C3 angeordnet. An den Spannungsausgang, das heißt, an den Mittenabgriff M, des Halbbrückenwechselrichters Q1, Q2 ist ein als Serienresonanzkreis ausgebildeter Lastkreis angeschlossen. Der Lastkreis weist die Primärwicklung N1 des zur Ansteuerungsvorrichtung gehörenden Ringkerntransformators, einen Koppelkondensator C4, eine Lampendrossel L5 und einen Resonanzkondensator C6, die alle in Serie geschaltet sind, auf. Der Mittenabgriff M des Halbbrückenwechselrichters Q1, Q2 ist über die Primärwicklung N1, den Koppelkondensator C4, die Lampendrossel L5 und den Resonanzkondensator C6 mit der Anode der Diode D1 und mit dem Verzweigungspunkt j3 verbunden. Die Schaltungsanordnung weist ferner einen Trapezkondensator C7 auf, dessen erster Anschluß mit der Anode der Diode D1 und mit dem Verzweigungspunkt j3 und dessen zweiter Anschluß mit dem Mittenabgriff M des Halbbrückenwechselrichters Q1, Q2 verbunden ist. Außerdem besitzt die Schaltungsanordnung eine Startvorrichtung, die aus einem Diac DC, einem Startkondensator C9, einem Widerstand R7 und einer Diode D4 besteht, und Anschlüsse j5, j6, j7, j8 für zwei in Reihe geschaltete Niederdruckentladungslampen LP1, LP2, sowie einen Zündhilfskondensator C8. Der Zündhilfskondensator C8 ist parallel zur zweiten Niederdruckentladungslampe LP2 angeordnet. Ein erster Anschluß des Zündhilfskondensators C8 ist über einen Knotenpunkt im Lastkreis mit dem Resonanzkondensator C6 und mit der Lampendrossel L5 verbunden. Der zweite Anschluß des Zündhilfskondensators C8 ist mit der zweiten Elektrode der ersten Niederdruckentladungslampe LP1 und mit der ersten Elektrode der zweiten Niederdruckentladungslampe LP2 verbunden. Die erste Elektrode der ersten Niederdruckentladungslampe LP1 ist über den Anschluß j5 mit der Kathode der Diode D1, mit dem Kollektor des Transistors Q1 und mit dem positiven Anschluß des Glättungskondensators C3 verbunden und über den Anschluß j6, den Widerstand R7 und den Startkondensator C9 mit dem Anschluß j4 sowie mit dem negativen Anschluß des Glättungskondensators C3 verbunden. Die zweite Elektrode der zweiten Niederdruckentladungslampe LP2 ist über den Anschluß j8 mit der Lampendrossel L5, dem Resonanzkondensator C6 und mit dem Zündhilfskondensator C8 verbunden.The invention based on a preferred embodiment explained in more detail. The figure shows a schematic representation of the invention Circuit arrangement according to a preferred embodiment of the Invention. This circuit arrangement has a mains voltage input j1, j2 and a filter circuit connected to the mains voltage input j1, j2, which off a current-compensated filter choke L1, a non-current-compensated filter choke L2 and a capacitor C1, and one downstream of the filter circuit Mains voltage rectifier GL. Parallel to the DC voltage output of the mains voltage rectifier GL is at the junction points j3, j4 Support capacitor C2 switched. To the positive output of the mains voltage rectifier GL is connected to the anode of a diode D1 via junction j3. The cathode of the diode D1 is with the positive connection of a smoothing capacitor C3 connected. The negative terminal of the smoothing capacitor C3 is across junction j4 with the negative output of the line rectifier GL connected. The smoothing capacitor C3 serves as a DC voltage source for a free-swinging half-bridge inverter that by two transistors Q1, Q2, its control device N1, N2, N3, L3, L4, R1, R2, R4, R5 and the emitter resistors R3, R6 and two freewheeling diodes D2, D3, each parallel to the collector-emitter path of one of the transistors Q1 or Q2 are switched, is formed. The DC input of the half-bridge inverter Q1, Q2 from the collector terminal of transistor Q1 and the emitter terminal of the transistor Q2 and the emitter resistor R5 are formed is arranged in parallel to the smoothing capacitor C3. To the voltage output, that is, at the center tap M, of the half-bridge inverter Q1, Q2 a load circuit designed as a series resonance circuit is connected. The load circuit the primary winding N1 of the toroidal transformer belonging to the control device, a coupling capacitor C4, a lamp inductor L5 and one Resonance capacitor C6, all of which are connected in series. The center tap M of the half-bridge inverter Q1, Q2 is via the primary winding N1, the coupling capacitor C4, the lamp inductor L5 and the resonance capacitor C6 with the Anode of the diode D1 and connected to the junction j3. The circuit arrangement also has a trapezoidal capacitor C7, the first connection with the anode of the diode D1 and with the branch point j3 and its second connection with the center tap M of the half-bridge inverter Q1, Q2 connected is. In addition, the circuit arrangement has a starting device, the from a diac DC, a starting capacitor C9, a resistor R7 and one Diode D4 exists, and connections j5, j6, j7, j8 for two low-pressure discharge lamps connected in series LP1, LP2, and an auxiliary ignition capacitor C8. The auxiliary ignition capacitor C8 is arranged parallel to the second low-pressure discharge lamp LP2. A first connection of the auxiliary ignition capacitor C8 is via a node in the load circuit with the resonance capacitor C6 and with the lamp choke L5 connected. The second connection of the auxiliary ignition capacitor C8 is connected to the second Electrode of the first low-pressure discharge lamp LP1 and with the first electrode connected to the second low-pressure discharge lamp LP2. The first electrode of the First low pressure discharge lamp LP1 is connected to the cathode via connection j5 the diode D1, with the collector of the transistor Q1 and with the positive terminal of the smoothing capacitor C3 and via the connection j6, the resistor R7 and the starting capacitor C9 with the connection j4 and with the negative Terminal of the smoothing capacitor C3 connected. The second electrode of the second low-pressure discharge lamp LP2 is connected to the lamp inductor via connection j8 L5, the resonance capacitor C6 and with the auxiliary ignition capacitor C8 connected.

Die Startvorrichtung dient zum Anschwingen des Halbbrückenwechselrichters Q1, Q2. Der Diac DC erzeugt nach dem Einschalten des Betriebsgerätes Triggerimpulse für die Basis des Transistors Q2. Ein Anschluß des Diacs DC ist zu diesem Zweck mit einem zwischen dem Widerstand R7 und dem Startkondensator C9 angeordneten Abgriff verbunden, während der andere Anschluß des Diacs DC über den Basisvorwiderstand R4 mit der Basis des Transistors Q2 verbunden ist. Außerdem ist der vorgenannte, zwischen dem Startkondensator C9, dem Widerstand R7 und dem Diac DC angeordnete Abgriff über eine in Durchlaßrichtung gepolte Diode D4 mit dem Mittenabgriff M des Halbbrückenwechselrichters Q1, Q2 verbunden.The starting device is used to start the half-bridge inverter Q1, Q2. The Diac DC generates trigger pulses after switching on the control gear for the base of transistor Q2. A connection of the Diacs DC is for this purpose with one arranged between the resistor R7 and the starting capacitor C9 Tap connected while the other connection of the DC DC via the base series resistor R4 is connected to the base of transistor Q2. In addition, the the aforementioned, between the starting capacitor C9, the resistor R7 and the diac DC arranged tap via a forward polarized diode D4 with the Center tap M of the half-bridge inverter Q1, Q2 connected.

Der Wechselrichter ist als freischwingender Halbbrückenwechselrichter mit zwei Bipolartransistoren Q1, Q2 ausgebildet. Die Ansteuerung des Wechselrichters erfolgt im wesentlichen mittels des Ringkerntransformators N1, N2, N3, dessen Primärwicklung N1 in dem Lastkreis angeordnet ist und dessen Sekundärwicklungen N2, N3 jeweils in einem Basisstromkreis eines der der beiden Wechselrichtertransistoren Q1, Q2 angeordnet sind. Die Ansteuerungsvorrichtung weist für beide Transistoren Q1, Q2 jeweils einen Basisvorwiderstand R1 bzw. R4, eine Induktivität L3 bzw. L4 und einen parallel zum Basis-Emitter-Übergang geschalteten Widerstand R2 bzw. R5, der das Schaltverhalten der Wechselrichter-Transistoren Q1, Q2 verbessert, auf.The inverter is a free-swinging half-bridge inverter with two Bipolar transistors Q1, Q2 are formed. The inverter is controlled essentially by means of the toroidal transformer N1, N2, N3, whose primary winding N1 is arranged in the load circuit and its secondary windings N2, N3 in each case in a base circuit of one of the two inverter transistors Q1, Q2 are arranged. The control device has for both transistors Q1, Q2 each have a basic series resistor R1 or R4, an inductor L3 or L4 and a resistor R2 connected in parallel with the base-emitter junction or R5, which improves the switching behavior of the inverter transistors Q1, Q2.

Nach dem Einschalten der Schaltungsanordnung liegt an dem Stützkondensator C2 die durch den Netzspannungsgleichrichter GL gleichgerichtete Netzspannung an. Über die Diode D1 und den Widerstand R7 wird der Startkondensator C9 auf die Durchbruchsspannung des Diac DC aufgeladen, so daß der Diac DC Triggerimpulse zur Ansteuerung der Basiselektrode des Transistors Q2 erzeugt und dadurch das Anschwingen des Halbbrückenwechselrichters Q1, Q2 auslöst. Mit Hilfe des Ringkerntransformators RK werden die Basiselektroden der Transistoren Q1, Q2 derart angesteuert, daß die Transistoren Q1, Q2 alternierend schalten. Der Startkondensator C9 wird nach dem Durchschalten des Transistors Q2 über die Diode D4, über die Schaltstrecke des Transistors Q2 und über den Emitterwiderstand R6 so weit entladen, daß der Diac DC keine weiteren Triggerimpulse mehr generiert. Durch den Lastkreis und durch die in Reihe geschalteten Lampen LP1, LP2 fließt ein hochfrequenter Wechselstrom, dessen Frequenz durch den Schalttakt der Transistoren Q1, Q2 bestimmt ist. Am Glättungskondensator C3 wird eine Gleichspannung aufgebaut, deren Wert ungefähr dem 1,4-fachen bis 1,5-fachen des Spitzenwertes der Netzspannung entspricht. Der Koppelkondensator C4 wird ungefähr auf die Hälfte der am Glättungskondensator C3 anliegenden Spannung aufgeladen. Durch alternierendes Schalten der Transistoren Q1, Q2 wird der Mittenabgriff abwechselnd mit dem negativen und dem positiven Anschluß des Glättungskondensators C3 verbunden und das Potential des Mittenabgriffs entsprechend gesenkt oder angehoben. Dadurch fließt im Lastkreis ein durch den Transistorschalttakt bestimmter, hochfrequenter Wechselstrom. Während der Schaltpausen der Transistoren Q1, Q2, während der beide Transistoren Q1, Q2 sperren, hält die in der Lampendrossel L5 gespeicherte Energie den Stromfluß durch die entsprechende Freilaufdiode D2 bzw. D3 aufrecht. Die Lampendrossel L5 bildet mit dem Resonanzkondensator C6 einen Serienresonanzkreis. Die elektrischen Bauteile der Schaltungsanordnung sind so dimensioniert, daß zum Zünden einer Gasentladung in den Niederdruckentladungslampen LP1, LP2 an dem Resonanzkondensator C6 und an dem Zündhilfskondensator C8 eine resonanzüberhöhte Spannung bereitgestellt wird. Nach erfolgter Zündung der Gasentladung wird der Serienresonanzkreis C6, L5 durch die Impedanz der Entladungsstrecken der Niederdruckentladungslampen LP1, LP2 gedämpft.After switching on the circuit arrangement, the supporting capacitor C2 is connected the mains voltage rectified by the mains voltage rectifier GL. Via the diode D1 and the resistor R7, the start capacitor C9 is connected to the Breakdown voltage of the diac DC is charged so that the diac DC trigger pulses generated for driving the base electrode of transistor Q2 and thereby the oscillation of the half-bridge inverter Q1, Q2 triggers. With the help of the toroidal transformer RK, the base electrodes of the transistors Q1, Q2 are driven in such a way that the transistors Q1, Q2 switch alternately. The starting capacitor C9 is turned on after the transistor Q2 is turned on via the diode D4 Switching path of transistor Q2 and discharged so far via emitter resistor R6 that the diac DC no longer generates any further trigger pulses. By the Load circuit and a high-frequency flows through the lamps LP1, LP2 connected in series AC, whose frequency is determined by the switching clock of transistors Q1, Q2 is determined. A DC voltage is built up on the smoothing capacitor C3, whose value is approximately 1.4 times to 1.5 times the peak value of the mains voltage corresponds. The coupling capacitor C4 is about half of the am Smoothing capacitor C3 applied voltage applied. By alternating Switching the transistors Q1, Q2 becomes the center tap alternately with the negative one and the positive terminal of the smoothing capacitor C3 and the potential of the center tap correspondingly reduced or increased. Thereby flows in the load circuit determined by the transistor switching clock, high-frequency Alternating current. During the switching breaks of the transistors Q1, Q2, during the block both transistors Q1, Q2, holds the one stored in the lamp choke L5 Energy maintains the current flow through the corresponding freewheeling diode D2 or D3. The lamp choke L5 forms a series resonance circuit with the resonance capacitor C6. The electrical components of the circuit arrangement are dimensioned so that for igniting a gas discharge in the low-pressure discharge lamps LP1, LP2 on the resonance capacitor C6 and on the auxiliary ignition capacitor C8 a resonance-exaggerated Voltage is provided. After the gas discharge has ignited the series resonance circuit C6, L5 by the impedance of the discharge paths the low-pressure discharge lamps LP1, LP2 are damped.

Die Diode D1, der Stützkondensator C2, der Trapezkondensator C7 und der Resonanzkondensator C6 bilden ein Oberwellenfilter, das im Schalttakt des Wechselrichters Q1, Q2 und proportional zur Netzspannung kleine Ladungsmengen in den Glättungskondensator C3 einspeist. Der Stützkondensator C2, der Resonanzkondensator C6, der Trapezkondensator C7 und die Diode D1 wirken zusammen als Ladungspumpe.The diode D1, the backup capacitor C2, the trapezoidal capacitor C7 and the resonance capacitor C6 form a harmonic filter that is in the switching cycle of the inverter Q1, Q2 and small amounts of charge proportional to the mains voltage in the smoothing capacitor C3 feeds. The support capacitor C2, the resonance capacitor C6, the trapezoidal capacitor C7 and the diode D1 act together as a charge pump.

Schaltet der Transistor Q2 durch, so wird der Mittenabgriff M des Wechselrichters Q1, Q2 durch die leitfähige Kollektor-Emitter-Strecke des Transistors Q2 mit dem negativen Pol des Netzspannungsgleichrichterausgangs verbunden. Der Trapezkondensator C7 wird dann entsprechend der Potentialdifferenz, die durch die Differenz des Momentanwertes der Spannung am Stützkondensator C2 und dem Potential am Mittenabgriff M bestimmt ist, geladen. Am Stützkondensator C2 liegt eine pulsierende Gleichspannung an, deren Frequenz doppelt so groß wie die Netzspannungsfrequenz ist. Durchläuft die Netzspannung gerade ihren Scheitelpunkt, so wird der Trapezkondensator C7 ungefähr auf das 1,4-fache des Netzspannungswertes aufgeladen.If the transistor Q2 turns on, the center tap M of the inverter Q1, Q2 through the conductive collector-emitter path of the transistor Q2 with the negative pole of the mains voltage rectifier output connected. The trapezoidal capacitor C7 will then correspond to the potential difference caused by the difference the instantaneous value of the voltage at the support capacitor C2 and the potential at Center tap M is determined, loaded. There is a pulsating capacitor C2 DC voltage whose frequency is twice the mains voltage frequency is. If the mains voltage is just passing its apex, the Trapezoidal capacitor C7 charged to approximately 1.4 times the mains voltage value.

In der darauf folgenden Sperrphase des Transistors Q2 wird das Potential am Mittenabgriff M des Wechselrichters Q1, Q2 und entsprechend das Potential am Trapezkondensator C7 sprunghaft angehoben. Der Trapezkondensator C7 erhält dadurch ein höheres Potential als der Glättungskondensator C3 und kann sich daher über die Diode D1 in den Glättungskondensator C3 entladen.In the subsequent blocking phase of transistor Q2, the potential at the center tap M of the inverter Q1, Q2 and accordingly the potential at the trapezoidal capacitor C7 suddenly raised. The trapezoidal capacitor C7 thereby receives a higher potential than the smoothing capacitor C3 and can therefore be Discharge diode D1 into smoothing capacitor C3.

Beim anschließenden Durchschalten des Transistors Q1 wird das Potential des Mittenabgriffs M auf das Potential des Glättungskondensators C3 angehoben. Die Lampendrossel L5 wird in Gegenrichtung geladen.When transistor Q1 is subsequently switched on, the potential of the center tap becomes M raised to the potential of the smoothing capacitor C3. The lamp choke L5 is charged in the opposite direction.

In der folgenden Sperrphase des Transistors Q1 fließt die in der Lampendrossel L5 gespeicherte Energie in den Trapezkondensator C7 und in den Resonanzkondensator C6 ab. Danach schaltet wieder der Transistor Q2 durch.In the following blocking phase of transistor Q1, that flows in lamp inductor L5 stored energy in the trapezoidal capacitor C7 and in the resonance capacitor C6 from. Then the transistor Q2 turns on again.

Pro Schaltzyklus des Wechselrichters Q1, Q2 bzw. pro Periode der hochfrequenten Wechselspannung wird auf diese Weise einmal Energie in den Glättungskondensator C3 gepumpt. Die Frequenz des im Lastkreis fließenden Wechselstroms beträgt typischerweise mehr als 20 kHz. Die in den Glättungskondensator C3 gepumpten Ladungsportionen sind proportional zu dem Momentanwert der am Stützkondensator C2 anliegenden Spannung.Per switching cycle of the inverter Q1, Q2 or per period of the high-frequency In this way, AC voltage becomes energy in the smoothing capacitor C3 pumped. The frequency of the alternating current flowing in the load circuit is typically more than 20 kHz. The portions of charge pumped into the smoothing capacitor C3 are proportional to the instantaneous value on the support capacitor C2 applied voltage.

Überschreitet der Spitzenwert der Lampenspannung der Serienschaltung der beiden Niederdruckentladungslampen LP1, LP2 die Hälfte der Spannung des Glättungskondensators C3, so wird das Potential am Mittenabgriff M beim Umschwingen auf ein Potential abgesenkt, das unterhalb des Massepotentials des Anschlusses j4 liegt, und der Resonanzkondensator C6 wird im Bereich des Netzspannungsnulldurchgangs nachgeladen. Durch die bei diesem Ausführungsbeispiel gewählte Dimensionierung (Tabelle I) der Kapazitäten des Stützkondensators C2 und des Resonanzkondensators C6 ist gewährleistet, daß das Nachladen des Resonanzkondensators C6 vornehmlich über den Stützkondensator C2 und nicht hauptsächlich aus dem Stromnetz erfolgt. Der Oberwellengehalt des Netzstromes kann daher gering gehalten werden. Damit das Nachladen des Resonanzkondensators C6 während des Netzspannungsnulldurchgangs vornehmlich über den Stützkondensator C2 erfolgt, sollte der Nominalwert der Kapazität des Stützkondensators C2 mindestens das 0,33-fache des Nominalwertes der Kapazität des Resonanzkondensators C6 betragen. Um zu hohe Ladeströme zu vermeiden, sollte der Nominalwert der Kapazität des Stützkondensators C2 den Nominalwert der Kapazität des Resonanzkondensators C6 nicht überschreiten.Exceeds the peak lamp voltage of the series connection of the two Low pressure discharge lamps LP1, LP2 half the voltage of the smoothing capacitor C3, so the potential at the center tap M when switching to Potential which is below the ground potential of the connection j4, and the resonance capacitor C6 is in the area of the mains voltage zero crossing reloaded. Due to the dimensioning chosen in this embodiment (Table I) the capacitances of the backup capacitor C2 and the resonance capacitor C6 ensures that the recharging of the resonance capacitor C6 primarily via the support capacitor C2 and not mainly from the power grid. The harmonic content of the mains current can therefore be kept low. In order to reloading the resonance capacitor C6 during the mains voltage zero crossing mainly via the capacitor C2, the nominal value of the Capacitance of the support capacitor C2 at least 0.33 times the nominal value the capacitance of the resonance capacitor C6. To keep charging currents too high avoid, the nominal value of the capacitance of the support capacitor C2 should be the nominal value the capacitance of the resonance capacitor C6.

In Tabelle I ist eine geeignete Dimensionierung der elektrischen Bauteile des bevorzugten Ausführungsbeispiels angegeben.Suitable dimensioning of the electrical components is preferred in Table I. Specified embodiment.

Die Erfindung beschränkt sich nicht auf das oben näher erläuterte Ausführungsbeispiel. Beispielsweise kann die erfindungsgemäße Schaltungsanordnung zusätzliche Komponenten, wie zum Beispiel eine Vorrichtung zum Vorheizen der Elektrodenwendeln der Niederdruckentladungslampen LP1, LP2 oder eine Sicherheitsabschaltung, die den Wechselrichter bei defekten Lampen abschaltet, aufweisen. Außerdem kann das Oberwellenfilter mindestens eine weitere, in Durchlaßrichtung gepolte Diode aufweisen, wobei eine erste Elektrode dieser Diode mit dem Gleichspannungsausgang des Netzspannungsgleichrichters und die zweite Elektrode über einen Verzweigungspunkt mit dem parallel zum Gleichspannungsausgang des Netzspannungsgleichrichters geschalteten Kondensator, mit dem Resonanzkondensator, mit dem mindestens einen Kondensator des Oberwellenfilters und mit der mindestens einen Diode des Oberwellenfilters verbunden ist. Dimensionierung der im Ausführungsbeispiel verwendeten elektrischen Bauteile R1, R4 8,2 Ω R2, R5 47 Ω R3, R6 0,56 Ω R7 1 MΩ L1 2 * 3,9 mH L2 2 * 39 mH L3, L4 10 µH L5 1,7 mH C1 150 nF C2 4,7 nF C3 10 µF C4 220 nF C6 10 nF C7 6,8 nF C8 560 pF C9 100 nF Q1, Q2 BUF644 D1, D2, D3, D4 BYD33J N1, N2, N3 5:2:2 Wicklungen LP1, LP2 Leuchtstofflampe mit jeweils 18 W Leistungsaufnahme, z.B. Osram Dulux D/E 18W The invention is not limited to the exemplary embodiment explained in more detail above. For example, the circuit arrangement according to the invention can have additional components, such as, for example, a device for preheating the electrode filaments of the low-pressure discharge lamps LP1, LP2 or a safety shutdown which switches off the inverter in the event of defective lamps. In addition, the harmonic filter can have at least one further diode which is polarized in the forward direction, a first electrode of this diode having the direct voltage output of the mains voltage rectifier and the second electrode having a branch point with the capacitor connected in parallel with the direct voltage output of the mains voltage rectifier, with the resonance capacitor, with the at least one Capacitor of the harmonic filter and is connected to the at least one diode of the harmonic filter. Dimensioning of the electrical components used in the exemplary embodiment R1, R4 8.2 Ω R2, R5 47 Ω R3, R6 0.56 Ω R7 1 MΩ L1 2 * 3.9 mH L2 2 * 39 mH L3, L4 10 µH L5 1.7 mH C1 150 nF C2 4.7 nF C3 10 µF C4 220 nF C6 10 nF C7 6.8 nF C8 560 pF C9 100 nF Q1, Q2 BUF644 D1, D2, D3, D4 BYD33J N1, N2, N3 5: 2: 2 windings LP1, LP2 Fluorescent lamp each with 18 W power consumption, e.g. Osram Dulux D / E 18W

Claims (5)

Schaltungsanordnung zum Betrieb mindestens einer Niederdruckentladungslampe mit einem Netzspannungsgleichrichter (GL), einem Kondensator (C2), der parallel zum Gleichspannungsausgang (+, -) des Netzspannungsgleichrichters (GL) geschaltet ist, einem Wechselrichter (Q1, Q2) mit einem Gleichspannungseingang und einem Spannungsausgang (M), einem als Serienresonanzkreis ausgebildeten Lastkreis, der an den Spannungsausgang (M) des Wechselrichters (Q1, Q2) angeschlossen ist, wobei der Lastkreis zumindest einen Resonanzkondensator (C6), eine Lampendrossel (L5) und Anschlüsse (j5, j6, j7, j8) für wenigstens eine Niederdruckentladungslampe (LP1, LP2) aufweist, einen Glättungskondensator (C3), der parallel zum Gleichspannungseingang des Wechselrichers (Q1, Q2) geschaltet ist, einem Oberwellenfilter, das mindestens eine Diode (D1) und mindestens einen Kondensator (C7) aufweist,
dadurch gekennzeichnet, daß ein erster Anschluß des mindestens einen Kondensators (C7) des Oberwellenfilters mit dem Resonantkondensator (C6), mit einer ersten Elektrode der mindestens eine Diode (D1) des Oberwellenfilters und mit dem Gleichspannungsausgang (+, -) des Netzspannungsgleichrichters (GL) verbunden ist, der zweite Anschluß des mindestens einen Kondensators (C7) des Oberwellenfilters mit dem Spannungsausgang (M) des Wechselrichters (Q1, Q2) verbunden ist, die zweite Elektrode der mindestens einen Diode (D1) des Oberwellenfilters mit dem Glättungskondensator (C3) verbunden ist. Circuit arrangement for operating at least one low-pressure discharge lamp a mains voltage rectifier (GL), a capacitor (C2) which is connected in parallel to the DC voltage output (+, -) of the mains voltage rectifier (GL), an inverter (Q1, Q2) with a DC voltage input and a voltage output (M), a load circuit designed as a series resonance circuit, which is connected to the voltage output (M) of the inverter (Q1, Q2), the load circuit having at least one resonance capacitor (C6), a lamp inductor (L5) and connections (j5, j6, j7, j8) for has at least one low-pressure discharge lamp (LP1, LP2), a smoothing capacitor (C3) which is connected in parallel to the DC voltage input of the inverter (Q1, Q2), a harmonic filter which has at least one diode (D1) and at least one capacitor (C7),
characterized in that a first connection of the at least one capacitor (C7) of the harmonic filter to the resonant capacitor (C6), to a first electrode the at least one diode (D1) of the harmonic filter and to the DC voltage output (+, -) of the mains voltage rectifier (GL) is connected, the second connection of the at least one capacitor (C7) of the harmonic filter is connected to the voltage output (M) of the inverter (Q1, Q2), the second electrode of the at least one diode (D1) of the harmonic filter is connected to the smoothing capacitor (C3). Schaltungsanordnung nach Anspruch 1, dadurch gekennzeichnet, daß der Nominalwert der Kapazität des parallel zum Gleichspannungsausgang (+, -) des Netzspannungsgleichrichters (GL) geschalteten Kondensators (C2) größer oder gleich dem 0,33-fachen des Nominalwertes der Kapazität des Resonanzkondensators (C6) ist.Circuit arrangement according to claim 1, characterized in that the Nominal value of the capacitance of the parallel to the DC voltage output (+, -) of the mains voltage rectifier (GL) connected capacitor (C2) larger or equal to 0.33 times the nominal value of the capacitance of the resonance capacitor (C6) is. Schaltungsanordnung nach Anspruch 1, dadurch gekennzeichnet, daß der Nominalwert der Kapazität des parallel zum Gleichspannungsausgang (+, -) des Netzspannungsgleichrichters (GL) geschalteten Kondensators (C2) kleiner oder gleich dem Nominalwert der Kapazität des Resonanzkondensators (C6) ist.Circuit arrangement according to claim 1, characterized in that the Nominal value of the capacitance of the parallel to the DC voltage output (+, -) of the mains voltage rectifier (GL) connected capacitor (C2) smaller or equal to the nominal value of the capacitance of the resonance capacitor (C6) is. Schaltungsanordnung nach Anspruch 1, dadurch gekennzeichnet, daß das Oberwellenfilter aus dem parallel zum Gleichspannungsausgang (+, -) des Netzspannungsgleichrichters (GL) geschalteten Kondensator (C2), dem Resonanzkondensator (C6), dem mindestens einen Kondensator (C7) und der mindestens einen Diode (D1) besteht.Circuit arrangement according to claim 1, characterized in that the Harmonic filter from the parallel to the DC voltage output (+, -) Mains voltage rectifier (GL) switched capacitor (C2), the resonant capacitor (C6), the at least one capacitor (C7) and the there is at least one diode (D1). Schaltungsanordnung nach Anspruch 1, dadurch gekennzeichnet, daß das Oberwellenfilter mindestens eine weitere, Diode aufweist, wobei eine erste Elektrode dieser Diode mit dem Gleichspannungsausgang des Netzspannungsgleichrichters und die zweite Elektrode über einen Verzweigungspunkt mit dem parallel zum Gleichspannungsausgang des Netzspannungsgleichrichters geschalteten Kondensator, mit dem Resonanzkondensator, mit dem mindestens einen Kondensator des Oberwellenfilters und mit der mindestens einen Diode des Oberwellenfilters verbunden ist.Circuit arrangement according to claim 1, characterized in that the Harmonic filter has at least one further diode, a first Electrode of this diode with the DC voltage output of the mains voltage rectifier and the second electrode via a branch point with the parallel to the DC voltage output of the mains voltage rectifier switched capacitor, with the resonance capacitor, with the at least one capacitor of the harmonic filter and with the at least a diode of the harmonic filter is connected.
EP00100767A 1999-02-11 2000-01-15 Circuit for operating at least one low-pressure discharge lamp Expired - Lifetime EP1028606B1 (en)

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JP2004079331A (en) * 2002-08-19 2004-03-11 Matsushita Electric Works Ltd Discharge lamp lighting device
DE10343275A1 (en) 2003-09-18 2005-05-12 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Circuit arrangement for generating AC voltage from a DC voltage
DE102004033377A1 (en) * 2004-07-09 2006-02-16 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Circuit arrangement with a switch-relieved full bridge for the operation of lamps
DE102005058484A1 (en) * 2005-12-07 2007-06-14 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Circuit arrangement and method for operating at least one LED
ATE506835T1 (en) * 2007-04-23 2011-05-15 Osram Gmbh CIRCUIT ARRANGEMENT FOR IGNITING AND OPERATING AT LEAST ONE DISCHARGE LAMP

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Publication number Priority date Publication date Assignee Title
EP0244644A1 (en) * 1986-04-07 1987-11-11 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Circuit arrangement for the high-frequency operation of low-pressure discharge lamps
EP0253224A2 (en) * 1986-07-14 1988-01-20 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Circuit arrangement for operating low-pressure discharge lamps

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Publication number Priority date Publication date Assignee Title
DE3829388A1 (en) * 1988-08-30 1990-03-01 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh CIRCUIT ARRANGEMENT FOR OPERATING A LOAD
DE4140557A1 (en) * 1991-12-09 1993-06-17 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh CIRCUIT ARRANGEMENT FOR OPERATING ONE OR MORE LOW-PRESSURE DISCHARGE LAMPS
DE4410492A1 (en) * 1994-03-25 1995-09-28 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Circuit arrangement for operating low-pressure discharge lamps

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Publication number Priority date Publication date Assignee Title
EP0244644A1 (en) * 1986-04-07 1987-11-11 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Circuit arrangement for the high-frequency operation of low-pressure discharge lamps
EP0253224A2 (en) * 1986-07-14 1988-01-20 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Circuit arrangement for operating low-pressure discharge lamps

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ATE291827T1 (en) 2005-04-15
DE19905487A1 (en) 2000-08-31
JP4514269B2 (en) 2010-07-28
JP2000235897A (en) 2000-08-29
TW587407B (en) 2004-05-11
US6259213B1 (en) 2001-07-10
KR100632531B1 (en) 2006-10-09
EP1028606A3 (en) 2003-03-19
CN1263430A (en) 2000-08-16
CA2297419C (en) 2009-01-27
KR20010006628A (en) 2001-01-26
CN1166257C (en) 2004-09-08
CA2297419A1 (en) 2000-08-11
EP1028606B1 (en) 2005-03-23
DE50009827D1 (en) 2005-04-28

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