EP0424280A1 - Electronic control circuit for a direct current energised pulse motor - Google Patents

Electronic control circuit for a direct current energised pulse motor Download PDF

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Publication number
EP0424280A1
EP0424280A1 EP90420426A EP90420426A EP0424280A1 EP 0424280 A1 EP0424280 A1 EP 0424280A1 EP 90420426 A EP90420426 A EP 90420426A EP 90420426 A EP90420426 A EP 90420426A EP 0424280 A1 EP0424280 A1 EP 0424280A1
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EP
European Patent Office
Prior art keywords
coil
signal
chopper
voltage
input
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Granted
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EP90420426A
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German (de)
French (fr)
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EP0424280B1 (en
Inventor
Alain Kobilsek
Dominique Villard
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Merlin Gerin SA
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Merlin Gerin SA
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01H—ELECTRIC SWITCHES; RELAYS; SELECTORS; EMERGENCY PROTECTIVE DEVICES
    • H01H47/00—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current
    • H01H47/22—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current for supplying energising current for relay coil
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F7/00—Magnets
    • H01F7/06—Electromagnets; Actuators including electromagnets
    • H01F7/08—Electromagnets; Actuators including electromagnets with armatures
    • H01F7/18—Circuit arrangements for obtaining desired operating characteristics, e.g. for slow operation, for sequential energisation of windings, for high-speed energisation of windings
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01H—ELECTRIC SWITCHES; RELAYS; SELECTORS; EMERGENCY PROTECTIVE DEVICES
    • H01H3/00—Mechanisms for operating contacts
    • H01H3/22—Power arrangements internal to the switch for operating the driving mechanism
    • H01H3/30—Power arrangements internal to the switch for operating the driving mechanism using spring motor
    • H01H3/3005—Charging means
    • H01H3/3021—Charging means using unidirectional coupling

Definitions

  • the invention relates to an electronic circuit for controlling a vibrating motor comprising a control coil, means for controlling the passage of current in the coil causing, when a control signal from the vibrating motor is applied to them, alternately the power supply. current from the coil during an active period and non-supply of the coil during a rest period.
  • a device for arming a spring of a control mechanism of a breaking device in particular an electrical switch or circuit breaker, as described, for example, in French patent 2,593,323
  • the control coil of the vibrating motor is supplied by a periodic current.
  • a rectified alternating current is applied to the coil.
  • the object of the invention is to provide an electronic circuit for controlling a vibrating motor supplied from a DC supply voltage, the supply voltage possibly varying relatively considerably within different ranges.
  • the means for controlling the flow of current through the coil comprise a static switch, connected in series with the coil across a continuous supply voltage and comprising an electrode control connected to the output of a chopper, said chopper producing a binary signal making the static switch conductive during said active period, the control means also comprising means for controlling the duration of the active period to the current passing through the coil.
  • control means comprise a measuring resistor arranged in series with the static switch and the coil, and a comparator receiving on a first input a signal representative of the voltage across the measurement resistance and on a second input a reference signal, and whose output is applied to a servo input of the chopper so as to control a transition the output signal of the chopper from its active period to its rest period when the current passing through the coil reaches a predetermined value.
  • the coil 10 for controlling a vibrating motor (not shown) of a known type is supplied from a DC voltage source V1.
  • the coil 10 is connected in series with a transistor T, preferably of the MOS type, and a measurement resistor R1 between the terminals 12 and 14 of the power source. The coil 10 is therefore supplied only when the transistor T is made conductive by the control circuit.
  • the coil 10 is supplied with a periodic signal, the transistor T being, in the presence of a control signal from the vibrating motor, made alternately conductive and non-conductive and the palette of the vibrating motor being attracted by the coil when the transistor T is conductive and returned by a spring when the transistor is blocked.
  • a switch 16 normally open, connecting the DC voltage source V1 to a circuit 18 supplying the control circuit, is closed in the presence of the vibrating motor control signal.
  • the switch 16 and its control can be achieved by any suitable means.
  • the supply circuit 18 supplies a chopper 20 with a stabilized DC voltage V2.
  • the chopper 20 comprises an astable multivibrator producing a signal A intended to be applied to the gate of the transistor T.
  • the signal A is a binary type signal passing alternately from a high state to a low state and vice versa, with a certain duty cycle .
  • a conventional multivibrator (fig. 2) comprises an operational amplifier 22, supplied by the voltage V2, and whose non-inverting input receives a reference voltage (signal B) taking two distinct states as a function of the output voltage.
  • this reference voltage is obtained by means of a voltage divider constituted by two resistors R2 and R3, in series across the supply voltage V2, the non-inverting input being, moreover, connected to the output A1 of the amplifier 22 by a resistor R4.
  • the inverting input of the operational amplifier is connected to ground by a capacitor C1 and to the output A1 of the amplifier by a resistor R5.
  • a limiting resistor R6 connects the output of amplifier 22 to the gate of transistor T.
  • the durations of the high and low states of such an astable circuit are fixed, proportional respectively to the durations of charge and discharge of the capacitor C1.
  • the stabilized supply voltage V2 being fixed, for example equal to 15 V, the increase in the supply voltage V1 of the vibrating motor within a determined range can lead to harmful overheating. Indeed, the duration of the passage of the current in the coil 10 being fixed, independently of the value of the voltage V1, the current crossing the coil is all the more important as the voltage V1 is important.
  • the duration of the high state of the output signal A of the chopper 20 is controlled by the current passing through the coil 10.
  • the voltage C across the measurement resistor R1 ( fig.1), representative of this current, is applied to a servo input of the chopper 20.
  • voltage C is applied to the non-inverting input of an operational amplifier 24, supplied by voltage V2 and whose inverting input is connected to a voltage of Cref reference.
  • V2 supplied by voltage V2 and whose inverting input is connected to a voltage of Cref reference.
  • the latter is obtained by means of a voltage divider constituted by two resistors R7 and R8 in series between the ground and the voltage V2.
  • the output of the operational amplifier 24 is connected to the anode of a diode D1, the cathode of which is connected to the inverting input of the operational amplifier 22.
  • FIG. 3 illustrates the waveforms obtained at various points of the chopper according to FIG. 2.
  • V2 15 V and the resistors R2, R3 and R4 are identical, so that the signal B applied to the non-inverting input of the amplifier 22 passes from a low reference value (5V ) to a high reference value (10V) when the signal A1 passes respectively from its low state (0V) to its high state (15V).
  • the chopper then operates normally, as in the absence of servo-control: signal E, corresponding to the voltage across the capacitor, which is at its maximum reference value (10V) at the start (t0, t2, t4, t6, t8) of the rest period (T1) of the control signal A1, tends to 0 with a predetermined time constant R5 C1 (discharge of C1).
  • FIG. 3 shows the signals C obtained during the period T2 respectively with a supply voltage V1 close to the nominal voltage (24V) (t1-t2), with a voltage V1 lower than this nominal voltage (t5- t6) and with a voltage V1 greater than this nominal voltage (t3-t4 and t7-t8).
  • the end of the active period T2 is therefore determined by the moment when the current passing through the coil 10 reaches a predetermined peak value Ic, that is to say when the voltage C reaches the reference voltage Cref.
  • This active period T2 nevertheless remains always less than the period T2max obtained when the astable multivibrator operates without slaving.
  • a protection and discharge circuit is arranged in parallel on the transistor T and the resistor R1 so as to limit the overvoltages at the terminals of the transistor and to rapidly discharge the coil 10 when the transistor is blocked. It is indeed essential to protect the transistor against overvoltages created by a rapid variation of the current in the coil and to quickly evacuate the energy stored in the coil so that a spring recalls the palette of the vibrating motor during the rest period (T1).
  • Such a circuit is preferably constituted (fig. 1) by a diode D2 of the Transil type arranged in series with a power resistor R9 between the drain of the transistor T and the ground.
  • the same control circuit can be used for different ranges of supply voltage to the coil (10).
  • four ranges of DC voltage are generally used: 24-30V, 48-60V, 100-125V and 220-250V.
  • Each voltage range is associated with a vibrating motor having a coil whose resistance varies from one range to another.
  • the measurement resistance R1 is determined, taking into account the resistance of the coil, so as to allow correct servoing in all the ranges.
  • the invention is not limited to the particular embodiment shown.
  • the chopper 20 could be supplied permanently, the supply voltage V1 being applied to the coil only in the presence of a signal for controlling the vibrating motor.
  • the functions of cutting by the MOS transistor (T) and of measuring the current by the resistor R1 can be fulfilled by a MOS transistor with internal current measurement.

Abstract

The coil (10) of the pulse motor is supplied by a d.c. voltage (V1) and arranged in series with a transistor (T) across the terminals of the supply voltage (V1). The transistor (T) is controlled by the output signal (A) from a chopper (20) slaved to the current traversing the coil in such a way as to permit correct operation of the control circuit for extended ranges of supply voltage. <IMAGE>

Description

L'invention concerne un circuit électronique de commande d'un moteur vibrant comportant une bobine de commande, des moyens de commande du passage du courant dans la bobine provoquant, lorsqu'un signal de commande du moteur vibrant leur est appliqué, alternativement l'alimentation en courant de la bobine pendant une période active et la non-alimentation de la bobine pendant une période de repos.The invention relates to an electronic circuit for controlling a vibrating motor comprising a control coil, means for controlling the passage of current in the coil causing, when a control signal from the vibrating motor is applied to them, alternately the power supply. current from the coil during an active period and non-supply of the coil during a rest period.

Dans un dispositif d'armement d'un ressort d'un mécanisme de commande d'un appareil de coupure, notamment un interrupteur ou un disjoncteur électrique, tel que décrit, par exemple, dans le brevet français 2.593.323, la bobine de commande du moteur vibrant est alimentée par un courant périodique. Dans ce dispositif, en présence d'un signal de commande, un courant alternatif redressé est appliqué à la bobine.In a device for arming a spring of a control mechanism of a breaking device, in particular an electrical switch or circuit breaker, as described, for example, in French patent 2,593,323, the control coil of the vibrating motor is supplied by a periodic current. In this device, in the presence of a control signal, a rectified alternating current is applied to the coil.

L'invention a pour but un circuit électronique de commande d'un moteur vibrant alimenté à partir d'une tension d'alimentation continue, la tension d'alimentation pouvant varier de façon relativement importante à l'intérieur de différentes plages.The object of the invention is to provide an electronic circuit for controlling a vibrating motor supplied from a DC supply voltage, the supply voltage possibly varying relatively considerably within different ranges.

Selon l'invention, ce but est atteint par le fait que les moyens de commande du passage du courant dans la bobine comportent un interrupteur statique, connecté en série avec la bobine aux bornes d'une tension d'alimentation continue et comportant une électrode de commande connectée à la sortie d'un hâcheur, ledit hâcheur produisant un signal binaire rendant l'interrupteur statique conducteur pendant ladite période active, les moyens de commande comportant également des moyens d'asservissement de la durée de la période active au courant passant dans la bobine.According to the invention, this object is achieved by the fact that the means for controlling the flow of current through the coil comprise a static switch, connected in series with the coil across a continuous supply voltage and comprising an electrode control connected to the output of a chopper, said chopper producing a binary signal making the static switch conductive during said active period, the control means also comprising means for controlling the duration of the active period to the current passing through the coil.

Selon un mode de réalisation préférentiel de l'invention les moyens d'asservissement comportent une résistance de mesure disposée en série avec l'interrupteur statique et la bobine, et un comparateur recevant sur une première entrée un signal représentatif de la tension aux bornes de la résistance de mesure et sur une seconde entrée un signal de référence, et dont la sortie est appliquée à une entrée d'asservissement du hâcheur de manière à commander une transition du signal de sortie du hâcheur de sa période active à sa période de repos lorsque le courant traversant la bobine atteint une valeur prédéterminée.According to a preferred embodiment of the invention, the control means comprise a measuring resistor arranged in series with the static switch and the coil, and a comparator receiving on a first input a signal representative of the voltage across the measurement resistance and on a second input a reference signal, and whose output is applied to a servo input of the chopper so as to control a transition the output signal of the chopper from its active period to its rest period when the current passing through the coil reaches a predetermined value.

D'autres avantages et caratéristiques ressortiront plus clairement de la description qui va suivre d'un mode de mise en oeuvre de l'invention, donné à titre d'exemple non limitatif et représenté aux dessins annexés, sur lesquels :

  • La figure 1 représente un circuit de commande selon l'invention
  • La figure 2 illustre un mode de réalisation particulier du hâcheur asservi du circuit selon la figure 1
  • La figure 3 représente diverses formes d'onde obtenues en différents points du circuit selon les figures 1 et 2.
Other advantages and characteristics will emerge more clearly from the description which follows of an embodiment of the invention, given by way of nonlimiting example and represented in the appended drawings, in which:
  • FIG. 1 represents a control circuit according to the invention
  • FIG. 2 illustrates a particular embodiment of the slave chopper of the circuit according to FIG. 1
  • FIG. 3 represents various waveforms obtained at different points of the circuit according to FIGS. 1 and 2.

La bobine 10 de commande d'un moteur vibrant (non représenté) de type connu (par exemple FR-A- 2.593.323) est alimentée à partir d'une source de tension continue V1. Comme représenté sur la figure 1 la bobine 10 est connectée en série avec un transistor T, de préférence de type MOS, et une résistance de mesure R1 entre les bornes 12 et 14 de la source d'alimentation. La bobine 10 n'est donc alimentée que lorsque le transistor T est rendu conducteur par le circuit de commande.The coil 10 for controlling a vibrating motor (not shown) of a known type (for example FR-A-2,593,323) is supplied from a DC voltage source V1. As shown in FIG. 1, the coil 10 is connected in series with a transistor T, preferably of the MOS type, and a measurement resistor R1 between the terminals 12 and 14 of the power source. The coil 10 is therefore supplied only when the transistor T is made conductive by the control circuit.

Pour permettre le fonctionnement du moteur vibrant la bobine 10 est alimentée par un signal périodique, le transistor T étant, en présence d'un signal de commande du moteur vibrant, rendu alternativement conducteur et non conducteur et la palette du moteur vibrant étant attirée par la bobine lorsque le transistor T est conducteur et rappelée par un ressort lorsque le transistor est bloqué.To allow the vibrating motor to operate, the coil 10 is supplied with a periodic signal, the transistor T being, in the presence of a control signal from the vibrating motor, made alternately conductive and non-conductive and the palette of the vibrating motor being attracted by the coil when the transistor T is conductive and returned by a spring when the transistor is blocked.

Un interrupteur 16, normalement ouvert, connectant la source de tension continue V1 à un circuit 18 d'alimentation du circuit de commande, est fermé en présence du signal de commande du moteur vibrant. L'interrupteur 16 et sa commande peuvent être réalisés par tous moyens appropriés.A switch 16, normally open, connecting the DC voltage source V1 to a circuit 18 supplying the control circuit, is closed in the presence of the vibrating motor control signal. The switch 16 and its control can be achieved by any suitable means.

Le circuit d'alimentation 18 alimente un hâcheur 20 avec une tension continue V2 stabilisée. Le hâcheur 20 comporte un multivibrateur astable produisant un signal A destiné à être appliqué sur la grille du transistor T. Le signal A est un signal de type binaire passant alternativement d'un état haut à un état bas et réciproquement, avec un certain rapport cyclique. Un multivibrateur classique (fig.2) comporte un amplificateur opérationnel 22, alimenté par la tension V2, et dont l'entrée non-inverseuse reçoit une tension de référence (signal B) prenant deux états distincts en fonction de la tension de sortie. Sur la figure 2, cette tension de référence est obtenue au moyen d'un diviseur de tension constitué par deux résistances R2 et R3, en série aux bornes de la tension d'alimentation V2, l'entrée non-inverseuse étant, de plus, connecté à la sortie A1 de l'amplificateur 22 par une résistance R4. L'entrée inverseuse de l'amplificateur opérationnel est connectée à la masse par un condensateur C1 et à la sortie A1 de l'amplificateur par une résistance R5. Une résistance de limitation R6 connecte la sortie de l'amplificateur 22 à la grille due transistor T.The supply circuit 18 supplies a chopper 20 with a stabilized DC voltage V2. The chopper 20 comprises an astable multivibrator producing a signal A intended to be applied to the gate of the transistor T. The signal A is a binary type signal passing alternately from a high state to a low state and vice versa, with a certain duty cycle . A conventional multivibrator (fig. 2) comprises an operational amplifier 22, supplied by the voltage V2, and whose non-inverting input receives a reference voltage (signal B) taking two distinct states as a function of the output voltage. In FIG. 2, this reference voltage is obtained by means of a voltage divider constituted by two resistors R2 and R3, in series across the supply voltage V2, the non-inverting input being, moreover, connected to the output A1 of the amplifier 22 by a resistor R4. The inverting input of the operational amplifier is connected to ground by a capacitor C1 and to the output A1 of the amplifier by a resistor R5. A limiting resistor R6 connects the output of amplifier 22 to the gate of transistor T.

Les durées des états haut et bas d'un tel circuit astable sont fixes, proportionnelles respectivement aux durées de charge et de décharge du condensateur C1.The durations of the high and low states of such an astable circuit are fixed, proportional respectively to the durations of charge and discharge of the capacitor C1.

La tension d'alimentation stabilisée V2 étant fixe, par exemple égale à 15 V, l'augmentation de la tension d'alimentation V1 du moteur vibrant à l'intérieur d'une plage déterminée peut conduire à des échauffements préjudiciables. En effet, la durée du passage du courant dans la bobine 10 étant fixe, indépendamment de la valeur de la tension V1, le courant traversant la bobine est d'autant plus important que la tension V1 est importante.The stabilized supply voltage V2 being fixed, for example equal to 15 V, the increase in the supply voltage V1 of the vibrating motor within a determined range can lead to harmful overheating. Indeed, the duration of the passage of the current in the coil 10 being fixed, independently of the value of the voltage V1, the current crossing the coil is all the more important as the voltage V1 is important.

Pour permettre un fonctionnement correct, malgré une plage de tension V1 étendue, la durée de l'état haut du signal A de sortie du hâcheur 20 est asservie au courant traversant la bobine 10. La tension C aux bornes de la résistance R1 de mesure (fig.1), représentative de ce courant, est appliquée sur une entrée d'asservissement du hâcheur 20.To allow correct operation, despite a wide voltage range V1, the duration of the high state of the output signal A of the chopper 20 is controlled by the current passing through the coil 10. The voltage C across the measurement resistor R1 ( fig.1), representative of this current, is applied to a servo input of the chopper 20.

Dans le mode de réalisation particulier du hâcheur représenté à la figure 2, la tension C est appliquée sur l'entrée non-­inverseuse d'un amplificateur opérationnel 24, alimenté par la tension V2 et dont l'entrée inverseuse est connectée à une tension de référence Cref. Sur la figure 2, cette dernière est obtenue au moyen d'un diviseur de tension constitué par deux résistances R7 et R8 en série entre la masse et la tension V2. La sortie de l'amplificateur opérationnel 24 est connectée à l'anode d'une diode D1, dont la cathode est reliée à l'entrée inverseuse de l'amplificateur opérationnel 22.In the particular embodiment of the chopper shown in FIG. 2, voltage C is applied to the non-inverting input of an operational amplifier 24, supplied by voltage V2 and whose inverting input is connected to a voltage of Cref reference. In FIG. 2, the latter is obtained by means of a voltage divider constituted by two resistors R7 and R8 in series between the ground and the voltage V2. The output of the operational amplifier 24 is connected to the anode of a diode D1, the cathode of which is connected to the inverting input of the operational amplifier 22.

La figure 3 illustre les formes d'onde obtenues en divers points du hâcheur selon la figure 2.FIG. 3 illustrates the waveforms obtained at various points of the chopper according to FIG. 2.

A titre d'exemple, V2 = 15 V et les résistances R2, R3 et R4 sont identiques, de sorte que le signal B appliqué à l'entrée non-­inverseuse de l'amplificateur 22 passe d'une valeur de référence basse (5V) à une valeur de référence haute (10V) lorsque le signal A1 passe respectivement de son état bas (0V) à son état haut (15V).For example, V2 = 15 V and the resistors R2, R3 and R4 are identical, so that the signal B applied to the non-inverting input of the amplifier 22 passes from a low reference value (5V ) to a high reference value (10V) when the signal A1 passes respectively from its low state (0V) to its high state (15V).

Lorsque A1 est à l'état bas (t0-t1, t2-t3, t4-t5, t6-t7), le transistor T est bloqué et aucun courant ne circule dans la bobine 10 et dans la résistance de mesure R1. Le signal C, représentatif du courant, est nul et, en conséquence, inférieur à la référence Cref. Le signal D de sortie de l'amplificateur opérationnel 24 est à l'état bas (0V) et la diode D1 est non conductrice. Le hâcheur fonctionne alors normalement, comme en l'absence d'asservissement : le signal E, correspondant à la tension aux bornes du condensateur, qui est à sa valeur de référence maximale (10V) en début (t0, t2, t4, t6, t8) de la période de repos (T1) du signal A1 de commande, tend vers 0 avec une constante de temps prédéterminée R5 C1 (décharge de C1).When A1 is in the low state (t0-t1, t2-t3, t4-t5, t6-t7), the transistor T is blocked and no current flows in the coil 10 and in the measurement resistance R1. The signal C, representative of the current, is zero and, consequently, less than the Cref reference. The output signal D of the operational amplifier 24 is in the low state (0V) and the diode D1 is not conductive. The chopper then operates normally, as in the absence of servo-control: signal E, corresponding to the voltage across the capacitor, which is at its maximum reference value (10V) at the start (t0, t2, t4, t6, t8) of the rest period (T1) of the control signal A1, tends to 0 with a predetermined time constant R5 C1 (discharge of C1).

Lorsque le signal E atteint 5V, valeur de référence basse du signal B, aux instants t1, t3, t5 et t7, la sortie A1 de l'amplificateur opérationnel 22 bascule et prend sa valeur haute (15V). Le signal B passe alors à sa valeur de référence haute (10V), l'hystérèsis des valeurs de référence ne permettant pas un nouveau basculement du signal A1 tant que le signal E n'a pas atteint sa valeur de référence maximale (10V). Le condensateur C1 se charge à travers la résistance R5, la tension E à ses bornes tendant vers 15V (valeur de A1) avec une constante de temps fixe R5 C1. Pendant la période active (T2) du signal A1, où celui-ci est à l'état haut, le transistor T est conducteur et un courant traverse la bobine 10 et la résistance de mesure R1. Ce courant et le signal C, qui le représente, augmentent pendant la période T2, d'autant plus rapidement que la tension d'alimentation V1 est plus élevée. Pour une plage de tension prédéterminée, à titre d'exemple 24-30V, la tension V1 peut varier très largement, par exemple de 19 à 34,5V. On a représenté sur la figure 3, les signaux C obtenus pendant la période T2 respectivement avec une tension d'alimentation V1 proche de la tension nominale (24V) (t1-t2), avec une tension V1 inférieure à cette tension nominale (t5-t6) et avec une tension V1 supérieure à cette tension nominale (t3-t4 et t7-t8). Plus la tension d'alimentation V1 est élevée plus le temps nécessaire au signal C pour atteindre la valeur de référence Cref est faible.When signal E reaches 5V, the low reference value of signal B, at times t1, t3, t5 and t7, the output A1 of the operational amplifier 22 switches and takes its high value (15V). The signal B then goes to its high reference value (10V), the hysteresis of the reference values not allowing a new switching of the signal A1 until the signal E has not reached its maximum reference value (10V). The capacitor C1 charges through the resistor R5, the voltage E across its terminals tending towards 15V (value of A1) with a fixed time constant R5 C1. During the active period (T2) of the signal A1, where it is in the high state, the transistor T is conductive and a current flows through the coil 10 and the measurement resistance R1. This current and the signal C, which represents it, increase during the period T2, all the more quickly the higher the supply voltage V1. For a predetermined voltage range, for example 24-30V, the voltage V1 can vary very widely, for example from 19 to 34.5V. FIG. 3 shows the signals C obtained during the period T2 respectively with a supply voltage V1 close to the nominal voltage (24V) (t1-t2), with a voltage V1 lower than this nominal voltage (t5- t6) and with a voltage V1 greater than this nominal voltage (t3-t4 and t7-t8). The higher the supply voltage V1, the shorter the time necessary for the signal C to reach the reference value Cref.

Lorsque la tension d'alimentation V1 est suffisamment basse (t5-­t6) pour que la tension E atteigne sa valeur de référence maximale (10V) avant que le signal C atteigne la valeur de référence Cref à laquelle il est comparé, le signal D reste à sa valeur basse et la diode D1 reste bloquée. Il n'y a alors pas asservissement du hâcheur 22 et la période T2 est égale à une valeur T2max fixe.When the supply voltage V1 is low enough (t5-t6) for the voltage E to reach its maximum reference value (10V) before the signal C reaches the reference value Cref to which it is compared, the signal D remains at its low value and the diode D1 remains blocked. There is then no slaving of the chopper 22 and the period T2 is equal to a fixed value T2max.

Par contre, lorsque la tension d'alimentation V1 est suffisamment élevée (t1-t2, t3-t4, t7-t8) un courant crête Ic prédéterminé, correspondant à la tension de référence Cref, traverse la bobine 10 avant la fin de la période active normale T2max du circuit astable. La tension C atteignant la tension de référence Cref, le signal D de sortie de l'amplificateur opérationnel 24 passe à sa valeur haute (environ 15V), rendant conductrice la diode D1 et chargeant très rapidement le condensateur C1 à une valeur (tension D moins la chute de tension dans la diode D1, soit environ 13V) supérieure à la valeur de référence maximale (10V) du signal E, entraînant le basculement à zéro du signal A1.On the other hand, when the supply voltage V1 is sufficiently high (t1-t2, t3-t4, t7-t8) a predetermined peak current Ic, corresponding to the reference voltage Cref, crosses the coil 10 before the end of the period active normal T2max of the astable circuit. The voltage C reaching the reference voltage Cref, the output signal D of the operational amplifier 24 goes to its high value (around 15V), making the diode D1 conductive and charging the capacitor C1 very quickly to a value (voltage D less the voltage drop in the diode D1, ie about 13V) greater than the maximum reference value (10V) of the signal E, causing the signal A1 to switch to zero.

La fin de la période active T2 est donc déterminée par le moment où le courant traversant la bobine 10 atteint une valeur crête prédéterminée Ic, c'est-à-dire où la tension C atteint la tension de référence Cref. Cette période active T2 reste néanmoins toujours inférieure à la période T2max obtenue lorsque le multivibrateur astable fonctionne sans asservissement.The end of the active period T2 is therefore determined by the moment when the current passing through the coil 10 reaches a predetermined peak value Ic, that is to say when the voltage C reaches the reference voltage Cref. This active period T2 nevertheless remains always less than the period T2max obtained when the astable multivibrator operates without slaving.

Dès que le signal A1 passe à 0, le transistor T se bloque et le courant traversant la résistance R1 s'annule ramenant à zéro le signal C et , en conséquence, le signal D et bloquant de nouveau la diode D1.As soon as the signal A1 goes to 0, the transistor T is blocked and the current passing through the resistor R1 is canceled, bringing the signal C and, consequently, the signal D and blocking the diode D1 again.

Un circuit de protection et de décharge est disposé en parallèle sur le transistor T et la résistance R1 de manière à limiter les surtensions aux bornes du transistor et à décharger rapidement la bobine 10 lors du bloquage du transistor. Il est en effet indispensable de protéger le transistor contre les surtensions crées par une variation rapide du courant dans la bobine et d'évacuer rapidement l'énergie emmaganisée dans la bobine pour qu'un ressort rappelle la palette du moteur vibrant pendant la période de repos (T1).A protection and discharge circuit is arranged in parallel on the transistor T and the resistor R1 so as to limit the overvoltages at the terminals of the transistor and to rapidly discharge the coil 10 when the transistor is blocked. It is indeed essential to protect the transistor against overvoltages created by a rapid variation of the current in the coil and to quickly evacuate the energy stored in the coil so that a spring recalls the palette of the vibrating motor during the rest period (T1).

Un tel circuit est de préférence constituée (fig.1) par une diode D2 de type Transil disposée en série avec une résistance R9 de puissance entre le drain du transistor T et la masse.Such a circuit is preferably constituted (fig. 1) by a diode D2 of the Transil type arranged in series with a power resistor R9 between the drain of the transistor T and the ground.

Ces composants sont choisis de manière à ce que la tension maximale développée aux bornes du circuit de protection et de décharge soit inférieure à la tension maximale supportable par le transistor et à ce que l'échauffement maximum dû aux commutations du courant soit inférieur à la tenue thermique des composants.These components are chosen so that the maximum voltage developed at the terminals of the protection and discharge circuit is less than the maximum voltage which can be supported by the transistor and so that the maximum heating due to switching of the current is less than the withstand. components.

Le même circuit de commande est utilisable pour différentes plages de tension d'alimentation de la bobine (10). A titre d'exemple quatre plages de tension continue sont généralement utilisées : 24-30V, 48-60V, 100-125V et 220-250V. A chaque plage de tension est associé un moteur vibrant ayant une bobine dont la résistance varie d'une plage à l'autre. La résistance de mesure R1 est déterminée, tenant compte de la résistance de la bobine, de manière à permettre un asservissement correct dans toutes les plages.The same control circuit can be used for different ranges of supply voltage to the coil (10). As an example, four ranges of DC voltage are generally used: 24-30V, 48-60V, 100-125V and 220-250V. Each voltage range is associated with a vibrating motor having a coil whose resistance varies from one range to another. The measurement resistance R1 is determined, taking into account the resistance of the coil, so as to allow correct servoing in all the ranges.

L'invention n'est pas limitée en mode particulier de réalisation représenté. En particulier, le hâcheur 20 pourrait être alimenté en permanence, la tension d'alimentation V1 n'étant appliquée à la bobine qu'en présence d'un signal de commande du moteur vibrant. Par ailleur, les fonctions de découpage par le transistor MOS (T) et de mesure du courant par la résistance R1 peuvent être remplies par un transistor MOS à mesure de courant interne.The invention is not limited to the particular embodiment shown. In particular, the chopper 20 could be supplied permanently, the supply voltage V1 being applied to the coil only in the presence of a signal for controlling the vibrating motor. Furthermore, the functions of cutting by the MOS transistor (T) and of measuring the current by the resistor R1 can be fulfilled by a MOS transistor with internal current measurement.

Claims (7)

1 - Circuit électronique de commande d'un moteur vibrant comportant une bobine de commande (10), des moyens (16,18,20,T) de commande du passage du courant dans la bobine provoquant, lorsqu'un signal de commande du moteur vibrant leur est appliqué, alternativement l'alimentation en courant de la bobine pendant une période active (T2) et la non-alimentation de la bobine pendant une période de repos (T1), circuit caractérisé en ce que les moyens de commande du passage du courant dans la bobine comportent un interrupteur statique (T), connecté en série avec la bobine (10) aux bornes d'une tension d'alimentation continue (V1) et comportant une électrode de commande connectée à la sortie d'un hâcheur (20), ledit hâcheur produisant un signal binaire (A) rendant l'interrupteur statique (T) conducteur pendant ladite période active (T2), les moyens de commande comportant également des moyens (R1, 24, D1) d'asservissement de la durée de la période active au courant passant dans la bobine.1 - Electronic circuit for controlling a vibrating motor comprising a control coil (10), means (16,18,20, T) for controlling the flow of current in the coil causing, when a motor control signal vibrating is applied to them, alternately the current supply to the coil during an active period (T2) and the non-supply of the coil during a rest period (T1), circuit characterized in that the means for controlling the passage of the current in the coil include a static switch (T), connected in series with the coil (10) across a DC supply voltage (V1) and having a control electrode connected to the output of a chopper (20 ), said chopper producing a binary signal (A) making the static switch (T) conductive during said active period (T2), the control means also comprising means (R1, 24, D1) for controlling the duration of the current active period passing in the reel. 2- Circuit selon la revendication 1, caractérisé en ce que les moyens d'asservissement comportent une résistance de mesure (R1) disposée en série avec l'interrupteur statique (T) et la bobine (10), et un comparateur (24) recevant sur une première entrée un signal (C) représentatif de la tension aux bornes de la résistance de mesure (R1) et sur une seconde entrée un signal de référence (Cref), et dont la sortie est appliquée à une entrée d'asservissement du hâcheur de manière à commander une transition du signal (A) de sortie du hâcheur de sa période active (T2) à sa période de repos (T1) lorsque le courant traversant la bobine atteint une valeur prédéterminée.2- Circuit according to claim 1, characterized in that the control means comprise a measurement resistor (R1) arranged in series with the static switch (T) and the coil (10), and a comparator (24) receiving on a first input a signal (C) representative of the voltage across the measurement resistance (R1) and on a second input a reference signal (Cref), the output of which is applied to a chopper control input so as to control a transition of the output signal (A) of the chopper from its active period (T2) to its rest period (T1) when the current passing through the coil reaches a predetermined value. 3 - Circuit selon la revendication 2, caractérisé en ce que le hâcheur (20) est un multivibrateur astable comportant une première entrée (+) sur laquelle est appliqué un signal (B) de référence asservi à la sortie (A1) et une seconde entrée (E), formant ladite entrée d'asservissement, connectée par un condensateur (C1) à la masse et par une résistance (R5) à la sortie du multivibrateur, les moyens d'asservissement comportant une diode (D1) connectée entre la sortie du comparateur et l'entrée d'asservissement du hâcheur.3 - Circuit according to claim 2, characterized in that the chopper (20) is an astable multivibrator comprising a first input (+) to which is applied a reference signal (B) controlled by the output (A1) and a second input (E), forming said servo input, connected by a capacitor (C1) to ground and by a resistor (R5) at the output of the multivibrator, the servo means comprising a diode (D1) connected between the output of the comparator and the servo input of the chopper. 4 - Circuit selon l'une quelconque des revendications 1 à 3, caractérisé en ce qu'il comporte un circuit d'alimentation stabilisé (18) disposé en série aux bornes de la tension d'alimentation continue (V1) avec un interrupteur (16) contrôlé par le signal de commande du moteur vibrant.4 - Circuit according to any one of claims 1 to 3, characterized in that it comprises a stabilized supply circuit (18) arranged in series across the terminals of the DC supply voltage (V1) with a switch (16 ) controlled by the vibrating motor control signal. 5 - Circuit selon l'une des revendications 1 à 4, caractérisé en que l'interrupteur statique (T) est un transistor de type MOS.5 - Circuit according to one of claims 1 to 4, characterized in that the static switch (T) is a MOS type transistor. 6 - Circuit selon la revendication 5, caractérisé en ce qu'il comporte un circuit de protection disposé en parallèle sur le transistor (T).6 - Circuit according to claim 5, characterized in that it comprises a protection circuit arranged in parallel on the transistor (T). 7 - Circuit selon la revendication 6, caractérisé en ce que le circuit de protection comporte, en série, une diode de type Transil (D2) et une résistance de décharge de puissance (R9)7 - Circuit according to claim 6, characterized in that the protection circuit comprises, in series, a Transil type diode (D2) and a power discharge resistor (R9)
EP19900420426 1989-10-17 1990-10-03 Electronic control circuit for a direct current energised pulse motor Expired - Lifetime EP0424280B1 (en)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
FR89136665 1989-10-17
FR8913665A FR2653275B1 (en) 1989-10-17 1989-10-17 ELECTRONIC CONTROL CIRCUIT FOR A VIBRATING MOTOR POWERED BY DIRECT CURRENT.

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EP0424280A1 true EP0424280A1 (en) 1991-04-24
EP0424280B1 EP0424280B1 (en) 1994-08-03

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DE (1) DE69011269D1 (en)
FR (1) FR2653275B1 (en)

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EP0720193A1 (en) * 1994-12-28 1996-07-03 Schneider Electric Sa Electric control for opening and closing a switch or a circuit breaker
WO2000058983A1 (en) * 1999-03-29 2000-10-05 Siemens Energy & Automation, Inc. An electrical control module for a circuit breaker stored energy operator
EP2551881A1 (en) * 2011-07-25 2013-01-30 ABB Technology AG Actuator for a circuit breaker
EP2763155A1 (en) * 2013-02-01 2014-08-06 General Electric Company Electrical operator for circuit breaker and method thereof

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CN104505214B (en) * 2014-12-19 2016-08-24 安阳凯地电磁技术有限公司 A kind of high thrust low-temperature-rise no-noise AC electric magnet

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EP0720193A1 (en) * 1994-12-28 1996-07-03 Schneider Electric Sa Electric control for opening and closing a switch or a circuit breaker
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WO2000058983A1 (en) * 1999-03-29 2000-10-05 Siemens Energy & Automation, Inc. An electrical control module for a circuit breaker stored energy operator
EP2551881A1 (en) * 2011-07-25 2013-01-30 ABB Technology AG Actuator for a circuit breaker
WO2013013984A1 (en) * 2011-07-25 2013-01-31 Abb Technology Ag Method for driving an actuator of a circuit breaker, and actuator for a circuit breaker
CN103703535A (en) * 2011-07-25 2014-04-02 Abb技术有限公司 Method for driving an actuator of a circuit breaker, and actuator for a circuit breaker
CN103703535B (en) * 2011-07-25 2016-05-04 Abb技术有限公司 Be used for the method for the actuator that drives breaker and the actuator for breaker
EP2763155A1 (en) * 2013-02-01 2014-08-06 General Electric Company Electrical operator for circuit breaker and method thereof
US9184014B2 (en) 2013-02-01 2015-11-10 General Electric Company Electrical operator for circuit breaker and method thereof

Also Published As

Publication number Publication date
FR2653275B1 (en) 1991-12-13
EP0424280B1 (en) 1994-08-03
DE69011269D1 (en) 1994-09-08
FR2653275A1 (en) 1991-04-19

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