EP0326489A1 - Regulierungssystem des Arbeitspunktes einer Gleichstromversorgung - Google Patents

Regulierungssystem des Arbeitspunktes einer Gleichstromversorgung Download PDF

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Publication number
EP0326489A1
EP0326489A1 EP89400219A EP89400219A EP0326489A1 EP 0326489 A1 EP0326489 A1 EP 0326489A1 EP 89400219 A EP89400219 A EP 89400219A EP 89400219 A EP89400219 A EP 89400219A EP 0326489 A1 EP0326489 A1 EP 0326489A1
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EP
European Patent Office
Prior art keywords
voltage
converter
input
output
delivered
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Granted
Application number
EP89400219A
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English (en)
French (fr)
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EP0326489B1 (de
Inventor
Christian Rouzies
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Centre National dEtudes Spatiales CNES
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Centre National dEtudes Spatiales CNES
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Priority claimed from FR8801057A external-priority patent/FR2626689B1/fr
Application filed by Centre National dEtudes Spatiales CNES filed Critical Centre National dEtudes Spatiales CNES
Priority to AT89400219T priority Critical patent/ATE86399T1/de
Publication of EP0326489A1 publication Critical patent/EP0326489A1/de
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    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
    • G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
    • G05F1/66—Regulating electric power
    • G05F1/67—Regulating electric power to the maximum power available from a generator, e.g. from solar cell
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S323/00—Electricity: power supply or regulation systems
    • Y10S323/906—Solar cell systems

Definitions

  • the present invention relates to a system for regulating the operating point of a DC power supply comprising a current generator system coupled to a pulse width modulation converter.
  • the supply is most often made from generators of the current generator type, such as solar generators.
  • These generators designated by the name of current generators have a substantially rectangular current-voltage output characteristic I (V), both a source of current in its zone (I) and a source of voltage in its zone (II), thus as shown in Figure 1a.
  • the power-voltage output characteristic P (V) has a substantially triangular shape, as shown in FIG. 1b.
  • width modulation electrical energy converter which is controlled so as to deliver pulses of rectangular voltage of variable width as a function of the power consumed by a load circuit.
  • PWM pulse width modulation electrical energy converter
  • the current-voltage input characteristics I (V) of such a converter supplying a load consuming a constant power has the appearance of the positive part of an equilateral hyperbola as shown in FIG. 1c, these converters being essentially reactive, and having a very good yield, consuming only very little power.
  • the electronic control loop of these converters comprises an error amplifier comparing the voltage to be regulated, the voltage supplied to the load, to a reference voltage, the amplified error signal being supplied to a comparator ensuring the modulation of width of the voltage pulses delivered by the converter by comparing the error signal to a signal generated by a sawtooth generator.
  • An integrator is introduced at the output of the comparator in order to obtain a zero static error.
  • a given converter according to the direction of variation of the error signal as a function of the variation of the voltage to be regulated, therefore has its operating point either on zone I current source, or on zone II voltage source of the current-voltage output characteristic of the generator for a constant power consumption P, as shown in FIGS. 1d and 1e.
  • the operating point When the power demand becomes greater than the maximum power Pmax, the operating point previously, located on the current generator zone or on the contrary on the voltage generator zone, passes over the voltage generator or current generator zone, as well as represented in figure 1f and 1g, beyond or below the point of coordinates I (Pmax), V (Pmax). Under these conditions, the operating point becomes unstable because there is a change in operating regime, that is to say passage from one to the other current source area respectively voltage.
  • the purpose of the system for regulating the operating point of a DC power supply according to the invention is to remedy the aforementioned drawback by eliminating the stall phenomenon.
  • Another object of the present invention is the implementation of a regulation system of a DC power supply, in which the amplitude of the excursion of the operating point around the point of maximum power Pmax is adjustable.
  • Another object of the present invention is also the implementation of a system for regulating a DC power supply, in which the operating point at demanded power lower than the maximum power Pmax can be adjusted either over the area of the current source characteristic, ie in the area of the voltage source characteristic.
  • Another object of the present invention is finally the implementation of a system for regulating a DC power supply, in which the solar generator can be coupled to the converter without particular precautions, one of the operating points corresponding to the power actually called being automatically reached.
  • the system for regulating the operating point of a DC power supply comprises a current generator system coupled to a pulse width modulation converter.
  • the regulation system which is the subject of the invention finds application in systems for supplying electrical energy to artificial satellites, for space aircraft and, more generally, to any system for supplying electrical energy using generators of intensity such as solar batteries, both in space and domestic.
  • the DC power supply is deemed to include a current generator system 1, which is coupled to a pulse width modulation converter 2.
  • the current generator system 1 can be constituted by a solar cell system and the designation current generator system must be understood as a system whose current-voltage output characteristic is substantially rectangular, as shown in FIG. 1a.
  • the pulse width modulation converter 2 is coupled to the current generator system. It makes it possible to generate rectangular voltage pulses, the width of which varies as a function of the power called up by the payload CU; of course, the pulse width modulation converter includes smoothing circuits, not shown in FIG. 2a, which make it possible to deliver the DC voltage Vc to the payload CU.
  • the regulation system which is the subject of the invention, it comprises, as shown in FIG. 2a, means denoted 11, 12 for sampling and measuring the voltage V and the current I delivered by the current generator 1 to converter 2.
  • the means for sampling and measuring the voltage V and the current I can advantageously be constituted by a potentiometric system as regards the measurement of the voltage V, and a shunt or similar device, in as regards the sampling and measurement of the current I.
  • the sampling and measuring means 11 and 12 deliver a signal I, respectively V, representative of the intensity I and of the output voltage V of the current generator, which are applied to the input of the converter with width modulation d pulses 2.
  • the regulation system which is the subject of the invention comprises means 3 detectors with a threshold for the converter stalling 2.
  • the stall state of the converter 2 has been defined beforehand on the basis of the corresponding voltages of voltage V and of current. I delivered by the current generator 1 to the converter 2 in conjunction with FIGS. 1f and 1g.
  • the means 3 detectors at the dropout point of the converter 2 receive the signals representative of the intensity 1 and of the voltage V delivered by the intensity generator 1, to the converter 2 and delivers a logic signal C, representative of the state of the converter 2 stalling or not stalling with respect to the threshold values.
  • the threshold values correspond either to an initially low voltage V value, or to an initially low intensity value, the comparison of the actual voltage V and intensity I value with these threshold values allowing when the values of voltage V or of current I are respectively lower than the corresponding threshold values, to highlight the off-hook or non-off-hook state of the converter 2, as a function of the power called up by the payload CU.
  • the regulation system which is the subject of the invention comprises a regulation loop 4 for the width of pulses delivered by the converter 2.
  • the regulation loop 4 comprises, as shown in FIG. 2a , means 20 for sampling and measuring the voltage Vc delivered by the converter 2 to the payload CU.
  • These means can be constituted by a potentiometric assembly similar to that already mentioned for the production of the means for sampling and measuring the voltage V delivered by the current generator 1.
  • the regulation loop 4 also comprises differential amplifier means 40 receiving on a first input the signal delivered by the means 20 for measuring the voltage delivered by the converter 2 and on a second input a reference voltage denoted Ur.
  • This reference voltage is delivered by a DC voltage generator 41 suitably stabilized. This type of generator will not be described, since it calls upon normal knowledge of a person skilled in the art.
  • the differential amplifier means 40 deliver an amplified error signal denoted ⁇ .
  • reversing means 42 are provided, these reversing means 42 comprising an input terminal 420, connected to the output of the differential amplifier 40 and receiving the amplified error signal.
  • the reversing means 42 further comprise an inversion control terminal represented diagrammatically by a switch blade denoted 421, the inversion control terminal 421 receiving the logic signal C delivered by the means 3 threshold detectors.
  • the reversing means further comprise a direct transmission terminal 424 of the amplified error signal and a reverse transmission terminal of the amplified signal terminal denoted 425, which is connected to an inverter denoted 423. Reversing means 42 thus deliver, on switching by via the control signal C, the amplified error signal not inverted, via terminal 424 or the amplified error signal inverted via terminal 425 and the inverter 423.
  • Integrating means 43 are further provided, the latter receiving the inverted or non-inverted error signal, ⁇ ⁇ and delivering an integrated error signal denoted S.
  • means 44 for pulse width modulation comprising a comparator 440 and a sawtooth generator 441.
  • the comparator comprises a first input terminal receiving integrator 43 the integrated error signal S and a second input terminal receiving the signal delivered by the sawtooth generator 441.
  • the output terminal of comparator 44 delivers a control signal denoted SCL, of pulse width of the pulse width modulation converter 2.
  • the pulse width is controlled by the duration of the high state of the SCL signal, which is itself controlled by the time during which the sawtooth voltage delivered by the sawtooth generator 441 is less than the value of the amplified error signal inverted or not ⁇ ⁇ .
  • the operating point oscillates between the two extreme positions defined on the current-voltage output characteristic I (V) of the generator intensity, extreme position defined by the threshold values Imin and Vmin, position denoted A and B in FIG. 2b at points 1 and 2 thereof.
  • the means 3 detectors with threshold converter 2 dropout are variable threshold dropout detection means.
  • the aforementioned variable thresholds make it possible to change these thresholds Imin and Vmin framing the point of maximum power Pmax towards the coordinates of this point.
  • coefficients kI and kV are coefficients strictly less than 1.
  • V (Imin) represents the value of the voltage V on the current-voltage output characteristic I (V) of the generator current 1. This point corresponds substantially to point B in Figure 2b at points 1 and 2 thereof.
  • the successive threshold values correspond to the torque values: kI and kV being defined as above.
  • the converter extracts a power P Pmax but the power supplied P tends towards Pmax.
  • the power called P is greater than the maximum power Pmax, the voltage delivered by the converter cannot remain close to the set value, except in the case where an auxiliary source provides the necessary additional power.
  • the corresponding voltage V (I 2r ) x kV with kV 1 is used for the next voltage threshold.
  • the means 3 detectors with a drop-out threshold of the converter 2, the thresholds being variable, comprise directly connected respectively to the means for sampling and measuring the voltage V and the current I, denoted 11, 12, a first and second comparator circuit 31, 32 constituted by a differential amplifier.
  • the negative terminal of comparator 31 is directly connected to the output of the voltage sampling and measurement means V, and the positive terminal of this same comparator is connected at the output of the means 12 for sampling and measuring the voltage V via a first attenuator circuit 310, connected in cascade with a first sampler-blocker circuit 311.
  • the first attenuator circuit 310 has a coefficient d attenuation kV, less than 1.
  • the means 3 threshold detectors also comprise a second comparator circuit 32, constituted by a differential amplifier, the negative terminal of which is directly connected to the output of the means 11 for sampling and measuring the intensity I and the positive terminal of which is connected to the output means for sampling and measuring the intensity I, via a second attenuator circuit 320, connected in cascade with a second circuit 321 sampler-blocker.
  • the second attenuator circuit 320 has an attenuation coefficient kI, less than 1.
  • variable threshold detection means 3 comprise a flip-flop 33 of RS type, the input R of which is directly connected to the output of the second comparator 32 and the input of which S is directly connected to the output of the first comparator 31.
  • the output Q of the flip-flop 33 of RS type delivers the logic signal C representative of the off-hook or non-off-hook state of the converter 2, with respect to the aforementioned variable threshold values .
  • the exit Q of the RS type flip-flop is connected directly to the sampling-blocking control input of the first blocker-sampler 311 and the output Q to the sampling-blocking control input of the second blocker-sampler 321.
  • the samplers-blockers 321 and 311 allow each to store alternately a fraction kI of the current I delivered by the current generator 1, when the last voltage threshold V r is crossed and a fraction kV of the voltage V delivered by the current generator 1 to converter 2, when the last current threshold I r is crossed.
  • the crossing of the thresholds thus memorized therefore corresponding to variable values in accordance with the previously described variation law is detected by the comparators 31 and 32 which then control the flip-flop RS 33, the latter delivering the logic signal C for command to switch the sign of the error signal amplified.
  • variable threshold detection means 3 comprise connected at the output of the blocking samplers 311 and 321, ensuring the connection with the positive input of the first and second comparators 31, 32, a conditional switching circuit 312, 322, receiving on a first input the signal delivered by the corresponding blocking sampler 311 or 321 and on a second input a reference voltage V r1 , V r2 representative of the limit threshold value Vmin respectively Imin.
  • Each of the conditional routing circuits 312, 322 ensures the transmission of the largest of the values constituted by the value of the signal delivered by the corresponding blocking sampler or by the reference voltage V r1 or V r2 .
  • the last sampled threshold values vary accordingly and the threshold threshold values of voltage V and current I delivered by the intensity generator 1, converge towards the corresponding values of current and voltage of the point of maximum power Pmax, values denoted I (Pmax) and V (pmax) as shown in FIG. 2c.
  • the converter 2 When the power called P by the payload CU becomes less than the maximum power Pmax, capable of being supplied by the intensity generator 1, the converter 2 is then positioned with equi-probability, on one of the two points of possible operation, noted Ai and Bi in Figure 3b.
  • this comprises a Zener diode 3120 delivering the reference voltage V r1 , representative of the voltage value Vmin or Imin .
  • the Zener diode 3120 is connected on the one hand to a resistor 3121 supplied by a supply voltage source + E and on the other hand, to a first diode 3122 polarized in the passing direction with respect to the power source + E.
  • Diode 3122 is connected to the positive input terminal of comparator 31 charged by a resistor 312 connected in parallel to the positive terminal of comparator 31.
  • a second diode 3124 provides the link between the output of the blocking sampler 311, the terminal positive input of comparator 31.
  • the two diodes 3122, 3124 and the resistor 3123 play the role of an analog OR gate allowing the transmission of the signal with the highest amplitude value.
  • the point Bi will be chosen if one wishes to limit the current absorbed by the converter 2 to a current IL such as IAi> IL> IBi.
  • the point Ai will be chosen if we want to limit the input voltage of converter 2, to a voltage VL such that VBi> VL> VAi.
  • the operating point can be located in the "current source” area on the generator if you want to limit the input voltage of the converter to a Vlim value or in the "voltage source” area on the generator if on the contrary one wishes to limit the input current of the converter to a value Ilim.
  • variable threshold detection means 3 further comprises a comparator 323 whose positive terminal is connected to the sampling and intensity measurement means I1 and the negative terminal of which is connected to a reference voltage V r3 representative of the limit intensity Ilim.
  • the comparator 323 by detection of the overshoot, delivers, by its output connected to the input S of the flip-flop RS33 through an OR gate 314 receiving on a second input the signal delivered by the output of the comparator 31 control which allows to introduce a corresponding inversion in the regulation loop 4, making the initial operating point unstable.
  • a switch 325 controlled by the output of the comparator 323 allows the setting in short circuit of the blocking sampler 321, which makes it possible to enter a zero value on the blocking sampler 321, the intensity threshold can then only be reset to the value Imin, if it does not was already.
  • the detection means 3 to variable threshold include another comparator 313, the positive terminal of which is connected to the voltage sampling and measurement means and the negative terminal of which is connected to a reference voltage V r4 representative of the limit voltage Vlim.
  • the comparator 313, on detection of the overshoot, delivers by its output connected to the input R of the flip-flop RS33 via an OR gate 324 receiving on a second input the signal delivered by the output of the comparator 32, a signal control allowing to introduce a corresponding inversion in the regulation loop 4.
  • a switch 326 controlled by the output of comparator 313 allows the simultaneous short-circuiting of the sampler-blocker 312, which makes it possible to enter a zero value on the sampler-blocker 312, the voltage threshold does not can then be reset only to the value Vmin, if it was not already.
  • the differential amplifier means 40 and the reversing means 42 can advantageously be constituted by a first error amplifier 401, the positive input of which is connected to the reference voltage Ur delivered by the voltage source of reference 41 not shown in FIG. 3a.
  • the negative input of the first error amplifier 401 is connected to the means 20 for sampling and measuring the voltage Vc delivered by the converter 2.
  • the output of the first error amplifier 401 delivers a first error signal noted ⁇ 1 .
  • a second error amplifier 402 is provided, the negative input of which is connected to the reference voltage Ur and the positive input of which is connected to the means 20 for sampling and measuring the voltage Vc delivered by the converter. 2.
  • the output of the second error amplifier 402 delivers a second error signal ⁇ 2 and the gain of the second error amplifier 402 is identical to the gain of the first error amplifier 401.
  • the output terminal of the first error amplifier 401 and the output terminal of the second error amplifier 402 are each connected to a common point which is connected to the input terminal of the integrator 43.
  • inverting means comprising an inverter comprising a first input terminal receiving the amplified error signal, a second input terminal, an output terminal and an inversion control terminal receiving the logic signal representative of the stall or non-stall state of the converter, means generating a reference voltage being directly connected to the second output terminal of the inverter, output terminal of the latter being directly connected to the input of the integrator means for delivering to the latter either the amplified error signal, or, on switching via the logic signal representative of the converter stall state, the reference voltage so as to position the operating point directly on the current source or voltage source zone independently of the value of the input current or of the converter voltage.
  • the regulation system which is the subject of the invention comprises, as described above, a current generator system coupled to a converter 2 with pulse width modulation.
  • the means 11 and 12 for sampling and measuring the voltage V and the current I delivered by the current generator 1 to the converter 2 are provided, these means delivering a signal representative of the above-mentioned intensity and voltage.
  • Detector means 3 at the dropout threshold of the converter 2 receive the signals representative of the above-mentioned intensity 1 and of the voltage V and deliver a logic signal C representative of the dropout or non-dropout state of the converter 2 with respect to the values threshold.
  • a regulation loop 4 regulates the width of the pulses delivered by the converter.
  • This loop comprises means 20 for sampling and measuring the voltage VC delivered by the converter 2 to the load CU and amplifier means 40 of the differential amplifier type receiving on a first input the signal delivered by the means 20 for measuring the voltage delivered by the converter and on a second input a reference voltage UR delivering the amplified error signal.
  • reversing means 42 comprise an actual reverser denoted 042 comprising a first input terminal 420 receiving the amplified error signal, a second terminal input 422, an output terminal 423 and an inversion control terminal 421 receiving the aforementioned logic signal C.
  • a generator 424 of reference voltage denoted Uc is directly connected to the second input terminal 422 of the inverter 042.
  • the output terminal 4230 of the inverter 042 is directly connected to the input of the integrating means 43 to deliver to the latter either the amplified error signal ⁇ or, on switching via the logic signal C representative of the stall or non-stall state of the converter 2, the reference voltage Uc so as to position directly the operating point on the current source or voltage source zone independently of the value of the input current or the input voltage of the converter 2.
  • the integrating means 43 and the pulse width modulation means constituted by the comparator 440 and the sawtooth generator 441 provide the same function as the same elements in the other embodiments.
  • the embodiment, object of the invention allows to replace the amplified error signal ⁇ ensuring the operation in voltage regulation on the current source area or vice versa on the voltage source area by a constant control voltage constituted by the reference voltage Uc similar to that delivered by the inverted output of the error amplifier 40 when the converter is operating in maximum power extraction mode.
  • a constant control voltage constituted by the reference voltage Uc similar to that delivered by the inverted output of the error amplifier 40 when the converter is operating in maximum power extraction mode.
  • the constant voltage Uc integrated by the integrator 43 the operating point of the converter is always returned to the corresponding operating point in the voltage source zone or vice versa in the current source zone even if , at this time, the power called by the payload CU becomes less than the maximum power that the generator can provide.
  • the operating point of the converter 2 is thus positioned on the current source zone or on the voltage source zone independently of the value of the input current or of the voltage of the converter.
  • the reference voltage Uc can be constituted by a DC voltage source of good stability. Its voltage value has a value substantially equal to the value of the amplified error signal ⁇ which it replaces for the operating point corresponding to the maximum power extraction regime so as to impose, on reduction of the power demand, a position of the operating point of the converter and of the generator 1 either in the current source area or in the voltage source area.
  • control voltage Uc may in fact correspond to one of the two values Uc1 or Uc2, which are close to the control voltage Uc. It will be understood in this case that the two values Uc1 and Uc2 can then correspond to the choice of operation in the voltage zone respectively of the current zone of the generator 1 as a function of the characteristics of the generator and of those of the chopping converter 2.
  • a switch 4000 allows a user to switch to ensure the choice between the corresponding control voltages Uc1 or Uc2, the voltage Uc1 having for value the voltage value during the operation in maximum power extraction mode for the amplifier 402 represented in FIG.
  • the switch 4000 can comprise two parts 4000 A, 4000 B forming a double switch, the second part 4000 B comprising a first and a second input terminal, which are respectively connected to the output of the amplifier 401, 402.
  • the output terminal of the second part 4000 B is connected to the first input terminal of the inverter 042.
  • the amplified error signal ⁇ is delivered by an amplifier 401 playing the role of comparator with respect to a reference voltage denoted Ur.
  • the comparator 401 is followed by the switching stage denoted 42 and of course playing the role of the reversing means 42 previously described.
  • the switching stage 42 is connected in parallel to the output of the amplifier 401 and is constituted by a transistor T1 mounted as a common emitter and the base of which is connected directly to the output Q of the flip-flop 33 of the means 3 threshold detectors converter stall 2.
  • the reference voltage Uc is generated on switching at its high level from the output Q of the flip-flop 33 by saturation of the above-mentioned transistor T1. This switching then makes it possible to apply a substantially zero reference voltage Uc to the input of the integrating means 43, at the saturation voltage denoted VCEsat near the transistor T1, similar to the error voltage of the amplifier replaced during the mode maximum power extraction.
  • the regulation system which is the subject of the invention appears to be particularly well suited to space use for supplying electrical energy to electronic circuits of artificial satellites or aircraft and more particularly to space exploration probes.
  • the intensity generator 1 due to the near impossibility of intervention in the event of failure and the ignorance of the evolution of the behavior of the solar generator, the intensity generator 1, this regulation electronics makes it possible to guard against operating faults.
  • unfavorable operating conditions unfavorable conditions consisting for example of various degradations, state of penumbra, deflection of the sun, distance from the sun, variation in temperature, or the like.
  • a buffer storage assembly constituted by a battery possibly in series with a discharge regulator which can be connected in parallel on the payload CU, at the output of the converter.
  • the operation of the entire regulation system which is the subject of the invention is of course not modified by the presence of such a buffer storage assembly.
  • the system for regulating the operating point of a DC power supply object of the invention makes it possible to ensure satisfactory operation even in spite of the modification of the current-voltage characteristics of the solar generator, modification due to aging and / or environmental conditions of the electronic components constituting it.

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  • Engineering & Computer Science (AREA)
  • Electromagnetism (AREA)
  • Sustainable Development (AREA)
  • Sustainable Energy (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Life Sciences & Earth Sciences (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Automation & Control Theory (AREA)
  • Dc-Dc Converters (AREA)
  • Control Of Electrical Variables (AREA)
  • Control Of Voltage And Current In General (AREA)
EP89400219A 1988-01-29 1989-01-26 Regulierungssystem des Arbeitspunktes einer Gleichstromversorgung Expired - Lifetime EP0326489B1 (de)

Priority Applications (1)

Application Number Priority Date Filing Date Title
AT89400219T ATE86399T1 (de) 1988-01-29 1989-01-26 Regulierungssystem des arbeitspunktes einer gleichstromversorgung.

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
FR8801057 1988-01-29
FR8801057A FR2626689B1 (fr) 1988-01-29 1988-01-29 Systeme de regulation du point de fonctionnement d'une alimentation a courant continu
FR8809682 1988-07-18
FR888809682A FR2634293B2 (fr) 1988-01-29 1988-07-18 Systeme de regulation du point de fonctionnement d'une alimentation a courant continu en zone de caracteristique generateur de tension ou de courant imposee

Publications (2)

Publication Number Publication Date
EP0326489A1 true EP0326489A1 (de) 1989-08-02
EP0326489B1 EP0326489B1 (de) 1993-03-03

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EP89400219A Expired - Lifetime EP0326489B1 (de) 1988-01-29 1989-01-26 Regulierungssystem des Arbeitspunktes einer Gleichstromversorgung

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US (1) US4899269A (de)
EP (1) EP0326489B1 (de)
JP (1) JP2765716B2 (de)
DE (1) DE68905049T2 (de)
ES (1) ES2038420T3 (de)
FR (1) FR2634293B2 (de)

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DE4030494C1 (en) * 1990-09-26 1992-04-23 Helmut 6753 Enkenbach De Jelonnek Solar power generator setter - has indicator in centre of concentric circles calibrated in ambient temperatures
EP0628901A2 (de) * 1993-06-11 1994-12-14 Canon Kabushiki Kaisha Leistungsregelungsverfahren und -vorrichtung und Stromversorgungssystem damit
EP0653692A3 (de) * 1993-11-16 1995-09-27 Canon Kk Vorrichtung und Verfahren zur Regelung der Leistungsversorgung einer Batteriestromversorgung.
AT409674B (de) * 1999-03-22 2002-10-25 Felix Dipl Ing Dr Himmelstoss Verfahren zur erfassung der messdaten von solargeneratoren zur bestimmung des punktes maximaler leistung
AU757080B2 (en) * 2000-09-29 2003-01-30 Canon Kabushiki Kaisha Solar battery module and power generation apparatus
EP2110729A1 (de) * 2007-02-09 2009-10-21 Ingeteam Energy, S.A. Einrichtung zur umwandlung von gleichstrom in wechselstrom und zur steuerung der maximalleistung für solarpanels
WO2012032274A1 (fr) * 2010-09-10 2012-03-15 Nexcis Commande du fonctionnement d'un panneau photovoltaïque
CN111679713A (zh) * 2020-06-28 2020-09-18 齐鲁工业大学 一种直接计算的光伏最大功率点跟踪方法

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US5289359A (en) * 1991-02-13 1994-02-22 Charles Industries, Limited DC-DC power converter including sensing means for providing an output when the reserve power of the converter falls below a predetermined amount for a given input voltage
JPH06292365A (ja) * 1992-10-30 1994-10-18 Fuji Electric Co Ltd Ｐｗｍインバータの制御方法および制御装置
DE69401965T2 (de) * 1993-01-21 1997-10-09 Lambda Electronics Inc Überlastschutz eines Schaltnetzteiles
AT401976B (de) * 1993-04-08 1997-01-27 Sassmann Alfred Anordnung zur einregelung der leistungsabgabe von solarzellenanlagen
DE4343822C1 (de) * 1993-12-22 1994-12-22 Ant Nachrichtentech Einrichtung zur selbsttätigen Einstellung eines optimalen Arbeitspunktes für den Betrieb eines Verbrauchers an einer Spannungsquelle
US5604430A (en) * 1994-10-11 1997-02-18 Trw Inc. Solar array maximum power tracker with arcjet load
US5594325A (en) * 1995-08-10 1997-01-14 David B. Manner Spacecraft power system architecture to mitigate spacecraft charging effects
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EP0628901A2 (de) * 1993-06-11 1994-12-14 Canon Kabushiki Kaisha Leistungsregelungsverfahren und -vorrichtung und Stromversorgungssystem damit
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JPH01224817A (ja) 1989-09-07
US4899269A (en) 1990-02-06
ES2038420T3 (es) 1993-07-16
FR2634293B2 (fr) 1990-10-19
JP2765716B2 (ja) 1998-06-18
DE68905049T2 (de) 1993-06-17

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