EP0241979B1 - Disposition de circuit pour la réduction de courant parasite originaire d'une charge - Google Patents

Disposition de circuit pour la réduction de courant parasite originaire d'une charge Download PDF

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Publication number
EP0241979B1
EP0241979B1 EP87200622A EP87200622A EP0241979B1 EP 0241979 B1 EP0241979 B1 EP 0241979B1 EP 87200622 A EP87200622 A EP 87200622A EP 87200622 A EP87200622 A EP 87200622A EP 0241979 B1 EP0241979 B1 EP 0241979B1
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EP
European Patent Office
Prior art keywords
current
voltage
load
circuit
supply voltage
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP87200622A
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German (de)
English (en)
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EP0241979A2 (fr
EP0241979A3 (en
Inventor
Manfred Dr. Albach
Armin Wegener
Hubert Raets
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Philips Intellectual Property and Standards GmbH
Koninklijke Philips NV
Original Assignee
Philips Patentverwaltung GmbH
Philips Gloeilampenfabrieken NV
Koninklijke Philips Electronics NV
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Priority claimed from DE19863612380 external-priority patent/DE3612380A1/de
Priority claimed from DE19863612378 external-priority patent/DE3612378A1/de
Application filed by Philips Patentverwaltung GmbH, Philips Gloeilampenfabrieken NV, Koninklijke Philips Electronics NV filed Critical Philips Patentverwaltung GmbH
Publication of EP0241979A2 publication Critical patent/EP0241979A2/fr
Publication of EP0241979A3 publication Critical patent/EP0241979A3/de
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Publication of EP0241979B1 publication Critical patent/EP0241979B1/fr
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H02M1/15—Arrangements for reducing ripples from dc input or output using active elements

Definitions

  • the invention relates to a circuit arrangement with a load, which is coupled to a supply voltage source, according to the preamble of the main claim.
  • a circuit arrangement is known from EP 00 59 053, in which a supply voltage source, which supplies an alternating voltage, is coupled to a load, a switching power supply, via a filter.
  • the switching power supply causes an interference current due to switching operations, the frequency of which is significantly higher than that of the current of the supply voltage source and which has an effect on the supply voltage source.
  • the filter consisting of a coil and a capacitor serves to prevent this interference current.
  • the coil is connected to the supply voltage source and on the other hand to the load and the capacitor lying parallel to the load.
  • the circuit arrangement described therein for reducing an interference current caused in a load contains a compensation circuit which is arranged in a connecting branch between the load and a supply voltage source.
  • the compensation circuit comprises a controlled signal source with a capacitor.
  • the controlled signal source is designed as a bridge circuit, which contains switching transistors in each branch.
  • the switching transistors are controlled by a control circuit so that the transistors arranged in opposite bridge branches are each conductive or blocked.
  • the compensation current flows through a transistor and the capacitor to the transistor in the opposite branch.
  • Half of the supply voltage drops across a transistor, which means that transistors with a high dielectric strength must be used.
  • a voltage divider is connected in parallel with the load and supplies the control circuit with a voltage which is proportional to the interference voltage and the supply voltage.
  • the control circuit determines the duration of the conductive or blocked state of a transistor from this voltage. With the help of the bridge circuit, a current largely compensating for the interference current is generated. Due to the non-ideal components in the controlled signal source and the control circuit, the interference current is not fully compensated.
  • an active low-pass filter which is connected between a supply voltage source and a load, such as a teleprinter.
  • the variable load causes interference currents that are largely compensated for by the active filter.
  • the active filter contains a compensation circuit, an inductive element and a capacitive element.
  • the interference currents caused by the load are partially eliminated by the inductive and capacitive element.
  • a further reduction is achieved through the compensation circuit.
  • a measuring resistor that measures in a supply line is arranged between the supply voltage source and the compensation circuit, the existing interference current, which is fed to a voltage-current converter via a voltage amplifier.
  • the voltage-current transformer generates a compensation current that counteracts the existing interference current. A direct current is superimposed on this compensation current because the compensation circuit is supplied with energy by the supply voltage source.
  • the invention has for its object to provide a circuit arrangement of the type mentioned which contains a simply designed compensation circuit which brings about a substantial reduction in the interference current.
  • a current is conducted into the capacitor with the circuit, which corresponds approximately to the interference current in terms of phase and size.
  • the interference current is largely conducted through the controlled signal source via the capacitor, so that only a small proportion of the interference current can reach the supply voltage source.
  • the control signal that is supplied to the signal source depends on the interference current.
  • the control signal is obtained here by means of two measuring resistors and the amplifier circuit.
  • the current that flows through the first measuring resistor contains the total Interference current.
  • a current flows in the second measuring resistor which still has a small proportion of the interference current.
  • the currents flowing through the two measuring resistors cause a voltage drop. These voltages are subtracted from each other in the amplifier circuit and form the control signal for the controlled signal source.
  • the second measurement on the second measuring resistor results in a further reduction in the interference current.
  • the voltage difference between the voltage at the load and the voltage at the output of the controlled switching source drops, which is usually an order of magnitude smaller than the voltage at the load.
  • the transistors used in the controlled signal source therefore do not need to have a dielectric strength that corresponds to the voltage at the load.
  • the capacitor 11 is connected in series with the base-emitter path of the replacement transistor. Its base-collector path is bridged by the resistor 27.
  • a resistor 25 leads to the base terminal of the replacement transistor, ie to one terminal of capacitor 11, and voltage source 19 is also connected with its negative pole to this terminal 3. The positive pole of the voltage source 19 is at the collector terminal of the replacement transistor.
  • the voltage ripple at the load 9 is compensated for by a series regulator.
  • the resistor 21 is in series with the load 9 and the entire load current flows through it. Since the resistor 21 has a significant amount, there is the problem of a very poor efficiency, as with all series regulators.
  • a current flows through capacitor 11 and increases the base current set by the voltage divider from resistors 25 and 27 through the replacement transistor.
  • the transistor current thereby increased (in the collector-emitter path of the replacement transistor) causes a larger voltage drop across the resistor 21.
  • the change in voltage across the capacitor 7, which is attributable to the ripple, is therefore not noticeable at the load 9.
  • a circuit arrangement is known from French patent application 21 32 235, which likewise does not provide any suggestion for solving the present problem.
  • the circuit described there can only be used with sources of lower voltages, e.g. Battery chargers occur.
  • sources of lower voltages e.g. Battery chargers occur.
  • higher losses occur in particular in the output stage of the amplifier G due to a direct current component of the current i.
  • the output stage of the amplifier is designed here as a "class A amplifier", which naturally has higher losses.
  • the teaching according to the present application also enables the low-loss compensation of interference currents in supply sources with high supply voltages.
  • the circuit arrangement according to the invention can either contain one or more connection branches.
  • a current is conducted into the capacitor connected to the signal source, which largely corresponds to the interference current measured in a supply line.
  • Part of the interference current is largely derived in each connection branch, so that only a small proportion of the interference current can reach the supply voltage source.
  • the control signal that of the respective signal source supplied depends on the current in a supply line. It is not necessary that this dependency be linear.
  • an active low-pass filter is known from US Pat. No. 3,414,824, which is connected between a supply voltage source and a variable load, for example a teleprinter.
  • the variable load causes interference currents that are largely compensated for by the active filter.
  • the active filter contains a compensation circuit, an inductive element and a capacitive element.
  • the interference currents caused by the load are largely from the inductive and capacitive element eliminated.
  • a further reduction is achieved through the compensation circuit.
  • a measuring resistor measures the existing interference current, which is fed to a voltage-current converter via a voltage amplifier.
  • the voltage-current transformer generates a counter current, which counteracts the existing interference current. A direct current is superimposed on this counter current.
  • the compensation circuit is supplied with energy by the supply voltage source. For this reason, a direct current is superimposed on the counter current. As a result, in addition to the losses occurring in the inductive and capacitive elements, there are additional high losses.
  • the supply voltage source can in principle only be a DC voltage source since it supplies the compensation circuit with energy.
  • the direct component is suppressed by a capacitor in the connecting branch.
  • most of the voltage across the load drops across this capacitor.
  • the compensation circuit generates a current opposite to the interference current without a DC component. With this implementation, the losses in the compensation circuit are very much lower than in US Pat. No. 3,414,824.
  • the compensation circuit is also not supplied with energy by the supply voltage source, but receives it from an external energy source. If the load is designed as a switching power supply, the compensation circuit can receive the energy from the load.
  • the circuit arrangement has only one connecting branch, it is provided that from a first Measuring resistor, which is arranged in a supply line between the load and the series circuit comprising the capacitor and the signal source, the voltage drop the control signal is obtained.
  • the voltage across the measuring resistor is dependent on the current supplied by the supply voltage source and the interference current caused by the load.
  • an amplifier circuit is supplied with the voltage dropping across the first measuring resistor at its first input and a reference voltage at its second input, which approximately corresponds to the time profile of the current of the supply voltage source , forms an output voltage that represents the control signal.
  • a signal which is independent of the current of the supply voltage source can also be obtained by means of a capacitor which is arranged between the measuring resistor and the controlled signal source. The capacitance of the capacitor must be chosen so that it suppresses the low-frequency signal caused by the current of the supply voltage source.
  • the reference voltage is obtained from a second measuring resistor, which is arranged between the supply voltage source and the connecting branch and on which the residual interference current remaining due to the incomplete compensation of the interference current is also measured.
  • the compensation circuit contains at least two connecting branches, that first measuring resistors are arranged in a feed line in each case between the connecting branches and between the load and a connecting branch and that the control signal for the respective signal source is obtained from the voltage drop in the respective first measuring resistor.
  • the current of the supply voltage source is measured with the interference current in the first measuring resistors.
  • the voltage across the first measuring resistors is dependent on the current supplied by the supply voltage source and the interference current caused by the load.
  • each signal source is assigned an amplifier circuit which is supplied with the voltage dropping at the respective first measuring resistor at its first input and a reference voltage at its second input is, which approximately corresponds to the time course of the current of the supply voltage source, and which forms an output voltage which represents the control signal.
  • a signal independent of the current of the supply voltage source could be obtained instead of the amplifier circuit by means of a capacitor which is arranged between the respective first measuring resistor and the respective controlled signal source. The capacitance of the capacitor must be selected so that it suppresses the low-frequency signal caused by the current of the supply voltage source.
  • the comparison voltage for the respective amplifier circuit can be obtained at second measuring resistors, which are each arranged in a supply line between the connecting branches and between the supply voltage source and a connecting branch and which are each connected to a connecting branch and a first measuring resistor at which the other input voltage of the amplifier circuit falls off.
  • each controlled signal source it is provided that it comprises a power amplifier with a complementary output stage.
  • the invention can be used in such a circuit arrangement which contains a switching power supply as a load.
  • the circuit arrangement according to FIG. 1 has a supply voltage source 1 which e.g. outputs a DC voltage of 50 V.
  • a DC voltage only has a portion at a frequency of zero.
  • the supply voltage source l supplies a load 2 via feed lines, which e.g. can be a switching power supply designed as an up-voltage converter. Switching power supplies of this type are generally operated at switching frequencies of approximately 20 kHz to 200 kHz. These switching processes cause an interference current in the input current of the supply voltage source 1, the frequency spectrum of which has components in the switching frequency and its harmonics.
  • a compensation circuit which contains a capacitor 3, a controlled signal source 4 and an amplifier circuit 5.
  • the current Ya that flows through the load and that contains the interference current, causes a voltage drop across a measuring resistor l0.
  • the resistor l0 should preferably be selected such that it is as small as possible on the one hand to limit the losses occurring on it, but on the other hand the voltage drop across it has a sufficiently high level for driving the amplifier circuit 5.
  • the measuring resistor l0 is arranged between the negative reference point of the supply voltage source l and a connection point of the load 2.
  • the amplifier circuit 5 is connected at the connection point between the load 2 and the measuring resistor 10.
  • the amplifier circuit 5 contains an amplifier 11, the inverting input of which is connected to the connection point mentioned above via a resistor l2 and to its output via a resistor l3.
  • a resistor l4 connected to the negative reference point of the supply voltage source l and a resistor l5 connected to a reference voltage source Uref are connected to the non-inverting input of the amplifier 11.
  • the amplifier circuit 5 contains an amplifier 16, the non-inverting input of which is connected to the negative reference point and the inverting input of which is connected to the output of the amplifier 11 via a resistor 17 and to its output via a resistor 18.
  • the output of the amplifier 16 forms the output of the amplifier circuit 5.
  • the difference between the reference voltage at the non-inverting input of the amplifier 11, which is an image of the voltage supplied by the supply voltage source 1, and the voltage drop across the first measuring resistor is formed.
  • the voltage at the output of the amplifier circuit 5 is dependent on that generated by the load 2 Interference current.
  • the resistors l2 to l5 and l7, l8 and the reference voltage Uref, which is an order of magnitude smaller than the DC voltage of the supply voltage source 1, can be chosen so that there is a DC matching of the amplification circuit 5 and the following controlled signal source 4.
  • the controlled signal source 4 contains a power amplifier with a complementary output stage of class AB.
  • the complementary output stage contains an NPN transistor 20 and a PNP transistor 2l.
  • the collector of the transistor 2l is connected to the negative reference point of the supply voltage source l and the base on the one hand to a resistor 22 connected to the negative reference point and on the other hand to the cathode of a diode 23.
  • the anode of the diode 23 is on the one hand connected to the output of the amplifier circuit 5, which supplies the control voltage, and on the other hand connected to the cathode of a diode 24.
  • the base of transistor 20 is connected to the connection point between the anode of diode 24 and a resistor 25.
  • a supply voltage Ub which is an order of magnitude lower than the DC voltage of the supply voltage source 1, is applied to the collector of the transistor 20 and to the other connection point of the resistor 25.
  • the emitters of the two transistors 20 and 2l are connected via a connection point to the capacitor 3, which in turn is connected to the positive connection point of the supply voltage source l.
  • the controlled signal source 4 drives a current Yc, which is approximately equal to the interference current, through the capacitor 3.
  • the transistor 20 or the transistor 2l is conductive. If transistor 20 is conductive, the required current Yc is drawn from the voltage source, which supplies the voltage Ub and which is connected to the ground connection of the supply voltage source 1, which is not shown here. If the transistor 20 is conductive, the current Yc flows through it to the negative reference point.
  • the capacitor 3 prevents the DC voltage of the controlled signal source from acting on the supply voltage source 1 and the load 2. The voltage difference across the capacitor 3 drops between the voltage at the load 2 and the voltage at the output of the signal source 4, which is generally an order of magnitude smaller than the voltage at the load 2.
  • FIG. 2 one possibility is shown of how a further reduction of the interference current can be achieved.
  • the circuit elements with the same functions as in Fig. 1 are provided with the same reference numerals.
  • a difference in the exemplary embodiment of FIG. 2 arises in comparison to the exemplary embodiment according to FIG. 1 only in the amplifier circuit 5.
  • the resistor 12 is connected, which on the other hand is connected to the inverting input of the amplifier 11 is.
  • the inverting input is connected to its output via the resistor l3.
  • the non-inverting input is connected to the negative connection of the supply voltage source 1.
  • the amplifier 11 At the non-inverting input of the amplifier 11 there is a voltage which drops across a second measuring resistor 30 which is between the negative connection of the supply voltage source 1 and the first measuring resistor l0 is arranged.
  • the negative connection of the voltage source Ub from which both the signal source 4 and the amplifiers 11 and 16 are supplied, is connected to the connection point between the two measuring resistors 10 and 30.
  • the further structure of the amplifier circuit 5 is identical to the structure according to the exemplary embodiment in FIG. 1.
  • the difference between the voltage across the measuring resistor l0 and the voltage across the measuring resistor 30 is formed in the amplifier circuit 5 in accordance with the exemplary embodiment in FIG. 2.
  • connection branches are used.
  • the example according to FIG. 3 has a supply voltage source 10, which for example emits a DC voltage of 50 V.
  • the direct voltage supplied by the supply voltage source 10l only has parts at a frequency of zero.
  • the supply voltage source l0l supplies a load l02 via feed lines, which can be, for example, a switching power supply designed as an step-up voltage converter. Switching power supplies of this type are generally operated at switching frequencies of approximately 20 kHz to 200 kHz. These switching processes cause an interference current in the input current of the supply voltage source l0l, the frequency spectrum of which has components at the switching frequency and its harmonics.
  • a compensation circuit which contains a first connecting branch with a capacitor l03, with a controlled signal source l04 and with an amplifier circuit l05 and a second connecting branch with a capacitor l06, with a controlled signal source l07 and with an amplifier circuit l08.
  • the current Ya which flows through the load and which contains the interference current causes a voltage drop across a measuring resistor 11.
  • the measuring resistor ll0 should preferably be chosen so that it is as small as possible to limit the losses that arise on the one hand, but on the other hand the voltage drop across it has a sufficiently high level to control the amplifier circuit l05.
  • This resistor ll0 is connected on the one hand to a connection point of the load l02 and on the other hand to a second measuring resistor l30 connected to the negative connection point of the supply voltage source l0l.
  • the connection point between the two measuring resistors ll0 and l30 is referred to as the reference point of the first connecting branch.
  • the amplifier circuit l05 is connected at the connection point between the load l02 and the measuring resistor ll0.
  • the amplifier circuit l05 contains an amplifier lll, the inverting input of which is connected via a resistor ll2 to the connection point mentioned above and via a resistor ll3 to its output.
  • a resistor ll4 connected to the reference point of the first connecting branch and a resistor ll5 connected to a reference voltage source Uref are connected to the non-inverting input of the amplifier III.
  • amplifier circuit 106 contains an amplifier 116, whose non-inverting input is at the reference point of the first Connection branch is laid and its inverting input is connected via a resistor ll7 to the output of the amplifier III and via a resistor ll8 to its output.
  • the output of amplifier ll6 forms the output of amplifier circuit l05.
  • the difference between the voltage at the measuring resistor ll0 and a reference voltage at the non-inverting input of the amplifier lll is formed in the amplifier circuit l05, which is an image of the direct voltage supplied by the supply voltage source l0l.
  • the voltage at the output of the amplifier circuit l05 depends on the interference current generated by the load l02.
  • the resistors ll2 to ll5 and ll7, ll8 and the reference voltage Uref which is an order of magnitude smaller than the DC voltage of the supply voltage source l0l, can be selected so that there is a DC matching of the amplification circuit l05 and the following controlled signal source l04.
  • the controlled signal source l04 contains a power amplifier with a complementary output stage of class AB.
  • the complementary output stage comprises an NPN transistor l20 and a PNP transistor l2l.
  • the collector of the transistor l2l is connected to the reference point of the first connection branch and the base is connected on the one hand to a resistor l22 connected to the reference point of the first connection branch and on the other hand to the cathode of a diode l23.
  • the anode of the diode l23 is connected on the one hand to the output of the amplifier circuit l05, which supplies the control voltage, and on the other hand to the cathode of a diode l24.
  • the base of the transistor I20 is connected to the connection point between the anode of the diode I24 and a resistor I25.
  • a supply voltage Ub that is an order of magnitude lower is than the DC voltage of the supply voltage source l0l, is connected to the collector of the transistor l20 and to the other connection point of the resistor l25.
  • the emitters of the two transistors l20 and l2l are connected via a connection point to the capacitor l03, which in turn is connected to the positive connection point of the supply voltage source l0l.
  • the controlled signal source l04 drives a current Yc, which is approximately equal to the interference current, through the capacitor l03 depending on the output voltage supplied by the amplifier circuit l05.
  • a current Yc which is approximately equal to the interference current
  • transistor l20 or transistor l2l is conductive. If the transistor l20 is conductive, the required current Yc is drawn from the voltage source, which supplies the voltage Ub and is connected to the negative connection point of the supply voltage source l0l, which is not shown here. If the transistor l2l is conductive, the current Yc flows through it to the reference point of the first connection branch.
  • the capacitor l03 prevents the DC voltage of the controlled signal source from acting on the supply voltage source l0l and the load. The voltage difference across the capacitor l03 drops between the voltage at the load l02 and the voltage at the output of the signal source l04, which is generally an order of magnitude smaller than the voltage at the load 2.
  • the interference current which has not been derived via the capacitor l03, will be referred to as partial interference current in the following.
  • This Partial interference current causes a voltage drop in measuring resistor l30.
  • the measuring resistor l30 should be selected according to the same criteria as the measuring resistor ll0.
  • the amplifier circuit 108 is connected to the negative reference point of the first connection branch.
  • the amplifier circuit l08 contains an amplifier l3l, the inverting input of which is connected via a resistor l32 to the negative reference point of the first connecting branch and via a resistor l33 to its output.
  • a resistor l34 connected to the negative reference point of the supply voltage source l0l and a resistor l35 connected to the reference voltage source Uref are connected to the non-inverting input of the amplifier l3l.
  • an amplifier l36 is present in the amplifier circuit l08, the non-inverting input of which is connected to the negative connection of the supply voltage source l0l and the inverting input of which is connected via a resistor l37 to the output of the amplifier l3l and via a resistor l38 to its output.
  • the output of amplifier circuit l08 is also the output of amplifier l36.
  • the amplifier circuit l08 controls a controlled signal source l07, which comprises a power amplifier with a complementary output stage of class AB.
  • the complementary output stage contains an NPN transistor l40 and a PNP transistor l4l.
  • the collector of the transistor l40 is connected to the supply voltage Ub and connected to a resistor l42, the other connection point of which is connected to the base of the transistor l40 and to the anode of a diode l43.
  • the cathode of diode I43, the anode of a diode I44 and the output of amplifier I36 are connected to a common connection point.
  • the cathode of the diode l44 is connected to the one negative connection of the supply voltage source l0l connected resistor l45 and connected to the base of the transistor l4l.
  • the collector of the transistor l4l is connected to the negative terminal of the supply voltage source l0l.
  • the interconnected emitters of transistors l40 and l4l are connected via capacitor l06 to the positive connection point of supply voltage source l0l.
  • the operation of the second connection branch which contains the amplifier circuit l08, the controlled signal source l07 and the capacitor l06, is the same as described above in the explanation of the first connection branch.
  • the partial interference current is largely derived through the capacitor l06. A further reduction in the residual interference current can be achieved with one or more further connection branches.
  • the remaining interference current can be reduced further by a measure that does not require any further connection branch.
  • This possibility is shown in an exemplary embodiment, which is shown in FIG. 4.
  • the circuit elements with the same functions as in Fig. 3 are provided with the same reference numerals.
  • a difference in the exemplary embodiment in FIG. 4 arises in comparison to the example in accordance with FIG. 3 only in the amplifier circuit 105 and 108.
  • the resistor ll2 is connected, which on the other hand is connected to the inverting input of the amplifier lll.
  • the inverting input is connected to its output via resistor ll3.
  • the non-inverting input is connected to the connection point between the measuring resistor l30 and a further measuring resistor l50, which on the other hand is connected with the connection point of the resistor ll0 facing away from the load l02 is connected.
  • the further construction of the amplifier circuit l05 is identical to the construction according to the example in FIG. 3. At the non-inverting input of the amplifier lll there is a voltage which drops across the measuring resistor l50. This voltage is proportional to the current flowing through this resistor 150.
  • the voltage across the measuring resistor l50 which is proportional to the current of the voltage source l0l and a low partial interference current, is used to generate the comparison voltage on the one hand and to further reduce the partial interference current on the other hand.
  • the resistor l32 is connected to the connection point between the two resistors l30 and l50.
  • This resistor l32 and the resistor l33 which is connected with its other connection to the output of the amplifier l3l, are connected to the inverting input of the amplifier l3l.
  • the non-inverting input of the amplifier l3l is connected to the negative connection point of the supply voltage source l0l.
  • a measuring resistor l5l is connected between the negative connection point of the supply voltage source l0l and the connection point of the resistor l30, which has no connection to the resistor l50.
  • the further structure of the amplifier circuit 108 is identical to the structure according to the example in FIG. 3.
  • the voltage drop across this measuring resistor l5l is proportional to the current flowing through this resistor.
  • the resistor l5l has the same function as the resistor l50.
  • the resistor l30 can be omitted if the resistor l32 is not connected between the two resistors l30 and l50, as shown in FIG. 4, but between the resistors l50 and ll0.
  • the circuit arrangement according to the invention is not limited to the use of a supply voltage source which supplies a DC voltage, but can also be used if a supply voltage source supplies an AC voltage.
  • the parts of the AC voltage source must be at much lower frequencies than the parts of the interference current.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Amplifiers (AREA)
  • Power Conversion In General (AREA)
  • Dc-Dc Converters (AREA)
  • Control Of Electrical Variables (AREA)

Claims (5)

  1. Montage de circuit avec une charge (2, 102) qui est couplé à une source de tension d'alimentation (1) et qui, dans le courant de la source de tension d'alimentation (1, 101), produit un courant parasite dont la fréquence est sensiblement supérieure à celle du courant de la source de tension d'alimentation (1), comportant un circuit de compensation prévu pour réduire le courant parasite, qui comprend une branche de liaison disposée dans les lignes d'alimentation entre la charge (2) et la source de tension d'alimentation (1) et pourvu d'un condensateur (3, 103, 106) et d'une source de signaux commandée (4), qui fournit un courant par le condensateur (3), qui dépend d'un signal de commande dérivé du courant parasite et dont la grandeur et la phase sont dimensionnées d'une manière telle que le courant parasite puisse, en grande partie, traverser le condensateur (3), et comportant une première résistance de mesure (10), caractérisé en ce que la première résistance de mesure (10, 110, 130) est installée dans une ligne d'alimentation entre la charge (2) et le montage en série du condensateur (3) et de la source de signaux (4, 104, 107), qu'une seconde résistance de mesure (30, 150, 151) sur laquelle une tension de comparaison est obtenue, est installée entre la source de tension d'alimentation (1) et la branche de liaison et qu'un circuit amplificateur (5) est prévu qui reçoit, sur sa première entrée, la tension chutant au passage de la première résistance de mesure (10) et, sur sa seconde entrée, la tension de comparaison, et qui fournit un signal de commande pour la source de signaux commandée (4), le circuit amplificateur (5) ayant la forme d'un amplificateur de la classe AB.
  2. Montage de circuit suivant la revendication 1, caractérisé en ce que la tension de comparaison correspond approximativement à l'allure dans le temps du courant de la source de tension d'alimentation (1).
  3. Montage de circuit suivant la revendication 1 ou 2, caractérisé en ce que le circuit de compensation comprend au moins deux branches de liaison (103, 104, 106, 107), que des premières résistances de mesure (110, 130) sont installées dans une ligne d'alimentation, chaque fois entre les branches de liaison et entre la charge (102) et une branche de liaison, et qu'à chaque source de signaux (104, 107) est associé un circuit amplificateur (105, 108) qui reçoit, sur sa première entrée, la tension chutant au passage de la première résistance de mesure respective (110, 130) et, sur sa seconde entrée, une tension de comparaison, et le circuit amplificateur forme une tension de sortie qui représente le signal de commande et que la tension de comparaison est obtenue sur des secondes résistances de mesure (150, 151) qui sont installées chaque fois dans une ligne d'alimentation entre les branches de liaison et entre la source de tension d'alimentation (101) et une branche de liaison et qui sont chaque fois reliées à une branche de liaison et à une première résistance de mesure (110, 130) au passage de laquelle l'autre tension d'entrée du circuit amplificateur (105, 108) chute.
  4. Montage de circuit suivant l'une quelconque des revendications précédentes, caractérisé en ce qu'une source de signaux commandée (4, 104, 107) comprend un amplificateur de puissance avec un étage final complémentaire.
  5. Montage de circuit suivant l'une quelconque des revendications précédentes, caractérisé en ce que la charge (2, 102) a la forme d'une partie de réseau de commutation.
EP87200622A 1986-04-12 1987-04-03 Disposition de circuit pour la réduction de courant parasite originaire d'une charge Expired - Lifetime EP0241979B1 (fr)

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
DE3612378 1986-04-12
DE3612380 1986-04-12
DE19863612380 DE3612380A1 (de) 1986-04-12 1986-04-12 Schaltungsanordnung zur verringerung eines in einer last hervorgerufenen stoerstromes
DE19863612378 DE3612378A1 (de) 1986-04-12 1986-04-12 Schaltungsanordnung zur verringerung eines in einer last hervorgerufenen stoerstromes

Publications (3)

Publication Number Publication Date
EP0241979A2 EP0241979A2 (fr) 1987-10-21
EP0241979A3 EP0241979A3 (en) 1988-10-12
EP0241979B1 true EP0241979B1 (fr) 1991-11-21

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Application Number Title Priority Date Filing Date
EP87200622A Expired - Lifetime EP0241979B1 (fr) 1986-04-12 1987-04-03 Disposition de circuit pour la réduction de courant parasite originaire d'une charge

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US (1) US4736152A (fr)
EP (1) EP0241979B1 (fr)
DE (1) DE3774610D1 (fr)

Families Citing this family (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE19741430A1 (de) * 1997-09-19 1999-04-01 Siemens Ag Schaltungsanordnung und Verfahren zur Unterdrückung störender Rückwirkungen eines Umrichters
ATE482695T1 (de) * 2002-12-13 2010-10-15 Durect Corp Orale darreichungsform mit flüssigen hochviskosen trägersystemen
US10778089B2 (en) * 2017-04-07 2020-09-15 Texas Instruments Incorporated Cascaded active electro-magnetic interference filter
US11601045B2 (en) 2019-04-01 2023-03-07 Texas Instruments Incorporated Active electromagnetic interference filter with damping network

Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3414824A (en) * 1966-07-11 1968-12-03 Allen Bradley Co Active low pass filter

Family Cites Families (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2132235A1 (fr) * 1971-03-31 1972-11-17 Westinghouse Brake & Signal
US3825815A (en) * 1973-06-12 1974-07-23 Westinghouse Electric Corp Electrical power system
US3875539A (en) * 1973-11-26 1975-04-01 Amp Inc High voltage ripple reduction circuit
US4016481A (en) * 1975-11-26 1977-04-05 Gte Automatic Electric Laboratories Incorporated Unmatched field effect transistors providing matched voltage-controlled resistances
EP0059053A3 (fr) * 1981-02-21 1983-05-18 THORN EMI plc Alimentation de courant à impulsions

Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3414824A (en) * 1966-07-11 1968-12-03 Allen Bradley Co Active low pass filter

Also Published As

Publication number Publication date
EP0241979A2 (fr) 1987-10-21
DE3774610D1 (de) 1992-01-02
EP0241979A3 (en) 1988-10-12
US4736152A (en) 1988-04-05

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