CN117674591B - Single-switch DC-DC converter based on improved quasi-Z source network - Google Patents
Single-switch DC-DC converter based on improved quasi-Z source network Download PDFInfo
- Publication number
- CN117674591B CN117674591B CN202410125853.1A CN202410125853A CN117674591B CN 117674591 B CN117674591 B CN 117674591B CN 202410125853 A CN202410125853 A CN 202410125853A CN 117674591 B CN117674591 B CN 117674591B
- Authority
- CN
- China
- Prior art keywords
- diode
- inductance
- winding
- power switch
- switch tube
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
- 239000003990 capacitor Substances 0.000 claims abstract description 118
- 238000004804 winding Methods 0.000 claims abstract description 93
- 238000010168 coupling process Methods 0.000 claims abstract description 73
- 238000005859 coupling reaction Methods 0.000 claims abstract description 73
- 230000008878 coupling Effects 0.000 claims abstract description 72
- 238000000034 method Methods 0.000 claims abstract description 31
- 238000004146 energy storage Methods 0.000 claims abstract description 23
- 230000014509 gene expression Effects 0.000 claims description 8
- 230000005284 excitation Effects 0.000 claims description 4
- 230000008859 change Effects 0.000 description 11
- 238000010586 diagram Methods 0.000 description 8
- 230000008569 process Effects 0.000 description 7
- 230000007423 decrease Effects 0.000 description 4
- 238000006243 chemical reaction Methods 0.000 description 3
- 239000004576 sand Substances 0.000 description 3
- 238000012360 testing method Methods 0.000 description 3
- 239000000463 material Substances 0.000 description 2
- 230000036962 time dependent Effects 0.000 description 2
- 230000009286 beneficial effect Effects 0.000 description 1
- 230000005540 biological transmission Effects 0.000 description 1
- 230000007547 defect Effects 0.000 description 1
- 238000013461 design Methods 0.000 description 1
- 238000007599 discharging Methods 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 230000003631 expected effect Effects 0.000 description 1
- 238000000605 extraction Methods 0.000 description 1
- 230000001939 inductive effect Effects 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 238000010248 power generation Methods 0.000 description 1
- 230000008054 signal transmission Effects 0.000 description 1
- 238000012546 transfer Methods 0.000 description 1
Abstract
The invention disclosesA single-switch DC-DC converter based on improved quasi-Z source network is disclosed, which includes DC input power supplyEnergy storage inductorL 1 First diodeD 1 Second diodeD 2 Third diodeD 3 Fourth diodeD 4 A first capacitorC 1 A first output capacitorC o1 A second output capacitorC o2 A third output capacitorC o3 Fourth output capacitorC o4 Power switch tubeSLoad(s)RAnd three-winding coupling inductanceL 2a 、L 2b 、L 2c The method comprises the steps of carrying out a first treatment on the surface of the Energy storage inductorL 1 Power switch tubeSA first capacitorC 1 Coupling inductanceL 2a 、L 2b First diodeD 1 And a first output capacitorC o1 The improved quasi-Z source network is formed together, the advantages of continuous input current and passive circuit clamping of the quasi-Z source converter are inherited, and the improved quasi-Z source network has excellent boosting capability by combining the use of coupling inductors. The invention only uses one switching tube and realizes the soft switching characteristic of all active devices, reduces the switching loss, reduces the electromagnetic interference in the circuit and improves the efficiency and the reliability of the converter.
Description
Technical Field
The invention belongs to the technical field of DC-DC converters, and particularly relates to a single-switch DC-DC converter based on an improved quasi-Z source network.
Background
In recent years, more and more devices are required for high voltage sites, such as photovoltaic grid-connected systems, high voltage direct current transmission systems, micro power grid-connection, and the like. The non-isolated high-boost DC-DC converter is widely applied to the direct-current micro-grid system, and the application of the non-isolated high-boost DC-DC converter reduces the voltage level of the micro-source modules, so that the number of the series micro-source modules is reduced, and the safety of the direct-current micro-grid system is further improved. The DC-DC converter for the direct current micro-grid system has the characteristics of high voltage gain, small input current ripple, high efficiency, simple structure, low electromagnetic interference and the like.
Document x.j. Zhang, l. Sun, y.s. guard, s.h. Han: a Novel High Step-Up DC-DC converter with inductively coupled switched capacitors is provided, which uses parallel charging and series discharging of capacitors and additional inductive coupling to obtain higher Step-Up gain. By utilizing the energy stored in the coupling inductance leakage current, the zero-voltage switch can be realized by both switches, so that the switching loss is reduced, the efficiency is improved, but the voltage gain is not high enough; document t.j. Liang, p.luo and k.h. Chen, a High Step-Up DC-DC Converter with Three-Winding Coupled Inductor for Sustainable Energy Systems J. IEEE trans. Ind. Electron, 2022, 69 (10): 10249-10258, proposes a High boost DC-DC converter with continuous input current suitable for sustainable energy systems, implementing clamping, boosting functions of active switching inductance and switching capacitance by means of a three-winding coupled inductance, two power switches, three diodes and three capacitors, the input inductance being replaced by a winding of coupled inductance, reducing the volume of the converter, with the drawback of insufficient voltage gain, high device stress being unfavorable for the selection; document s.hasanmour, y.p. Siwakoti, and f. Blaabjerg, A New High Efficiency High Step-Up DC-DC Converter for Renewable Energy Applications J. IEEE trans.ind. Electron, 2023, 70 (2): 1489-1500, proposes a new efficient high boost DC-DC converter for renewable energy sources that uses a three-coupled inductor and a voltage doubling structure as boost unit to further boost the voltage gain, but the voltage stress across the switching tube is higher.
Disclosure of Invention
Aiming at the problems, the invention provides a single-switch DC-DC converter based on an improved quasi-Z source network, which only utilizes one power switch tube and realizes the soft switching characteristics of all active devices, thereby greatly reducing the switching loss and reducing the electromagnetic interference in a circuit and improving the efficiency and the reliability of the converter.
In order to achieve the technical purpose and achieve the technical effect, the invention is realized by the following technical scheme:
a single-switch DC-DC converter based on improved quasi-Z source network comprises a DC input power supplyV g Energy storage inductorL 1 First diodeD 1 Second diodeD 2 Third diodeD 3 Fourth diodeD 4 A first capacitorC 1 A first output capacitorC o1 A second output capacitorC o2 A third output capacitorC o3 Fourth output capacitorC o4 Power switch tubeSLoad(s)RFirst winding coupling inductanceL 2a Second winding coupling inductanceL 2b Third winding coupling inductanceL 2c ；
The direct current input power supplyV g Positive electrode of (a) and energy storage inductorL 1 Is connected with the first end of the power switch tube, and the negative electrode thereof is respectively connected with the power switch tubeSA third port, a first output capacitorC o1 Is a negative electrode of (2) and a loadRIs connected to the first end of the housing;
the energy storage inductorL 1 Respectively with the second end of the first diodeD 1 Anode, first capacitor of (a)C 1 Is a negative electrode of (a) and power switch tubeSIs connected to the first port of the first port;
the power switch tubeSIs used for accessing the control signal;
the first capacitorC 1 Is coupled with the third windingL 2c Is connected with the homonymous end of the formula (I);
the first diodeD 1 Respectively with the first output capacitorC o1 Positive pole, first winding coupling inductance of (a)L 2a Is the same name terminal and the second output capacitorC o2 Is connected with the negative electrode of the battery;
the second diodeD 2 Respectively coupled with the third winding by the anode of (a)L 2c Is a first winding coupled inductorL 2a The cathodes of which are respectively connected with the third diodeD 3 Anode, third output capacitance of (c)C o3 Is connected with the negative electrode of the first capacitor and the second capacitorC o2 Is connected with the positive electrode of the battery;
the third diodeD 3 Cathode of (a) is respectively connected with the fourth diodeD 4 Anode and second winding coupled inductance of (a)L 2b Is connected with the homonymous end of the formula (I);
the fourth diodeD 4 Cathode of (a) is respectively connected with the fourth output capacitorC o4 Positive electrode of (a) and loadRIs connected to the second end of the first member;
the third output capacitorC o3 The positive pole of (a) is respectively coupled with the second winding to form an inductanceL 2b Different name terminal and fourth output capacitorC o4 Is connected to the negative electrode of the battery.
Optionally, the power switch tubeSAnd a body diodeD s The method comprises the steps of carrying out a first treatment on the surface of the The power switch tubeSThird port of (d) and body diodeD s Is connected with the anode of the power switch tubeSFirst port and body diode of (2)D s Is connected to the cathode of the battery.
Optionally, the first winding couples the inductanceL 2a Second winding coupling inductanceL 2b Third winding coupling inductanceL 2c The upper part is provided with leakage inductance equivalent to leakage inductanceL 1K The method comprises the steps of carrying out a first treatment on the surface of the The first winding is coupled with inductanceL 2a The upper part is provided with an excitation inductance which is equivalent to the excitation inductanceL m 。
Optionally, the first winding couples the inductanceL 2a Second winding coupling inductanceL 2b Third winding coupling inductanceL 2c The winding turns ratio of (2) is 1:n 1 ：n 2 whereinn 1 =N 2 ：N 1 ，n 2 =N 3 ：N 1 。
Optionally, the power switch tubeSFirst diodeD 1 Second diodeD 2 Third diodeD 3 Fourth diodeD 4 The voltage stress expression of (2) is:
，
wherein,V s is a power switch tubeSThe voltage at the two ends of the capacitor,V D1 、V D2 、V D3 、V D4 respectively a first diodeD 1 Second diodeD 2 Third diodeD 3 Fourth diodeD 4 The voltage across the two terminals of the capacitor,Dis a power switch tubeSThe duty cycle at the time of conduction,Bfor the output gain of the DC-DC converter,V g is a direct current input power supplyV g Is used for the voltage across the two ends of the (c),V o is the direct current output voltage of the DC-DC converter.
Optionally, the power switch tubeSFirst diodeD 1 Second diodeD 2 Third diodeD 3 Fourth diodeD 4 The voltage stress expression of (2) is:
，
wherein,I s respectively, is a power switch tubeSIs used for the current flow of (a),Bfor the output gain of the DC-DC converter,Dis a power switch tubeSThe duty cycle at the time of conduction,I D1 、I D2 、I D3 、I D4 respectively flow through the first diodeD 1 Second diodeD 2 Third diodeD 3 Fourth diodeD 4 Is used for the current flow of (a),I o is the output current of the DC-DC converter.
Optionally, when the power switch tubeSWhen IGBT is used, the power switch tubeSThe first, second and third ends of (a) respectively represent the collector, base and emitter thereof.
Optionally, when the power switch tubeSWhen MOSEFET is used, the power switch tubeSThe first, second and third ends of (a) respectively represent the source, gate and drain thereof.
Optionally, the single-switch high-voltage gain zero-current soft-switch DC-DC converter further comprises a controller, wherein the controller is connected with the power switch tubeSThe second end of the control circuit is connected with the second end of the control circuit in a unipolar PWM control mode.
Optionally, the controller is a TMS320F28335DSP control chip.
Compared with the prior art, the invention has the beneficial effects that:
the invention provides a single-switch DC-DC converter based on an improved quasi-Z source network, which comprises a direct-current input power supplyV g Energy storage inductorL 1 First diodeD 1 Second diodeD 2 Third diodeD 3 Fourth diodeD 4 A first capacitorC 1 A first output capacitorC o1 A second output capacitorC o2 A third output capacitorC o3 Fourth output capacitorC o4 Power switch tubeSLoad(s)RAnd three-winding coupling inductanceL 2a 、L 2b 、L 2c The method comprises the steps of carrying out a first treatment on the surface of the Wherein, energy storage inductanceL 1 Power switch tubeSA first capacitorC 1 Three-coupling inductorL 2a 、L 2b 、L 2c First diodeD 1 And a first output capacitorC o1 The improved quasi-Z source network is formed together, and the converter not only inherits the advantages of continuous input current and passive clamping of a circuit of the quasi-Z source converter, but also has excellent boosting capability by combining the use of a coupling inductor. Meanwhile, through the use of a quasi-resonant circuit structure of coupling inductance leakage inductance and resonant capacitance, only one switching tube is utilized, the soft switching characteristics of all active devices are realized, the switching loss is greatly reduced, and the efficiency and the reliability of the converter with improved electromagnetic interference in the circuit are also reduced.
The invention has the characteristics of simple structure, convenient control, high voltage gain, small input ripple, common ground, high efficiency and the like, and is suitable for the field of distributed power generation systems.
Drawings
For a clearer description of an embodiment of the invention or of the solutions of the prior art, the drawings that are needed in the embodiment will be briefly described, it being obvious that the drawings in the following description are only some embodiments of the invention, and that other drawings can be obtained according to these drawings without inventive effort for a person skilled in the art, in which:
FIG. 1 is a circuit topology of a converter according to an embodiment of the present invention;
FIG. 2 shows the converter of an embodiment of the present invention during a steady-state operation period t 0 ，t 6 ]Key waveform diagram of each switch tube;
FIG. 3 shows a mode 2 power switch tube according to an embodiment of the present inventionSConduction time t 1 ，t 2 ]Is an equivalent circuit diagram of (a);
FIG. 4 (a) shows a mode 4 power switch tube according to an embodiment of the present inventionSConduction time t 3 ，t 6 ]Is an equivalent circuit diagram of (a);
FIG. 4 (b) shows a mode 5 power switch tube according to an embodiment of the present inventionSConduction time t 3 ，t 6 ]Is an equivalent circuit diagram of (a);
FIG. 4 (c) shows a mode 6 power switch tube according to an embodiment of the present inventionSConduction time t 3 ，t 6 ]Is an equivalent circuit diagram of (a);
FIG. 5 shows voltage stress and gain of an active device of a converter according to an embodiment of the inventionBA relationship diagram;
FIG. 6 shows current stress and gain of an active device of a converter according to an embodiment of the inventionBA relationship diagram.
Detailed Description
The following description of the embodiments of the present invention will be made clearly and completely with reference to the accompanying drawings, in which it is apparent that the embodiments described are only some embodiments of the present invention, but not all embodiments. The following description of at least one exemplary embodiment is merely exemplary in nature and is in no way intended to limit the invention, its application, or uses. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
The relative arrangement of the components and steps, numerical expressions and numerical values set forth in these embodiments do not limit the scope of the present invention unless it is specifically stated otherwise. Meanwhile, it should be understood that the sizes of the respective parts shown in the drawings are not drawn in actual scale for convenience of description. Techniques, methods, and apparatus known to one of ordinary skill in the relevant art may not be discussed in detail, but should be considered part of the specification where appropriate. In all examples shown and discussed herein, any specific values should be construed as merely illustrative, and not a limitation. Thus, other examples of exemplary embodiments may also include different values. It should be noted that: like reference numerals and letters denote like items in the following figures, and thus once an item is defined in one figure, no further discussion thereof is necessary in subsequent figures.
In the description of the present invention, the meaning of a number is one or more, the meaning of a number is two or more, and greater than, less than, exceeding, etc. are understood to exclude the present number, and the meaning of a number is understood to include the present number. The description of the first and second is for the purpose of distinguishing between technical features only and should not be construed as indicating or implying relative importance or implicitly indicating the number of technical features indicated or implicitly indicating the precedence of the technical features indicated.
In the description of the present invention, the descriptions of the terms "one embodiment," "some embodiments," "illustrative embodiments," "examples," "specific examples," or "some examples," etc., mean that a particular feature, structure, material, or characteristic described in connection with the embodiment or example is included in at least one embodiment or example of the present invention. In this specification, schematic representations of the above terms do not necessarily refer to the same embodiments or examples. Furthermore, the particular features, structures, materials, or characteristics described may be combined in any suitable manner in any one or more embodiments or examples.
The principle of application of the invention is described in detail below with reference to the accompanying drawings.
As shown in FIG. 1, the invention provides a single-switch DC-DC converter based on an improved quasi-Z source network, which comprises a direct current input power supplyV g Energy storage inductorL 1 First diodeD 1 Second diodeD 2 Third diodeD 3 Fourth diodeD 4 A first capacitorC 1 A first output capacitorC o1 A second output capacitorC o2 A third output capacitorC o3 Fourth output capacitorC o4 Power switch tubeSLoad(s)RFirst winding coupling inductanceL 2a Second winding coupling inductanceL 2b Third winding coupling inductanceL 2c The method comprises the steps of carrying out a first treatment on the surface of the First winding coupling inductanceL 2a Second winding coupling inductanceL 2b Third winding coupling inductanceL 2c Can be called as three-winding coupling inductanceL 2a 、L 2b 、L 2c ）；
The direct current input power supplyV g Positive electrode and reservoir of (a)Energy inductanceL 1 Is connected to the first end of the housing; the direct current input power supplyV g Respectively and switch tubeSA third port, a first output capacitorC o1 Is a negative electrode of (2) and a loadRIs connected to the common end of the first end of the pair;
the energy storage inductorL 1 Respectively with the second end of the first diodeD 1 Anode, first capacitor of (a)C 1 Is provided with a negative electrode and a switching tubeSIs connected with the common end of the first port of the (a);
the switch tubeSIs used for accessing the control signal;
the first diodeD 1 Respectively with the first output capacitorC o1 Positive pole, first winding coupling inductance of (a)L 2a Is the same name terminal and the second output capacitorC o2 Is connected with the common end of the negative electrode;
the second diodeD 2 Respectively coupled with the third winding by the anode of (a)L 2c Is a first winding coupled inductorL 2a The public end of the heteronym end is connected; the second diodeD 2 Respectively with the cathode of the third diodeD 3 Anode, third output capacitance of (c)C o3 Is connected with the negative electrode of the first capacitor and the second capacitorC o2 Is connected with the common end of the positive electrode;
the third diodeD 3 Cathode of (a) is respectively connected with the fourth diodeD 4 Anode and second winding coupled inductance of (a)L 2b Is connected with the public end of the homonymous end;
the fourth diodeD 4 Anode of (d) is respectively connected with the third diodeD 3 Cathode and second winding coupled inductor of (a)L 2b Is connected with the public end of the homonymous end; the fourth diodeD 4 Cathode of (a) is respectively connected with the fourth output capacitorC o4 Positive electrode of (a) and loadRIs connected to the second end of the first member;
the first capacitorC 1 Is coupled with the third windingL 2c Is connected with the homonymous end of the formula (I);
the third output capacitorC o3 The positive pole of (a) is respectively coupled with the second winding to form an inductanceL 2b Different name terminal and fourth output capacitorC o4 Is connected with the common end of the negative electrode;
the output capacitorC o1 、C o2 、C o3 、C o4 In series with and loadRAnd are connected in parallel.
Based on the invention, only one power switch tube is utilized, and the soft switching characteristic of all active devices is realized, so that the switching loss is greatly reduced, the electromagnetic interference in a circuit is reduced, and the efficiency and the reliability of the converter are also improved.
In a specific embodiment of the present invention, the power switch tubeSAnd a body diodeD s The method comprises the steps of carrying out a first treatment on the surface of the The power switch tubeSThird port of (d) and body diodeD s Is connected with the anode of the switch tubeSFirst port and body diode of (2)D s Is connected to the cathode of the battery.
The power switch tubeSEnergy storage inductorL 1 First winding of coupling inductanceL 2a Second winding coupling inductanceL 2b First capacitorC 1 A first capacitorC o1 The improved quasi-Z source structure is formed, the input current is continuous, and overshoot is not brought to the front-stage circuit; meanwhile, the inherent clamping circuit structure of the quasi-Z source structure clamps voltage spikes generated by leakage inductance, so that the stress on the switching device is reduced, and electromagnetic interference is reduced.
The first winding is coupled with inductanceL 2a Third winding coupling inductanceL 2c And a first capacitorC 1 A first output capacitorC o1 Forms a quasi-resonant circuit structure, and the instantaneous change of current in the loop is limited due to the existence of leakage inductance, thereby realizing the power switch tubeSZero Current (ZCS) conduction; meanwhile, the inductance is coupled through three windingsL 2a 、L 2b 、L 2c ) Respectively with the capacitorC 1 、C o1 、C o2 、C o3 、C o4 To make the first diodeD 1 Second diodeD 2 Third diodeD 3 Fourth diodeD 4 The switching on and the switching off under the condition of Zero Voltage and Zero Current (ZVZCS) are respectively realized when the converter works, so that the soft switching characteristic of the active device of the converter is realized, the loss of the active device is greatly reduced, and the efficiency of the converter is improved.
The second diodeD 2 A second output capacitorC o2 First winding coupling inductanceL 2a The method comprises the steps of carrying out a first treatment on the surface of the Third diodeD 3 A third output capacitorC o3 Second winding coupling inductanceL 2b The method comprises the steps of carrying out a first treatment on the surface of the Fourth diodeD 4 Fourth output capacitorC o4 Second winding coupling inductanceL 2b The voltage doubling unit (MVC) structure is respectively formed, and the structure solves the defects of single inductance and capacitance boosting technologies through mixed charge and discharge between the coupling inductance and the capacitance, so that the voltages of different units are superposed on the output end, and the high voltage gain of the converter is realized.
The first output capacitorC o1 First diodeD 1 Power switch tubeSThe method comprises the steps of carrying out a first treatment on the surface of the The first capacitorC 1 A first output capacitorC o1 First winding coupling inductanceL 2a Third winding coupling inductanceL 2c First switch tubeD 1 The method comprises the steps of carrying out a first treatment on the surface of the The second diodeD 2 First winding coupling inductanceL 2a A second output capacitorC O2 The method comprises the steps of carrying out a first treatment on the surface of the The third diodeD 3 Second winding coupling inductanceL 2b A third output capacitorC o3 The method comprises the steps of carrying out a first treatment on the surface of the The fourth diodeD 4 Second winding of coupling inductanceL 2b Fourth output capacitorC o4 Respectively form clamping structures which couple three windings to the inductorL 2a 、L 2b AndL 2c the energy generated by the medium leakage inductance is absorbed and output to the load side, so that the voltage peak generated by the leakage inductance is clamped, the stress on the switching device is reduced, and the electromagnetic interference is reduced.
The three-winding coupling inductanceL 2a 、L 2b 、L 2c ) Forms the main energy loop of the converter and provides high-voltage gain, which can be equivalent to the primary side with exciting inductanceL m With leakage inductanceL 1k And the turn ratio isN 1 ：N 2 ：N 3 Is a transformer of the ideal type; the turn ratio can also be expressed as 1:n 1 ：n 2 whereinn 1 =N 2 ：N 1 ，n 2 =N 3 ：N 1 The method comprises the steps of carrying out a first treatment on the surface of the By the turn ratio n thereof 1 、n 2 And power switch tubeSDuty cycle of (2)DSo that it passes through a smaller turns ratio, duty cycleDA larger voltage gain is obtained and a high degree of freedom adjustment of the boost range of the converter is achieved.
The power switch tubeSThe second end can receive a control signal from an external controller to control the on and off of a switching tube of the switch; power switch tubeSAn IGBT may be used, or other power switching transistors such as a mosfet may be used. When power switch tubeSWhen the IGBT is used, the first end, the second end and the third end of the power switch tube S respectively represent the collector, the base and the emitter of the power switch tube S correspondingly; when power switch tubeSWhen MOSEFET is used, power switch tubeSThe first end, the second end and the third end of the first electrode respectively represent a source electrode, a grid electrode and a drain electrode of the first electrode; the external controller can select STM32 series single chip microcomputer, TMS320 series DSP and the like to carry out control signal transmission; in this embodiment, the power switch tubeSAll adopt N channel type MOS tube, receive the control signal of the external controller by its gate, source; the controller is selected as a TMS320F28335DSP control chip; the control mode adopts unipolar PWM control.
The converter in the present invention is described below in connection with an embodimentThe principle is explained in detail. As shown in FIG. 2, the key waveform diagram of each switching tube and inductor in a steady-state working period comprises a power switching tubeSReceived control signal waveform, energy storage inductorL 1 Exciting inductanceL m And equivalent leakage inductanceL 1k Current waveform, power switching tubeSFirst diodeD 1 Second diodeD 2 Third diodeD 3 Fourth diodeD 4 And (3) applying a waveform of voltage and current variation.
In the embodiment, there are 6 operation modes (mode 1-mode 6) in a steady-state working period, in order to simplify analysis, the influence of the leakage inductance of the coupling inductance is ignored in steady-state analysis, the transformer is regarded as an ideal transformer, meanwhile, the loss in the power device and the circuit is not considered, and because the time of the mode 1 and the mode 3 in a steady-state working period is very short, four main operation modes of the mode 2, the mode 4, the mode 5 and the mode 6 are mainly analyzed:
modality 2[t 2 ，t 3 ]: power switch tubeSIn a conductive state, energy storage inductanceL 1 Exciting inductanceL m Respectively storing power from DC inputV g And a first output capacitorC o1 Is a function of the energy of the (c). First capacitorC 1 Excited inductanceL m Third winding coupling inductanceL 2c Is charged. Energy storage inductorL 1 Exciting inductanceL m Upper currenti L1 、i Lm And linearly increases. First winding coupling inductanceL 2a Third winding coupling inductanceL 2c And a first capacitorC 1 A first output capacitorC o1 Resonance, forming Quasi-resonance (Quasi-resonance) circuit structure, and simultaneously coupling leakage inductance of inductorL 1k The existence of the (C) reduces the current variation degree of the switch at the conduction moment, so that the power switch tubeSAt Zero Current (ZCS) start. At this time, the first diodeD 1 Second diodeD 2 And a third secondPolar tubeD 3 Still reverse biased, and fourth diodeD 4 And is turned on in the forward direction due to the energy transfer of the coupled inductor. Thus leakage inductanceL 1k And a fourth diodeD 4 Upper currenti L1k Andi D4 are all increasing positively in the form of a sine wave. Power switching tube at end time of modeSTurn off after resonance of current value decreases, fourth diodeD 4 The switching losses are reduced both when operating at zero voltage start zero current shutdown (ZVZCS) at resonance current, see in particular fig. 3.
First capacitorC 1 Leakage inductanceL 1k The voltages and currents above are:
（1）
（2）
in the method, in the process of the invention,V C1 is a first capacitorC 1 Voltage at deltav C1 (t) Is a first capacitorC 1 The instantaneous value of the voltage change is applied,v C1 (t) Is a first capacitorC 1 The value of the change in the upper voltage over time,t 1 for the time of the end of modality 1,v L1k (t) To couple the time-dependent voltage across the inductor leakage inductance,to couple the time-dependent value of the current on the inductor leakage inductance,i C1 (t) Is a first capacitorC 1 The upper current is varied in value with time,i Co1 (t) For the first output capacitanceC o1 The upper current is varied in value with time,I o is the output current of the DC-DC converter,C 1 is a first capacitorC 1 Is used for the capacitor value of (a),wthe resonance angular frequency is:
（3）
in the method, in the process of the invention,L 1k in order to couple the inductance value of the leakage inductance of the inductor,C 1 is a first capacitorC 1 Is used for the capacitor value of (a),C o1 for the first output capacitanceC o1 Is a capacitance value of (2).
Power switch tubeSThe current above can be expressed as:
（4）
in the method, in the process of the invention,is a power switch tubeSThe value of the change in the upper current over time,I L1 as an average value of the energy storage inductor current,i C1 (t) Is a first capacitorC 1 Upper current time-varying value,/->Is a first capacitorC 1 The instantaneous value of the voltage change is applied,t 1 is the time of the end of modality 1.
Fourth diodeD 4 The upper current is:
（5）
in the method, in the process of the invention,is a fourth diodeD 4 The value of the change in the upper current over time,t 1 for the time of the end of modality 1,coupling an inductance for the second windingL 2b Upper topt 1 The value of the current at the moment in time,/>for the fourth output capacitanceC o4 The voltage across the resistor is applied to the resistor,L 2b coupling an inductance for the second windingL 2b Sensing amount of the upper part.
Mode 4 [ t ] 3 , t 4 ]Power switch tubeSIn the off state, leakage inductanceL 1k Electric currenti L1k The reverse direction starts to increase after the forward direction decreases to zero. Third winding coupling inductanceL 2c And a first capacitorC 1 A second output capacitorC o2 Such that the diodeD 2 Operating at zero voltage start zero current shutdown (ZVZCS). At this time, store in the first capacitorC 1 Energy storage inductorL 1 Exciting inductanceL m The energy in the coil is coupled with inductance through three windingsL 2a 、L 2b 、L 2c ) Transferred to the first output capacitorC o1 A second output capacitorC o2 A third output capacitorC o3 And a loadRThus the current of the energy storage inductori L1 And exciting inductance currenti Lm Start to decrease linearly, energy storage inductanceL 1 Is (1) the current of the (a)i L1 Coupling inductance with third windingL 2c Is (1) the current of the (a)i L2c The current difference value flows through the first diodeD 1 Making it conductive. Third diodeD 3 Due to coupling inductance of the second windingL 2b And a third output capacitorC o3 Upper voltage differenceV L2b -V Co3 Begin conducting, see specifically fig. 4 (a).
First diodeD 1 The current above can be expressed as:
（6）
in the method, in the process of the invention,i D1 (t) Is a first diodeD 1 The value of the change in the upper current over time,t 3 for the time of the end of modality 3,i L1 (t 3 ) For storing energyL 1 Upper topt 3 The value of the current at the moment in time,i L2c (t 3 ) Coupling an inductance for the third windingL 2c Upper topt 3 The value of the current at the moment in time,v Co2 for the second output capacitancev Co2 The voltage across the resistor is applied to the resistor,L 2c coupling an inductance for the third windingL 2c The sensing quantity of the air conditioner is equal to the sensing quantity,L 1 for storing energyL 1 The sensing quantity of the air conditioner is equal to the sensing quantity,V g is a direct current input power supplyV g Is set at the voltage across the terminals.
Mode 5 [ t ] 4 , t 5 ]: power switch tubeSAnd a first diodeD 1 In this mode both are off. Stored in an energy storage inductorL 1 Three-winding coupling inductorL 2a 、L 2b 、L 2c ) And a first capacitorC 1 The energy in the capacitor is commonly a first output capacitorC o1 A second output capacitorC o2 A third output capacitorC o3 And a loadRPower supply, fourth output capacitorC o4 Energy is transferred to the load. Three-winding coupling inductance with energy releaseL 2a 、L 2b 、L 2c ) Upper current decreases, correspondingly, a second diodeD 2 Upper currenti D2 Reduced, see in particular fig. 4 (b).
Second diodeD 2 The current above can be expressed as:
（7）
in the method, in the process of the invention,i D2 (t) Is a second diodeD 2 The value of the change in the upper current over time,t 5 for the time at the end of modality 5,i t2c(5) coupling an inductance for the third windingL 2c Upper topt 5 The value of the current at the moment in time,i tL2a(5) coupling an inductance for a first windingL 2a Upper topt 5 The value of the current at the moment in time,v Co2 for the second output capacitancev Co2 The voltage across the resistor is applied to the resistor,L 2c coupling an inductance for the third windingL 2c The sensing quantity of the air conditioner is equal to the sensing quantity,L 2a coupling an inductance for a first windingL 2a Sensing amount of the upper part.
Mode 6 [ t ] 5 , t 6 ]Power switch tubeSStill in the off state, the second diodeD 2 In an off state after the current reaches 0, a second output capacitorC o2 The discharge is started. During this period, the three-winding coupling inductance leaks inductance currenti L1k And energy storage inductorL 1 Is (1) the current of the (a)i L1 Equal. Due to the quasi-resonant circuit structure, flows through the third diodeD 3 Is brought to resonance in advance to 0, which causes it to switch off under Zero Current (ZCS) conditions, see in particular fig. 4 (c).
The current on diode D3 at this time is:
（8）
in the method, in the process of the invention,i D3 (t) Is a third diodeD 3 The value of the change in the upper current over time,t 6 for the time at the end of the modality 6,i L2b (t 6 ) Coupling an inductance for the second windingL 2b Upper topt 6 The value of the current at the moment in time,v Co3 for a third output capacitanceC o3 The voltage across the resistor is applied to the resistor,L 2b coupling an inductance for the second windingL 2b Sensing amount of the upper part.
After further operation mode analysis, in each operation mode, a first output capacitanceC o1 A second output capacitorC o2 A third output capacitorC o3 And a fourth output capacitorC o4 Some of the charges haveThis helps to reduce ripple of the output voltage, so the converter output voltage ripple is lower.
In the embodiment, the energy storage inductor is operated in the mode of 2 on mode, 4 off on mode, 5 mode and 6 modeL 1 Three-winding coupling inductorL 2a 、L 2b 、L 2c ) The voltage change is subjected to a volt-second balance rule to obtain the output voltage of the converterV o Output gainBIs represented by the expression:
（9）
（10）
from the analysis of the gain of the output voltage, the ratio of two turns of the coupling inductance through three windingsn 1 、n 2 Duty cycle when conducting with power switch tubeDThe factor of gain adjustment is used together, so that the boosting capacity of the converter is enhanced, and the adjustment range of output voltage is enlarged; while the converter has high boost multiple ratio, the duty ratio is highDThe frequency can be lower than 0.5, the occurrence of the limit duty ratio condition is avoided, and the reliability of the converter is improved; when the turns are comparedn 1 =2、n 2 =0.5, duty cycle extractionDWhen=0.5, the output gainBCan be up to 12 times.
In an embodiment, according to the output gainBAnd calculating the voltage stress expression of the power switch tube and the diode:
（11）
wherein,V s is a power switch tubeSThe voltage at the two ends of the capacitor,V D1 、V D2 、V D3 、V D4 respectively are first diodesPipeD 1 Second diodeD 2 Third diodeD 3 Fourth diodeD 4 The voltage across the two terminals of the capacitor,V g as a result of the input dc voltage,V o is the direct current output voltage of the DC-DC converter.
In the embodiment, the first capacitor is used in the working modes of the on-state mode 2, the off-state mode 4, the mode 5 and the mode 6C 1 A first output capacitorC o1 A second output capacitorC o2 A third output capacitorC o3 Fourth output capacitorC o4 And carrying out ampere-second balance rule on the upper current change to obtain a current stress expression of the power switch tube and the diode of the converter:
（12）
wherein,I s respectively, is a power switch tubeSIs used for the current flow of (a),I D1 、I D2 、I D3 、I D4 respectively flow through the first diodeD 1 Second diodeD 2 Third diodeD 3 Fourth diodeD 4 Is used for the current flow of (a),I o is the output current of the DC-DC converter.
From voltage and current stress analysis, it is known that when the single-switch high-gain DC-DC converter integrated with the improved quasi-Z source network related to the invention meets the boost gain at the input and the outputBTest under test conditions at=12, converter turn comparisonn 1 =2、n 2 =0.5, the voltage stress, current stress and gain of each active device are shown in fig. 5 and 6BIs related to the output voltage respectivelyV o And output currentI o Is a reference; at the moment, the voltage stress at two ends of the power device and the current stress flowing through the power device are very small, so that the loss in a loop is reduced, the working safety of a circuit is ensured, and the conversion is reducedElectromagnetic interference of the device.
In the embodiment, the converter prototype is tested under the test of 200W of power design, and the experimental result shows that the input-output conversion efficiency of the converter reaches about 97%, and the converter has higher working efficiency.
According to the theoretical analysis and experimental results, the converter has the boosting capability with high gain and high flexibility, has higher conversion efficiency, reduces the voltage stress on the output capacitor and the switching device by a multi-stage structure, meets the requirements of the purpose, and achieves the expected effect.
In the description of the present application, it should be understood that the terms "center," "longitudinal," "lateral," "front," "rear," "left," "right," "vertical," "horizontal," "top," "bottom," "inner," "outer," and the like indicate orientations or positional relationships based on the orientations or positional relationships shown in the drawings, merely to facilitate description of the present invention and simplify description, and do not indicate or imply that the device or element being referred to must have a specific orientation, be configured and operated in a specific orientation, and thus should not be construed as limiting the protection of the present invention.
The foregoing has shown and described the basic principles and main features of the present invention and the advantages of the present invention. It will be understood by those skilled in the art that the present invention is not limited to the embodiments described above, and that the above embodiments and descriptions are merely illustrative of the principles of the present invention, and various changes and modifications may be made without departing from the spirit and scope of the invention, which is defined in the appended claims. The scope of the invention is defined by the appended claims and equivalents thereof.
Claims (10)
1. A single-switch DC-DC converter based on an improved quasi-Z source network is characterized by comprising a direct-current input power supply and an energy storage inductor L 1 First diode D 1 Second diode D 2 Third diode D 3 Fourth diode D 4 First capacitor C 1 First output capacitor C o1 A second output capacitor C o2 A third output capacitor C o3 Fourth output capacitor C o4 Power switch tube S, load R and first winding coupling inductance L 2a Second winding coupling inductance L 2b Coupling inductance L of third winding 2c ；
Positive electrode of the direct current input power supply and energy storage inductance L 1 The negative pole of the first output capacitor C is connected with the third port of the power switch tube S o1 Is connected to the first end of the load R;
the energy storage inductance L 1 Respectively with the second end of the first diode D 1 Anode of (C), first capacitor C 1 The negative electrode of the power switch tube S is connected with the first port of the power switch tube S;
the second port of the power switch tube S is used for accessing a control signal;
the first capacitor C 1 Is coupled with the third winding by the positive electrode of L 2c Is connected with the homonymous end of the formula (I);
the first diode D 1 Respectively with the first output capacitor C o1 Positive pole of (a) and first winding coupling inductance L 2a Is the same name as the terminal of the second output capacitor C o2 Is connected with the negative electrode of the battery;
the second diode D 2 The anode of (a) is respectively coupled with the third winding to form an inductance L 2c Is a first winding coupling inductance L 2a The cathodes of which are respectively connected with a third diode D 3 Anode of (C), third output capacitance C o3 Is connected with the negative electrode of the second output capacitor C o2 Is connected with the positive electrode of the battery;
the third diode D 3 Respectively with the cathode of the fourth diode D 4 Anode and second winding coupled inductance L 2b Is connected with the homonymous end of the formula (I);
the fourth diode D 4 Cathode of (C) is respectively connected with the fourth output capacitor C o4 The positive electrode of the load R is connected with the second end of the load R;
the third output capacitor C o3 The positive pole of (a) is respectively coupled with the second winding to form an inductance L 2b Different name terminal of (C) and fourth output capacitor C o4 Is connected to the negative electrode of the battery.
2. A single-switch DC-DC converter based on an improved quasi-Z source network as claimed in claim 1, wherein: the power switch tube S also comprises a body diode D s The method comprises the steps of carrying out a first treatment on the surface of the The third port of the power switch tube S and the body diode D s Is connected with the anode of the power switch tube S and the body diode D s Is connected to the cathode of the battery.
3. A single-switch DC-DC converter based on an improved quasi-Z source network as claimed in claim 1, wherein: the first winding is coupled with inductance L 2a Second winding coupling inductance L 2b Coupling inductance L of third winding 2c The leakage inductance is equivalent to L 1K The method comprises the steps of carrying out a first treatment on the surface of the The first winding is coupled with inductance L 2a The upper part is provided with an excitation inductance which is equivalent to the excitation inductance L m 。
4. A single-switch DC-DC converter based on an improved quasi-Z source network as claimed in claim 3, wherein: the first winding is coupled with inductance L 2a Second winding coupling inductance L 2b Coupling inductance L of third winding 2c The winding turns ratio of (2) is 1: n is n 1 ：n 2 Wherein n is 1 ＝N 2 ：N 1 ，n 2 ＝N 3 ：N 1 ，N 1 Coupling an inductance L for the first winding 2a Number of turns, N 2 Coupling an inductance L for the second winding 2b Number of turns, N 3 Coupling an inductance L for the third winding 2c Is a number of turns of (b).
5. The single-switch DC-DC converter of claim 4, wherein the single-switch DC-DC converter is based on an improved quasi-Z source network, wherein: the power switch tube S and the first diode D 1 Second diode D 2 Third diode D 3 Fourth diode D 4 The voltage stress expression of (2) is:
wherein V is s For the voltage at two ends of the power switch tube S, V D1 、V D2 、V D3 、V D4 Respectively a first diode D 1 Second diode D 2 Third diode D 3 Fourth diode D 4 The voltage at two ends, D is the duty ratio of the power switching tube S when being conducted, B is the output gain of the DC-DC converter, V g Is the voltage of two ends of the direct current input power supply, V o Is the direct current output voltage of the DC-DC converter.
6. The single-switch DC-DC converter of claim 4, wherein the single-switch DC-DC converter is based on an improved quasi-Z source network, wherein: flows through the power switch tube S and the first diode D 1 Second diode D 2 Third diode D 3 Fourth diode D 4 The current expression of (2) is:
wherein I is s Respectively, the current flowing through the power switch tube S, B is the output gain of the DC-DC converter, D is the duty ratio of the power switch tube S when being conducted, I D1 、I D2 、I D3 、I D4 Respectively flow through the first diode D 1 Second diode D 2 Third diode D 3 Fourth diode D 4 Current of I o Is the output current of the DC-DC converter.
7. A single-switch DC-DC converter based on an improved quasi-Z source network as claimed in claim 1, wherein: when the power switch tube S uses IGBT, the first end, the second end and the third end of the power switch tube S respectively represent the collector, the base and the emitter of the power switch tube S.
8. A single-switch DC-DC converter based on an improved quasi-Z source network as claimed in claim 1, wherein: when the power switch tube S uses a mosfet, the first end, the second end and the third end of the power switch tube S respectively represent the source, the gate and the drain thereof.
9. A single-switch DC-DC converter based on an improved quasi-Z source network as claimed in claim 1, wherein: the single-switch DC-DC converter further comprises a controller, wherein the controller is connected with the second end of the power switch tube S, and the control mode is unipolar PWM control.
10. A single-switch DC-DC converter based on an improved quasi-Z source network as claimed in claim 9, wherein: the controller is a TMS320F28335DSP control chip.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202410125853.1A CN117674591B (en) | 2024-01-30 | 2024-01-30 | Single-switch DC-DC converter based on improved quasi-Z source network |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202410125853.1A CN117674591B (en) | 2024-01-30 | 2024-01-30 | Single-switch DC-DC converter based on improved quasi-Z source network |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN117674591A CN117674591A (en) | 2024-03-08 |
| CN117674591B true CN117674591B (en) | 2024-04-16 |
Family
ID=90064362
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202410125853.1A Active CN117674591B (en) | 2024-01-30 | 2024-01-30 | Single-switch DC-DC converter based on improved quasi-Z source network |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN117674591B (en) |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101325368A (en) * | 2008-03-25 | 2008-12-17 | 浙江大学 | Alternation parallel voltage-releasing type convertor implemented by three-winding coupling inductance |
| JP2014050143A (en) * | 2012-08-29 | 2014-03-17 | Toyo Electric Mfg Co Ltd | Z-source inverter |
| CN107959429A (en) * | 2017-12-08 | 2018-04-24 | 河海大学文天学院 | A kind of coupling inductance boosting inverter and its control method |
| CN113394975A (en) * | 2021-07-30 | 2021-09-14 | 南京信息工程大学 | High-voltage gain DC-DC direct current converter |
| CN117458861A (en) * | 2023-09-27 | 2024-01-26 | 湖南大学 | Direct-current boost converter applicable to deep open sea wind turbine generator and application method thereof |
-
2024
- 2024-01-30 CN CN202410125853.1A patent/CN117674591B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101325368A (en) * | 2008-03-25 | 2008-12-17 | 浙江大学 | Alternation parallel voltage-releasing type convertor implemented by three-winding coupling inductance |
| JP2014050143A (en) * | 2012-08-29 | 2014-03-17 | Toyo Electric Mfg Co Ltd | Z-source inverter |
| CN107959429A (en) * | 2017-12-08 | 2018-04-24 | 河海大学文天学院 | A kind of coupling inductance boosting inverter and its control method |
| CN113394975A (en) * | 2021-07-30 | 2021-09-14 | 南京信息工程大学 | High-voltage gain DC-DC direct current converter |
| CN117458861A (en) * | 2023-09-27 | 2024-01-26 | 湖南大学 | Direct-current boost converter applicable to deep open sea wind turbine generator and application method thereof |
Also Published As
| Publication number | Publication date |
|---|---|
| CN117674591A (en) | 2024-03-08 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN108448913B (en) | Single-stage isolated AC-DC converter based on staggered parallel bridgeless PFC circuit and LLC resonance | |
| US11496054B2 (en) | High-gain quasi-resonant DC-DC converter based on voltage doubling rectifier circuit | |
| CN101527520B (en) | Single-stage single-phase AC-DC convertor based on LLC series resonance | |
| Zhao et al. | A novel multiresonant DC–DC converter with wide output-voltage range | |
| CN110601525B (en) | Integrated vehicle-mounted charging conversion system of new energy automobile | |
| CN111525809B (en) | High-frequency hybrid direct-current converter with adjustable output voltage | |
| CN113541500A (en) | Isolated semi-accurate Z source direct current boost converter | |
| CN114285286A (en) | Single-stage zero-current switch full-bridge boost direct current converter and control method thereof | |
| TWI238590B (en) | High-efficiency DC/DC converter with high voltage gain | |
| CN219287377U (en) | Bidirectional DC conversion circuit and corresponding device | |
| CN116365878A (en) | High-boost soft-switching direct-current converter applied to direct-current micro-grid system | |
| CN108599560B (en) | Multi-bootstrap cascade DC-DC converter with two-capacitor clamping for photovoltaic system | |
| CN117674591B (en) | Single-switch DC-DC converter based on improved quasi-Z source network | |
| CN108429452B (en) | Quadratic multi-bootstrap DC-DC converter for photovoltaic system | |
| CN216774624U (en) | High-voltage gain soft switching DC-DC converter | |
| CN113410990B (en) | High-efficiency high-gain quasi-Z-source soft switching DC-DC converter | |
| CN108736707A (en) | A kind of BOOST converter with switched inductors structure | |
| CN113783427A (en) | Extensible non-isolated high step-up ratio resonant DC-DC converter | |
| CN111682777B (en) | Secondary parallel LCD forward converter capable of avoiding reverse charging of energy storage capacitor | |
| Deng et al. | Modified topology and PWM modulation for bidirectional LLC-DCX converter with center-tapped transformer | |
| CN108448892B (en) | Quadratic form is many times presses unit DC-DC converter for photovoltaic system | |
| CN216819707U (en) | High-gain DC/DC converter | |
| CN215871196U (en) | Direct current-direct current DCDC converter and vehicle | |
| CN215010050U (en) | Y-source coupling inductance high-boost DC-DC converter | |
| CN117767739B (en) | Mixed-mode non-isolated DC converter and control method thereof |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant |