CN111682777B - A Secondary Parallel LCD Forward Converter Can Avoid Reverse Charging of Energy Storage Capacitor - Google Patents
A Secondary Parallel LCD Forward Converter Can Avoid Reverse Charging of Energy Storage Capacitor Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
- H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
- H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
- H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33523—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
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- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0038—Circuits or arrangements for suppressing, e.g. by masking incorrect turn-on or turn-off signals, e.g. due to current spikes in current mode control
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
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- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0051—Diode reverse recovery losses
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
Description
技术领域technical field
本发明属于开关电源技术领域,具体涉及一种可避免储能电容反向充电的副边并联LCD正激变换器。The invention belongs to the technical field of switching power supplies, and in particular relates to a secondary parallel LCD forward converter capable of avoiding reverse charging of an energy storage capacitor.
背景技术Background technique
在众多的隔离型开关电源变换拓扑中,相对于反激变换器,正激变换器的功率大小并不受限于变压器储存能量的能力;相对于半桥、全桥变换器,正激变换器而言,其所用的元器件更少,电路更简单,成本更低廉,可靠性更高。因此,正激变换器电路因其结构相对简单、成本较低、输入输出隔离、工作可靠性高等诸多优点,更适合应用在中小功率电能变换场合,并受到业界高度关注。In many isolated switching power supply conversion topologies, compared with the flyback converter, the power of the forward converter is not limited by the ability of the transformer to store energy; compared with the half-bridge and full-bridge converters, the forward converter As far as it is concerned, it uses fewer components, simpler circuits, lower cost, and higher reliability. Therefore, due to its relatively simple structure, low cost, input and output isolation, and high operational reliability, the forward converter circuit is more suitable for applications in small and medium power conversion applications, and has received high attention from the industry.
但对于单管正激变换器而言,因为其工作在正向激磁状态下,其高频变压器磁芯单向磁化,本身没有磁复位功能,致使其极有可能引起磁芯饱和等问题。磁饱和的结果将导致流过开关管的电流猛增,甚至损坏开关管,在很大程度上限制了正激变换器的推广,所以必须添加专门的磁复位电路或者能量转移电路来避免磁芯饱和。But for the single-transistor forward converter, because it works in the forward excitation state, its high-frequency transformer core is unidirectionally magnetized, and it has no magnetic reset function, so it is very likely to cause problems such as core saturation. The result of magnetic saturation will lead to a sharp increase in the current flowing through the switch tube, and even damage the switch tube, which limits the promotion of the forward converter to a large extent, so a special magnetic reset circuit or energy transfer circuit must be added to prevent the magnetic core from being damaged. saturation.
磁复位电路的主要工作机理是在每个周期的开关关断时间内将励磁能量进行转移,可以消耗在其他器件上或者返回到输入电源或传输到负载端。现有的正激变换器所采用的磁复位电路种类较多,大致分为三种:The main working mechanism of the magnetic reset circuit is to transfer the excitation energy during the switch off time of each cycle, which can be consumed on other devices or returned to the input power supply or transmitted to the load terminal. There are many types of magnetic reset circuits used in existing forward converters, which can be roughly divided into three types:
第一是在输入端接入复位绕组,使能量返回输入电源;The first is to connect the reset winding at the input end to return the energy to the input power supply;
第二是在变压器原边侧连接RCD、LCD等复位电路,使能量消耗掉或者返回到输入端;The second is to connect RCD, LCD and other reset circuits on the primary side of the transformer, so that the energy is consumed or returned to the input terminal;
第三是在副边采取复位措施,可将能量转移到输出端。The third is to take reset measures on the secondary side, which can transfer energy to the output.
但是,传统的RCD钳位电路比较简单,其不足是将励磁能量消耗在箝位电阻中,使系统的整体效率难以提高;可采用有源钳位技术实现磁复位,其是一种性能优良的方法,但其增加了变换器电路的复杂性、设计难度与成本;而磁复位绕组复位方法技术成熟可靠,励磁能量可返回到输入电源中,但是磁复位绕组增加了变压器结构的复杂度,并增加了功率开关管的电压应力。However, the traditional RCD clamping circuit is relatively simple, and its disadvantage is that the excitation energy is consumed in the clamping resistance, which makes it difficult to improve the overall efficiency of the system; active clamping technology can be used to achieve magnetic reset, which is an excellent performance method, but it increases the complexity, design difficulty and cost of the converter circuit; while the magnetic reset winding reset method is mature and reliable, and the excitation energy can be returned to the input power supply, but the magnetic reset winding increases the complexity of the transformer structure, and Increase the voltage stress of the power switch tube.
现有的副边复位要么需要增加复位绕组或使电路复杂,但是增加变压器或电路的设计和制造难度及成本;要么为了实现能量转移需要设置较多的二极管,但会增加了电路损耗;要么会影响正激电感的工作模式或其它电气性能指标,不利于大功率传输。The existing secondary side reset either needs to increase the reset winding or make the circuit complex, but increases the difficulty and cost of the design and manufacture of the transformer or circuit; or needs to set more diodes to achieve energy transfer, but will increase the circuit loss; or will It affects the working mode or other electrical performance indicators of the forward inductor, which is not conducive to high-power transmission.
因此,为使正激变换器得到进一步推广应用,解决其磁复位问题,提升其综合性能,并针对其他复位方式存在的缺点,研究新的磁复位方式是需要不断探讨的课题。Therefore, in order to further popularize and apply the forward converter, solve its magnetic reset problem, improve its overall performance, and address the shortcomings of other reset methods, researching new magnetic reset methods is a topic that needs to be continuously discussed.
发明内容Contents of the invention
本发明所要解决的技术问题在于针对上述现有技术中的不足,提供一种可避免储能电容反向充电的副边并联LCD正激变换器,解决现有磁复位电路励磁能量利用率低、电路组成复杂、损耗大、效率低等问题。The technical problem to be solved by the present invention is to provide a secondary parallel LCD forward converter that can avoid reverse charging of the energy storage capacitor in view of the above-mentioned deficiencies in the prior art, so as to solve the problem of low excitation energy utilization rate of the existing magnetic reset circuit The circuit composition is complex, the loss is large, and the efficiency is low.
为解决上述技术问题,本发明采用的技术方案是:提供一种可避免储能电容反向充电的副边并联LCD正激变换器,其特征在于:包括正激变换器主电路(1),以及与正激变换器主电路(1)连接的能量转移与传输电路(2);其中,所述正激变换器主电路(1)包括高频变压器T、开关管S、二极管D1、二极管D2、电感L1和电容C1,所述高频变压器T原边的同名端为正激变换器主电路(1)的正极电压输入端IN+且与外部电源的正极输出端连接,所述高频变压器T原边的异名端与开关管S的漏极连接,所述开关管S的源极为正激变换器主电路(1)的负极电压输入端IN-且与外部电源的负极输出端连接,所述开关管S的栅极与外部控制器的输出端连接,所述高频变压器T副边的同名端与二极管D1的阳极连接,所述二极管D1的阴极与二极管D2的阴极和电感L1的一端连接,所述电感L1的另一端与电容C1的一端连接且为正激变换器主电路(1)的正极电压输出端OUT+,所述高频变压器T副边的异名端与二极管D2的阳极和电容C1的另一端连接且为正激变换器主电路(1)的负极电压输出端OUT-,所述正激变换器主电路(1)的负极电压输出端OUT-接地;所述能量转移与传输电路(2)包括二极管D3和电容C2,所述二极管D3的阳极与二极管D2的阳极连接,所述二极管D3的阴极与电容C2的第二端连接,所述电容C2的第一端与二极管D1的阳极连接;所述能量转移与传输电路(2)包括二极管D3、电容C2、电感L2和二极管D4,所述二极管D3的阳极与二极管D2的阳极连接,所述二极管D3的阴极与电容C2的第二端连接,所述电容C2的第一端与二极管D1的阳极连接,所述电感L2的一端与二极管D3的阴极连接,其另一端与正激变换器主电路(1)的正极电压输出端OUT+连接,所述二极管D4的阳极与能量转移与传输电路(2)的电容C2的第一端连接,其阴极电容C2的第二端连接。In order to solve the above-mentioned technical problems, the technical solution adopted in the present invention is: provide a kind of secondary parallel LCD forward converter that can avoid the reverse charge of energy storage capacitor, it is characterized in that: comprise forward converter main circuit (1), And an energy transfer and transmission circuit (2) connected to the main circuit of the forward converter (1); wherein, the main circuit of the forward converter (1) includes a high-frequency transformer T, a switch tube S, a diode D1, and a diode D2 , inductance L1 and capacitor C1, the same-named end of the primary side of the high-frequency transformer T is the positive voltage input terminal IN+ of the main circuit of the forward converter (1) and is connected with the positive output terminal of the external power supply, and the high-frequency transformer T The opposite end of the primary side is connected to the drain of the switch tube S, the source of the switch tube S is the negative voltage input terminal IN- of the main circuit of the forward converter (1) and is connected to the negative output terminal of the external power supply, so The gate of the switching tube S is connected to the output terminal of the external controller, the same-named terminal of the secondary side of the high-frequency transformer T is connected to the anode of the diode D1, and the cathode of the diode D1 is connected to the cathode of the diode D2 and one end of the inductor L1 The other end of the inductance L1 is connected to one end of the capacitor C1 and is the positive voltage output end OUT+ of the main circuit (1) of the forward converter, and the opposite end of the secondary side of the high-frequency transformer T is connected to the anode of the diode D2 It is connected to the other end of the capacitor C1 and is the negative voltage output terminal OUT- of the main circuit of the forward converter (1), and the negative voltage output terminal OUT- of the main circuit of the forward converter (1) is grounded; the energy transfer The transmission circuit (2) includes a diode D3 and a capacitor C2, the anode of the diode D3 is connected to the anode of the diode D2, the cathode of the diode D3 is connected to the second end of the capacitor C2, and the first end of the capacitor C2 is connected to the second end of the capacitor C2. The anode of the diode D1 is connected; the energy transfer and transmission circuit (2) includes a diode D3, a capacitor C2, an inductor L2 and a diode D4, the anode of the diode D3 is connected to the anode of the diode D2, and the cathode of the diode D3 is connected to the capacitor The second end of C2 is connected, the first end of the capacitor C2 is connected to the anode of the diode D1, one end of the inductor L2 is connected to the cathode of the diode D3, and the other end is connected to the positive pole of the forward converter main circuit (1). The voltage output terminal OUT+ is connected, the anode of the diode D4 is connected to the first end of the capacitor C2 of the energy transfer and transmission circuit (2), and the second end of the cathode capacitor C2 is connected.
其中,较佳方案是:所述二极管D1、D2为快恢复二极管。Wherein, a preferred solution is: the diodes D1 and D2 are fast recovery diodes.
其中,较佳方案是:所述开关管S为全控型功率半导体器件。Among them, a preferred solution is: the switch tube S is a full-control power semiconductor device.
其中,较佳方案是:所述电容C2根据第一选取步骤选取;其中,所述第一选取步骤的步骤包括:Among them, the preferred solution is: the capacitor C2 is selected according to the first selection step; wherein, the steps of the first selection step include:
步骤101、选取励磁储能电容C2的容值C2,;Step 101, selecting the capacitance C 2 of the excitation energy storage capacitor C2;
步骤102、并计算电容C2的耐压值VC2,Ton;Step 102, and calculate the withstand voltage V C2,Ton of the capacitor C2;
步骤103、选取容值为C2且耐压值大于VC2,Ton的电容作为电容C2。Step 103: Select a capacitor with a capacitance value of C2 and a withstand voltage greater than V C2,Ton as the capacitor C2.
其中,较佳方案是:所述电感L2根据第二选取步骤选取;其中,所述第二选取步骤的步骤包括:Wherein, the preferred solution is: the inductance L2 is selected according to the second selection step; wherein, the steps of the second selection step include:
步骤201、获取整个周期内,流过电感L2电流变化量的平均值,以及获取电感L1的平均电流;Step 201, obtaining the average value of the current variation flowing through the inductor L2 during the entire period, and obtaining the average current of the inductor L1;
步骤202、确定电感L2的电感值L2的取值范围;Step 202, determine the value range of the inductance value L2 of the inductance L2 ;
步骤203、结合步骤201和步骤202,确定流过电感L2的最大电流IL2,max。Step 203, combining steps 201 and 202, determine the maximum current I L2,max flowing through the inductor L2.
其中,较佳方案是:所述二极管D3、二极管D4根据第三选取步骤选取;其中,所述第三选取步骤的步骤包括:Wherein, the preferred solution is: the diode D3 and the diode D4 are selected according to the third selection step; wherein, the steps of the third selection step include:
步骤301、计算流过二极管D3的最大电流ID3,max;Step 301, calculating the maximum current I D3,max flowing through the diode D3;
步骤302、计算二极管D3的最大耐压VD3,max;Step 302, calculating the maximum withstand voltage V D3,max of the diode D3;
步骤303、根据流过二极管D3的最大电流ID3,max和二极管D3的耐压值VD3,max选择二极管D3;Step 303, select the diode D3 according to the maximum current I D3,max flowing through the diode D3 and the withstand voltage V D3,max of the diode D3;
步骤304、计算流过二极管D4的最大电流ID4,max;Step 304, calculating the maximum current I D4,max flowing through the diode D4;
步骤305、计算二极管D4的最大耐压值VD4,max;Step 305, calculating the maximum withstand voltage V D4,max of the diode D4;
步骤306、根据流过二极管D4的最大电流ID4,max和二极管D4的耐压值VD4,max选择二极管D4。Step 306, select the diode D4 according to the maximum current I D4,max flowing through the diode D4 and the withstand voltage V D4,max of the diode D4.
本发明与现有技术相比具有以下优点:Compared with the prior art, the present invention has the following advantages:
1、本发明通过可避免储能电容反向充电的副边并联LCD正激变换器,实现励磁能量转移到负载侧,提升了变换器的整体效率。1. The present invention realizes the transfer of excitation energy to the load side through the secondary parallel LCD forward converter that can avoid reverse charging of the energy storage capacitor, and improves the overall efficiency of the converter.
2、本发明设计实现的副边并联LCD正激变换器,工作稳定性和可靠性高,电路简单,不需要复杂控制方案,具有较广的推广价值。2. The secondary side parallel LCD forward converter designed and realized by the present invention has high working stability and reliability, simple circuit, no complicated control scheme, and has wide popularization value.
3、本发明设计的副边LCD磁复位正激变换器电路,相对辅助绕组复位,降低了变压器的设计难度。3. The secondary LCD magnetic reset forward converter circuit designed in the present invention reduces the design difficulty of the transformer compared with the auxiliary winding reset.
4、本发明能量转移与传输电路的电容上并联有单向导电二极管,可防止C2反向充电,减少无功,进一步提高效率。4. The capacitance of the energy transfer and transmission circuit of the present invention is connected in parallel with a unidirectional conduction diode, which can prevent reverse charging of C2, reduce reactive power, and further improve efficiency.
5、可消除二极管D4的反向恢复问题,降低二极管损耗。5. The reverse recovery problem of the diode D4 can be eliminated, and the loss of the diode can be reduced.
6、电感L2可工作于CCM,适合大功率传输。6. Inductor L2 can work in CCM, suitable for high power transmission.
7、本发明的能量转移与传输电路,还能传输正激能量,可分散功率传输,进一步提高可靠性,较适合大功率应用。7. The energy transfer and transmission circuit of the present invention can also transmit forward energy, can disperse power transmission, further improves reliability, and is more suitable for high-power applications.
8、在开关电源中使用本发明后,开关电源的工作安全性和可靠性更高,能量转移与传输电路能够使能量利用率提高,可广泛应用于计算机、医疗通信、工业控制、航天设备等领域,因此本发明有较高的推广应用价值;8. After using the present invention in the switching power supply, the working safety and reliability of the switching power supply are higher, and the energy transfer and transmission circuit can improve the energy utilization rate, and can be widely used in computers, medical communications, industrial control, aerospace equipment, etc. field, so the present invention has higher application value;
综上所述,本发明电路结构简单,实现方便且成本低,工作模式简单,工作稳定性和可靠性高,使用寿命长,功耗低,变压器利用率高,能量传输效率高,能够提高开关电源的工作安全性和可靠性,实用性强,推广应用价值高。In summary, the circuit structure of the present invention is simple, easy to implement and low in cost, simple in working mode, high in working stability and reliability, long in service life, low in power consumption, high in transformer utilization, high in energy transmission efficiency, and capable of improving switching The working safety and reliability of the power supply are strong in practicability and high in popularization and application value.
下面通过附图和实施例,对本发明的技术方案做进一步的详细描述。The technical solutions of the present invention will be described in further detail below with reference to the accompanying drawings and embodiments.
附图说明Description of drawings
图1为本发明可避免储能电容反向充电的副边并联LCD正激变换器的电路原理图。FIG. 1 is a schematic circuit diagram of a secondary parallel LCD forward converter capable of avoiding reverse charging of an energy storage capacitor according to the present invention.
附图标记说明:Explanation of reference signs:
1—正激变换器主电路;2—能量转移与传输电路。1—Forward converter main circuit; 2—Energy transfer and transmission circuit.
具体实施方式detailed description
如图1所示,本发明的可避免储能电容反向充电的副边并联LCD正激变换器,包括正激变换器主电路1、以及与正激变换器主电路1连接的能量转移与传输电路2;其中,所述正激变换器主电路1包括高频变压器T、开关管S、二极管D1、二极管D2、电感L1和电容C1,所述高频变压器T原边的同名端为正激变换器主电路1的正极电压输入端IN+且与外部电源的正极输出端连接,所述高频变压器T原边的异名端与开关管S的漏极连接,所述开关管S的源极为正激变换器主电路1的负极电压输入端IN-且与外部电源的负极输出端连接,所述开关管S的栅极与外部控制器的输出端连接,所述高频变压器T副边的同名端与二极管D1的阳极连接,所述二极管D1的阴极与二极管D2的阴极和电感L1的一端连接,所述电感L1的另一端与电容C1的一端连接且为正激变换器主电路1的正极电压输出端OUT+,所述高频变压器T副边的异名端与二极管D2的阳极和电容C1的另一端连接且为正激变换器主电路1的负极电压输出端OUT-,所述正激变换器主电路1的负极电压输出端OUT-接地;所述能量转移与传输电路2包括二极管D3和电容C2,所述二极管D3的阳极与二极管D2的阳极连接,所述二极管D3的阴极与电容C2的第二端连接,所述电容C2的第一端与二极管D1的阳极连接;所述能量转移与传输电路2包括二极管D3、电容C2、电感L2和二极管D4,所述二极管D3的阳极与二极管D2的阳极连接,所述二极管D3的阴极与电容C2的第二端连接,所述电容C2的第一端与二极管D1的阳极连接,所述电感L2的一端与二极管D3的阴极连接,其另一端与正激变换器主电路1的正极电压输出端OUT+连接,所述二极管D4的阳极与能量转移与传输电路2的电容C2的第一端连接,其阴极电容C2的第二端连接。As shown in Figure 1, the secondary side parallel LCD forward converter that can avoid the reverse charge of the energy storage capacitor of the present invention includes the
具体实施时,负载RL接在正激变换器主电路1的正极电压输出端OUT+与负极电压输出端OUT-之间。所述正激变换器主电路1中,电感L1和电容C1均用于滤波。During specific implementation, the load RL is connected between the positive voltage output terminal OUT+ and the negative voltage output terminal OUT- of the forward converter
本实施例中,所述二极管D1为整流二极管,所述二极管D2为快恢复二极管。二极管D2用于续流。In this embodiment, the diode D1 is a rectifier diode, and the diode D2 is a fast recovery diode. Diode D2 is used for freewheeling.
本实施例中,所述开关管S为NMOS开关管。In this embodiment, the switch tube S is an NMOS switch tube.
本实施例的工作原理为:The working principle of this embodiment is:
在对本实施例的工作原理进行分析前,假设正激电感L1工作于DCM,辅助电感L2及变压器副边电感Lw2工作于CCM。下面分成开关管关断期间和导通期间来分析本实施例的工作原理。为了便于介绍原理,约定:对于C2,假定其电压左负右正为正向电压,左正右负为反向电压。Before analyzing the working principle of this embodiment, it is assumed that the forward inductor L1 works in DCM, and the auxiliary inductor L2 and transformer secondary inductor Lw2 work in CCM. The working principle of this embodiment is analyzed below by dividing the switching tube into the off period and the on period. In order to facilitate the introduction of the principle, it is agreed that for C2, it is assumed that its voltage is negative on the left and positive on the right as a positive voltage, and positive on the left and negative on the right is a reverse voltage.
第一、开关管S导通期间的工作原理:First, the working principle during the conduction period of the switch tube S:
假设开关导通时刻前,C2正向电压为最大值,Lw2和L2电流下降至最小值,电感L1电流维持为零。D3导通,D1、D2、D4关断。Assuming that before the switch is turned on, the forward voltage of C2 reaches the maximum value, the current of Lw2 and L2 drops to the minimum value, and the current of the inductor L1 remains zero. D3 is turned on, and D1, D2, and D4 are turned off.
第一阶段:D4关断,C2释放正向储能The first stage: D4 is turned off, and C2 releases positive energy storage
开关管导通后,输入电压Vi施加在变压器原边绕组两端,耦合到二次绕组w2的电压上正下负,D1导通,正激能量经过两条支路向负载传输,其一,经过D1、L1传输到负载,L1电流线性上升。其二,经过C2、D4、L2向负载转移能量,C2正向储能从最大值开始释放,L2电流曲线上升,直至C2正向电压下降为零,此阶段结束。此阶段中,D2、D3、D4仍保持截止。After the switch tube is turned on, the input voltage Vi is applied to both ends of the primary winding of the transformer, and the voltage coupled to the secondary winding w2 is positive and negative, D1 is turned on, and the forward energy is transmitted to the load through two branches. D1 and L1 are transmitted to the load, and the current of L1 rises linearly. Second, after transferring energy to the load through C2, D4, and L2, the forward energy storage of C2 is released from the maximum value, and the current curve of L2 rises until the forward voltage of C2 drops to zero, and this stage ends. In this stage, D2, D3, and D4 are still cut off.
第二阶段:D4导通,经D4、L2向负载转移能量The second stage: D4 is turned on, and energy is transferred to the load through D4 and L2
C2正向电压下降为零后,D4自然导通,C2被短路,通过D4、L2向负载传输能量,此时L2电流保持线性上升。与此同时,D1仍维持导通,L1电流继续线性上升,直至下一个开关关断周期到来,L1、L2电流均达到最大值,此过程结束。此阶段,实现D4零电压导通。After the forward voltage of C2 drops to zero, D4 is naturally turned on, C2 is short-circuited, and energy is transmitted to the load through D4 and L2. At this time, the current of L2 keeps increasing linearly. At the same time, D1 remains on, and the current of L1 continues to rise linearly until the next switch off cycle arrives, and the currents of L1 and L2 both reach the maximum value, and this process ends. At this stage, D4 is turned on with zero voltage.
第二、开关管S关断期间的工作原理:Second, the working principle when the switch tube S is turned off:
第一阶段:L1、L2同时续流向负载提供能量The first stage: L1 and L2 continue to provide energy to the load at the same time
开关管S关断后,D3导通,副边绕组经D3给C2正向储能,C2两端电压从零开始正向增加。与此同时,电感L2经过D3续流,电感L2电流线性下降。在此过程中,D2导通,L1经过D2续流向负载提供能量,电感L1电流线性下降,直至L1电流下降为零,此阶段结束。After the switch tube S is turned off, D3 is turned on, and the secondary winding stores positive energy for C2 through D3, and the voltage at both ends of C2 increases positively from zero. At the same time, the inductor L2 freewheels through D3, and the current of the inductor L2 decreases linearly. During this process, D2 is turned on, L1 provides energy to the load through continuous flow through D2, and the current of inductor L1 decreases linearly until the current of L1 drops to zero, and this phase ends.
第二阶段:仅L2续流向负载提供能量The second stage: only L2 freewheeling provides energy to the load
电感L1电流下降为零后,D2截止,D3维持导通,C2继续储存励磁能量,C2正向电压逐渐增大,耦合到副边绕组的电流缓慢下降。同时,电感L2继续通过D3续流。直至下一个开关导通周期到来,L2电流及耦合到副边绕组的电流均下降至最小值,C2电压达到最大值,此阶段结束。After the current of inductor L1 drops to zero, D2 is cut off, D3 remains on, C2 continues to store excitation energy, the forward voltage of C2 gradually increases, and the current coupled to the secondary winding decreases slowly. At the same time, inductor L2 continues to freewheel through D3. Until the next switch conduction period arrives, the L2 current and the current coupled to the secondary winding both drop to the minimum value, and the C2 voltage reaches the maximum value, and this phase ends.
在本实施例中,所述电容C2根据第一选取步骤选取;其中,所述第一选取步骤的步骤包括:In this embodiment, the capacitor C2 is selected according to the first selection step; wherein, the steps in the first selection step include:
步骤101、根据公式选取励磁储能电容C2的容值C2;Step 101, according to the formula Select the capacitance C 2 of the excitation energy storage capacitor C2;
步骤102、根据公式(A1)计算电容C2的耐压值VC2,Ton;Step 102, calculate the withstand voltage V C2,Ton of the capacitor C2 according to the formula (A1);
其中,d为开关管S的占空比,n为高频变压器T的一次绕组与二次绕组的匝数比,Lm为高频变压器T的一次绕组的励磁电感量,f为正激变换器主电路1的工作频率,λ一般取0.8≤λ≤1,励磁电感量Lm在一个周期内最大励磁电流为ILm,max,其最小励磁电流为ILm,min,具体公式是:Among them, d is the duty cycle of the switch tube S, n is the turns ratio of the primary winding of the high frequency transformer T to the secondary winding, L m is the excitation inductance of the primary winding of the high frequency transformer T, and f is the forward conversion The operating frequency of the
其中,Vi为正激变换器主电路1输入电压;Among them, V i is the input voltage of the
步骤103、选取容值为C2且耐压值大于VC2,Ton的电容作为电容C2。Step 103: Select a capacitor with a capacitance value of C2 and a withstand voltage greater than V C2,Ton as the capacitor C2.
在本实施例中,所述电感L2根据第二选取步骤选取;其中,所述第二选取步骤的步骤包括:In this embodiment, the inductance L2 is selected according to the second selection step; wherein, the steps of the second selection step include:
步骤201、根据公式(A8)和公式(A9)确定电感L2的电感值L2的取值范围;Step 201, determine the value range of the inductance value L2 of the inductance L2 according to formula (A8) and formula (A9);
其中,Vo为正激变换器主电路1的输出电压;Among them, V o is the output voltage of the
步骤202、根据公式(A10)确定流过电感L2的最大电流IL2,max;Step 202, determine the maximum current I L2,max flowing through the inductor L2 according to the formula (A10);
其中,电容C2两端电压下降为零的时间为Among them, the time for the voltage across the capacitor C2 to drop to zero is
电感L2在电容C2两端电压尚未降到零之前,电感L2电流表达式为Before the voltage across the capacitor C2 drops to zero in the inductor L2, the current expression of the inductor L2 is
整个周期内,流过电感L2电流变化量的平均值为In the whole cycle, the average value of the current variation flowing through the inductor L2 is
电感L1的平均电流为The average current of inductor L1 is
在本实施例中,所述二极管D3、二极管D4根据第三选取步骤选取;其中,所述第二选取步骤的步骤包括:In this embodiment, the diode D3 and the diode D4 are selected according to the third selection step; wherein, the steps of the second selection step include:
步骤301、根据公式(A15)计算流过二极管D3的最大电流ID3,max Step 301, calculate the maximum current I D3,max flowing through the diode D3 according to the formula (A15)
其中,IL1,max为流过高频变压器T的一次绕组的最大电流,IL2为流过电感L2的电流;Among them, I L1,max is the maximum current flowing through the primary winding of the high-frequency transformer T, and I L2 is the current flowing through the inductor L2;
步骤302、根据公式(A16)计算二极管D3的最大耐压VD3,max Step 302, calculate the maximum withstand voltage V D3,max of the diode D3 according to the formula (A16)
步骤303、根据流过二极管D3的最大电流ID3,max和二极管D3的耐压值VD3,max选择二极管D3。Step 303, select the diode D3 according to the maximum current I D3,max flowing through the diode D3 and the withstand voltage V D3,max of the diode D3.
步骤304、根据公式(A17)计算流过二极管D4的最大电流ID4,max;Step 304, calculate the maximum current I D4,max flowing through the diode D4 according to the formula (A17);
步骤305、根据公式(A18)计算二极管D4的最大耐压值VD4,max;Step 305, calculate the maximum withstand voltage value V D4,max of the diode D4 according to the formula (A18);
步骤303、根据流过二极管D4的最大电流ID4,max和二极管D4的耐压值VD4,max选择二极管D4。Step 303, select the diode D4 according to the maximum current I D4,max flowing through the diode D4 and the withstand voltage V D4,max of the diode D4.
当然,上述描述只是为了说明本发明技术方案的可行性,所列举的其中一种工作模式的原理及其对应的公式,但并非唯一且限定的描述,仅作为参考使用。Of course, the above description is only to illustrate the feasibility of the technical solution of the present invention, and the principle of one of the working modes and its corresponding formula are listed, but it is not the only and limited description, and is only used as a reference.
应当特别说明的是,以上实施例仅用以说明本发明的技术方案,而非对其限制,对本领域技术人员来说,可以对上述实施例所记载的技术方案进行修改,或者对其中部分技术特征进行等同替换;而所有这些修改和替换,都应属于本发明所附权利要求的保护范围。It should be noted that the above embodiments are only used to illustrate the technical solutions of the present invention, rather than to limit them. Those skilled in the art can modify the technical solutions described in the above embodiments, or modify some of the technical solutions. Features are equivalently replaced; and all these modifications and replacements should belong to the protection scope of the appended claims of the present invention.
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Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US6333861B1 (en) * | 2000-06-06 | 2001-12-25 | Astec International Limited | Low loss snubber and transformer reset circuit for forward converters |
CN102497106A (en) * | 2011-12-05 | 2012-06-13 | 北京新雷能科技股份有限公司 | Single-end forward power inverter |
CN105703627A (en) * | 2016-05-03 | 2016-06-22 | 西安科技大学 | Design method of self-resetting forward conversion circuit with single winding on the secondary side |
JP2018121390A (en) * | 2017-01-23 | 2018-08-02 | Ntn株式会社 | Switching power supply |
WO2018216401A1 (en) * | 2017-05-22 | 2018-11-29 | Ntn株式会社 | Isolated switching power supply |
Family Cites Families (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS596584B2 (en) * | 1979-09-12 | 1984-02-13 | 日本電信電話株式会社 | Single stone converter |
US6947297B2 (en) * | 2003-10-04 | 2005-09-20 | Delta Electronics, Inc. | Active resonant snubber for DC-DC converter |
-
2020
- 2020-06-02 CN CN202010490672.0A patent/CN111682777B/en active Active
- 2020-08-19 AU AU2020220124A patent/AU2020220124B1/en not_active Ceased
Patent Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US6333861B1 (en) * | 2000-06-06 | 2001-12-25 | Astec International Limited | Low loss snubber and transformer reset circuit for forward converters |
CN102497106A (en) * | 2011-12-05 | 2012-06-13 | 北京新雷能科技股份有限公司 | Single-end forward power inverter |
CN105703627A (en) * | 2016-05-03 | 2016-06-22 | 西安科技大学 | Design method of self-resetting forward conversion circuit with single winding on the secondary side |
JP2018121390A (en) * | 2017-01-23 | 2018-08-02 | Ntn株式会社 | Switching power supply |
WO2018216401A1 (en) * | 2017-05-22 | 2018-11-29 | Ntn株式会社 | Isolated switching power supply |
Non-Patent Citations (2)
Title |
---|
A High-Quality Rectifier Based on the Forward Topology With Secondary-Side Resonant Reset;Giorgio Spiazzi;《IEEE Transactions on Power Electronics》;20030531;第18卷(第3期);第725-732页 * |
一种新型谐振磁复位的单端正激变换器设计;张涌萍 等;《科学技术与工程》;20130228;第13卷(第6期);第1626-1629页 * |
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