CN117081360A - Voltage regulation control method of full-bridge inverter circuit - Google Patents
Voltage regulation control method of full-bridge inverter circuit Download PDFInfo
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/083—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the ignition at the zero crossing of the voltage or the current
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
- H02M7/53873—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current with digital control
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Abstract
A voltage regulation control method of a full-bridge inverter circuit belongs to the technical field of full-bridge inverter circuit control. The invention aims at solving the problem that the ZVS and the low reactive component cannot be compatible by adopting phase shift control in the existing full-bridge inverter circuit. Comprising the following steps: the duty ratio of a bridge arm driving signal of the full-bridge inverter circuit is 50%; the driving signal of the other bridge arm is synchronous with the driving signal of one bridge arm, and the duty ratio of the driving signal of the other bridge arm is regulated to be changed between 0 and 50 percent according to the ratio of the expected output alternating-current fundamental wave voltage and the direct-current input voltage, so that all switching tubes of the full-bridge inverter circuit realize zero-voltage switching under the low-inductive reactive power condition; the ratio of the output ac fundamental voltage to the dc input voltage is expected to be adjusted within a range of two times. The invention is used for voltage regulation control of the full-bridge inverter circuit.
Description
Technical Field
The invention relates to a voltage regulation control method of a full-bridge inverter circuit, and belongs to the technical field of full-bridge inverter circuit control.
Background
Inverter circuits are one of the most commonly used circuits in the field of power electronics, with bridge inverter circuits being used more widely in the field of resonant converters, for example in LLC converters and wireless power transfer systems.
The phase-shift control is one of the most commonly used control methods of bridge inverter circuits, and the ratio of the output voltage to the input voltage of the inverter can be adjusted by changing the phase-shift angle. However, in this control mode, zero voltage turn-on (ZVS) can be achieved only when the impedance angle is greater than half of the inverter phase-shift angle, and a larger impedance angle indicates that there are more reactive components in the system, so ZVS and low reactive components cannot be combined, resulting in difficulty in improving the system efficiency. Therefore, inverter circuits that can achieve ZVS under low reactive component conditions need to be investigated.
Disclosure of Invention
Aiming at the problem that the existing full-bridge inverter circuit adopts phase-shifting control and ZVS and low reactive components cannot be compatible, the invention provides a voltage regulation control method of the full-bridge inverter circuit.
The invention relates to a voltage regulating control method of a full-bridge inverter circuit, which comprises the following steps of,
the duty ratio of a bridge arm driving signal of the full-bridge inverter circuit is 50%; the driving signal of the other bridge arm is synchronous with the driving signal of one bridge arm, and the duty ratio of the driving signal of the other bridge arm is regulated to be changed between 0 and 50 percent according to the ratio of the expected output alternating-current fundamental wave voltage and the direct-current input voltage, so that all switching tubes of the full-bridge inverter circuit realize zero-voltage switching under the low-inductive reactive power condition; the ratio of the output ac fundamental voltage to the dc input voltage is expected to be adjusted within a range of two times.
According to the voltage regulation control method of the full-bridge inverter circuit of the invention,
when the duty ratio of the driving signal of the other bridge arm is 0, the full-bridge inverter circuit is equivalent to a half-bridge inverter circuit;
when the duty ratio of the driving signal of the other bridge arm is 50, the output voltage is a square wave with positive and negative symmetry.
According to the voltage regulation control method of the full-bridge inverter circuit, the actual output alternating current voltage is collected under the condition of direct current input voltage change, and the duty ratio of the driving signal of the other bridge arm is further regulated to be changed between 0 and 50% according to the difference value between the actual output alternating current fundamental wave voltage and the expected output alternating current fundamental wave voltage, so that the actual output alternating current fundamental wave voltage approaches the expected output alternating current fundamental wave voltage.
According to the voltage regulation control method of the full-bridge inverter circuit, under the condition of direct-current input voltage change, the constant actual output alternating-current fundamental wave voltage output is realized by adjusting the duty ratio of the driving signal of the other bridge arm to be changed between 0 and 50 percent.
According to the voltage regulation control method of the full-bridge inverter circuit, the duty ratios of the driving signals of the two bridge arms are in phase, and the duty ratios of the driving signals of the upper bridge arm and the lower bridge arm of each bridge arm are complementary.
According to the voltage regulation control method of the full-bridge inverter circuit, when the actual output alternating voltage is 0 time from negative to positive, the actual output alternating voltage is expressed as u in ：
U in in Is a direct current input voltage, T is a period of a switching tube driving signal, T is time, D is an upper bridge arm switching tube Q of the other bridge arm 1 Duty cycle of the drive signal.
According to the voltage regulation control method of the full-bridge inverter circuit, the amplitude U of the alternating-current fundamental wave voltage is actually output in1 The relation with the duty ratio D is obtained by the following steps:
fourier decomposition of formula (1) yields:
omega in 1 For actually outputting the fundamental wave angular frequency of the alternating voltage, a n And b n Is an intermediate variable;
obtaining the actual output AC fundamental voltage amplitude U from (2) in1 Relationship with duty cycle D:
according to the voltage regulation control method of the full-bridge inverter circuit, the alternating-current fundamental wave voltage u is actually output in The 0 time of (2) is the initial phase, and the actual output AC fundamental wave voltage u is obtained by the equation (2) in Phase angle theta leading initial phase in Greater than critical phase angle theta ZVS When the full-bridge inverter circuit is in a state of realizing zero-voltage on of all switching tubes:
the invention has the beneficial effects that: compared with the phase-shifting control method, the control method can realize zero-voltage switching on of all switching tubes under the condition of lower inductive reactive power, and is beneficial to improving the transmission efficiency of the system.
Drawings
Fig. 1 is a control schematic block diagram of a voltage regulation control method of a full-bridge inverter circuit according to the present invention; c in the figure in A filter capacitor is input;
FIG. 2 is a schematic diagram of a full-bridge inverter circuit controlled by a prior phase shifting method and the method of the present invention;
FIG. 3 shows the inverter step-down ratio G obtained by the method of the present invention v A graph relating to the duty cycle D of the drive signal;
FIG. 4 shows the critical equivalent impedance angle θ of the soft switch in the method of the present invention ZVS A graph relating to the duty cycle D of the drive signal;
FIG. 5 is a critical equivalent impedance angle θ of a soft switch obtained by the prior phase shifting method and the method of the present invention ZVS And inverter voltage gain G v A relationship curve comparison chart;
FIG. 6 is a schematic diagram of an IPT system based on an LCC/S compensation topology in an embodiment;
FIG. 7 is a simulation result of the fundamental amplitude of the output voltage of the inverter and the critical impedance angle of the soft switch as a function of duty cycle for controlling the system of FIG. 6 using the method of the present invention;
FIG. 8 is a critical equivalent impedance angle θ of a soft switch for controlling the system of FIG. 6 using the method of the present invention and a prior art phase shifting method ZVS And inverter voltage gain G v A relationship graph;
FIG. 9 is a waveform diagram of a supply voltage, an inverter output voltage, and a load voltage obtained by controlling the system of FIG. 6 using the method of the present invention; the lower left hand letter in the figure is offset = 0;
fig. 10 is a waveform of the inverter output voltage and current at a power supply voltage of 50V;
fig. 11 is a waveform of the inverter output voltage and current when the power supply voltage is 70V;
fig. 12 is a waveform of the inverter output voltage and current when the power supply voltage is 90V.
Detailed Description
The following description of the embodiments of the present invention will be made clearly and completely with reference to the accompanying drawings, in which it is apparent that the embodiments described are only some embodiments of the present invention, but not all embodiments. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
It should be noted that, without conflict, the embodiments of the present invention and features of the embodiments may be combined with each other.
The invention is further described below with reference to the drawings and specific examples, which are not intended to be limiting.
The first embodiment, referring to fig. 1, provides a voltage regulation control method of a full-bridge inverter circuit, comprising,
the duty ratio of a bridge arm driving signal of the full-bridge inverter circuit is 50%; the driving signal of the other bridge arm is synchronous with the driving signal of one bridge arm, and the duty ratio of the driving signal of the other bridge arm is regulated to be changed between 0 and 50 percent according to the ratio of the expected output alternating-current fundamental wave voltage and the direct-current input voltage, so that all switching tubes of the full-bridge inverter circuit realize zero-voltage switching under the low-inductive reactive power condition; the ratio of the output ac fundamental voltage to the dc input voltage is expected to be adjusted within a range of two times.
The full-bridge inverter circuit in this embodiment is a conventional full-bridge inverter circuit.
In this embodiment, when the duty ratio of the driving signal of the other bridge arm is 0, the full-bridge inverter circuit is equivalent to a half-bridge inverter circuit; when the duty ratio of the driving signal of the other bridge arm is 50, the output voltage is a square wave with positive and negative symmetry.
Further, under the condition of direct current input voltage change, the actual output alternating current voltage is collected, and the duty ratio of the driving signal of the other bridge arm is further adjusted to be changed between 0 and 50% according to the difference value between the actual output alternating current fundamental wave voltage and the expected output alternating current fundamental wave voltage, so that the actual output alternating current fundamental wave voltage approaches the expected output alternating current fundamental wave voltage.
As an example, under the condition that the dc input voltage varies, by adjusting the duty ratio of the driving signal of the other bridge arm to vary between 0 to 50%, a constant actual output ac fundamental voltage output can be achieved.
In combination with the illustration of fig. 1, the method of the invention can collect the output voltage of the inverter, obtain the control signal of the switching tube through the controller, then calculate and obtain the driving signal according to the control signal by the driver, control the duty ratio of the driving signal of the left bridge arm, and then adjust the duty ratio of the output voltage, thus realizing constant fundamental voltage output. In FIG. 1, Q 1 -Q 4 Is MOSFET, u in And i in The output voltage and the output current of the inverter are respectively, the point A and the point B are used as the connection points of the output ends, Z in The impedance is input to the system.
In fig. 1, the duty ratio D of the driving signal of the switching tube of the left arm is adjusted to be 0.5 at all times while the driving signal of the right arm is unchanged. In this embodiment, the duty ratios of the driving signals of the two bridge arms are in phase, and the duty ratios of the driving signals of the upper and lower bridge arms of each bridge arm are complementary; the driving signal duty ratio is controlled by the primary side inversion output voltage fundamental wave.
Still further, referring to FIG. 2, the new control in FIG. 2 corresponds to the control method of the present invention, u in1 Is the fundamental wave of the output voltage of the inverter.
Assuming that the time of the commutation point of the actual output AC voltage from negative to positive is 0, the actual output AC voltage is expressed as u in ：
U in in Is a direct current input voltage, T is a period of a switching tube driving signal, T is time, D is an upper bridge arm switching tube Q of the other bridge arm 1 Duty cycle of the drive signal.
In the present embodiment, the ac fundamental voltage amplitude U is actually output in1 The relation with the duty ratio D is obtained by the following steps:
fourier decomposition of formula (1) yields:
omega in 1 For actually outputting the fundamental wave angular frequency of the alternating voltage, a n And b n Is an intermediate variable;
obtaining the actual output AC fundamental voltage amplitude U from (2) in1 Relationship with duty cycle D:
to actually output the AC fundamental voltage u in The 0 time of (2) is the initial phase, and the actual output AC fundamental wave voltage u is obtained by the equation (2) in Phase angle theta leading initial phase in Greater than critical phase angle theta ZVS When the full-bridge inverter circuit is in a state of realizing zero-voltage on of all switching tubes:
in order to realize zero voltage turn-on, the inverter output current needs a hysteresis voltage, when the voltage is in rising or falling edge moment, the current crosses zero, and in order to realize the limit moment of the soft switch, at this moment:
θ ZVS ＝θ in 。
in contrast, in the phase shift control, the inverter output voltage u is set in Is of duty cycle D 1 Output voltage u in The expression of (2) is:
the fundamental wave amplitude U of the output voltage of the inverter can be obtained by the formula (5) in1 With duty cycle D 1 Relationship:
setting critical equivalent impedance angle theta for realizing soft switch by phase shift control ZVS The expression is:
in order to compare the advantages of the novel control on the phase shift control, the voltage reduction ratio of the inverter is set as G v The expression is as follows:
from the formula (3), the inverter step-down ratio G under the novel control method v And drive signal duty cycleA graph of the relationship of the ratio D is shown in fig. 3.
The critical equivalent impedance angle for realizing the soft switch under the novel control method is theta as can be obtained by the formula (4) ZVS A graph of the drive signal duty cycle D is shown in fig. 4.
The critical equivalent impedance angle theta of the soft switch can be realized by the formulas (3), (4) and (6), (7) ZVS And inverter voltage gain G v As shown in fig. 5. As can be seen from fig. 5, the novel control method of the present invention is easier to realize soft switching and has lower reactive component in the same voltage regulation range.
Specific examples:
through the analysis and calculation, the functional relation between the output voltage of the inverter and the critical equivalent impedance angle for realizing the soft switch and the duty ratio of the driving signal of the switching tube of the left bridge arm is determined. Based on the functional relationship, when the direct current input voltage changes, the output voltage of the inverter can be adjusted by adjusting the duty ratio of the driving signal, so that the constant voltage output of the inverter is realized. In addition, the method of the invention is easier to realize soft switching without excessively adjusting the primary input impedance, and therefore has lower reactive power component.
In order to verify the effectiveness and feasibility of the novel control method, in combination with the illustration of fig. 6, taking LCC/S compensation topology as an example, simulation verification is performed, and the compensation parameter design method is shown in formula (9), wherein G is the voltage gain of the compensation topology. The LCC/S compensation topology in this compensation mode has zero phase angle characteristics (ZPA) and the rectifier bridge input impedance is approximately resistive when the load resistance is small. The primary input impedance is also resistive. However, in order to achieve zero voltage turn-on of the switching tube, the primary input impedance must be made weakly inductive. In order to not destroy the constant voltage output characteristic of LCC/S and realize weak primary input impedance, the method can reduce C 1 Is a capacitance value of (2). However, when the resonance state of the compensation network is changed, reactive components tend to be increased, so that coil current is increased and efficiency is reduced, in order to compare a novel control method with a traditional phase-shifting control method, open-loop and closed-loop simulation experiments are performed in circuit simulation software, and finallyAnd constant voltage output of the inverter under the condition of changing direct current input voltage is realized.
An IPT system circuit model based on LCC/S compensation topology and a novel controllable rectifier is shown in fig. 6, and basic circuit parameters are shown in table 1.
U in re Inputting fundamental wave alternating voltage to a rectifier; m is mutual inductance; l (L) f1 To compensate for inductance; omega 1 Is the fundamental angular frequency; c (C) f1 A compensation capacitor is connected in parallel to the primary side; l (L) P Is self-inductance of the primary coil; c (C) 1 A compensation capacitor is connected in series for the primary side; c (C) 2 A compensation capacitor is connected in parallel to the secondary side; l (L) S Is the self-inductance of the secondary coil.
TABLE 1 IPT System parameter Table based on LCC/S Compensation topology
First, open loop experiments were performed to change Q 1 、Q 2 The duty ratio of the driving signal is shown in fig. 7 by taking load 5Ω as an example, the fundamental amplitude of the output voltage of the inverter and the simulation result of the change of the critical equivalent impedance angle of the soft switch along with the duty ratio are shown, the simulation result of the output voltage substantially accords with the theoretical calculation value, and the simulation result of the critical equivalent impedance angle of the soft switch is slightly larger than the theoretical calculation value, because the harmonic exists in the primary side input current in the actual circuit. Therefore, in order to realize soft switching, the critical equivalent impedance angle needs to be 3 to 5 ° greater than the theoretical value.
When the power supply voltage is changed, the duty ratio of the adjustable inversion controls the fundamental wave amplitude of the output voltage of the inverter to be basically constant, and further controls the power supply voltage to be changed within a certain range so as not to cause load voltage fluctuation. In this embodiment, taking the amplitude of the output fundamental voltage of the inverter as 63.7V as an example, the load is set to 10Ω, the dc input voltage is increased from 50V to 70V, and then increased to 90V, and waveforms of the power supply voltage, the output voltage of the inverter, and the load voltage are shown in fig. 9. In fig. 9, the fundamental wave amplitudes of the output voltages of the three inverters A1, A2 and A3 are substantially the same, and the influence of the power supply voltage change on the subsequent-stage circuit is counteracted by changing the duty ratio of a single bridge arm, so that the load voltage is maintained to be substantially constant.
The waveforms of the inverter output voltage and current when the power supply voltage is 50V are shown in fig. 10, the waveforms of the inverter output voltage and current when the power supply voltage is 70V are shown in fig. 11, and the waveforms of the inverter output voltage and current when the power supply voltage is 90V are shown in fig. 12. Under three conditions, the angle of the leading current fundamental wave of the output voltage of the inverter is about 26 degrees, and the four switching tubes all have the phase angle condition of realizing zero voltage opening. Therefore, the inverter control method provided by the invention can realize zero-voltage turn-on under the condition of low system input impedance angle.
In summary, the novel control method of the inverter provided by the invention can realize constant voltage output under the condition of changing direct current input voltage, and compared with phase shift control, zero voltage switching-on of four switching tubes of the inverter can be realized under the condition of lower inductive reactive power. The method uses a wireless power transmission system as an example to verify a specific example; however, the method of the invention can be applied not only to wireless power transmission technology, but also to other power electronics fields.
Although the invention herein has been described with reference to particular embodiments, it is to be understood that these embodiments are merely illustrative of the principles and applications of the present invention. It is therefore to be understood that numerous modifications may be made to the illustrative embodiments and that other arrangements may be devised without departing from the spirit and scope of the present invention as defined by the appended claims. It should be understood that the different dependent claims and the features described herein may be combined in ways other than as described in the original claims. It is also to be understood that features described in connection with separate embodiments may be used in other described embodiments.
Claims (8)
1. A voltage regulating control method of a full-bridge inverter circuit is characterized by comprising the following steps of,
the duty ratio of a bridge arm driving signal of the full-bridge inverter circuit is 50%; the driving signal of the other bridge arm is synchronous with the driving signal of one bridge arm, and the duty ratio of the driving signal of the other bridge arm is regulated to be changed between 0 and 50 percent according to the ratio of the expected output alternating-current fundamental wave voltage and the direct-current input voltage, so that all switching tubes of the full-bridge inverter circuit realize zero-voltage switching under the low-inductive reactive power condition; the ratio of the output ac fundamental voltage to the dc input voltage is expected to be adjusted within a range of two times.
2. The method for controlling voltage regulation of a full-bridge inverter circuit of claim 1, wherein,
when the duty ratio of the driving signal of the other bridge arm is 0, the full-bridge inverter circuit is equivalent to a half-bridge inverter circuit;
when the duty ratio of the driving signal of the other bridge arm is 50, the output voltage is a square wave with positive and negative symmetry.
3. The method for controlling voltage regulation of a full-bridge inverter circuit of claim 2, wherein,
under the condition of direct current input voltage change, collecting actual output alternating current voltage, and further adjusting the duty ratio of the driving signal of the other bridge arm to change between 0 and 50 percent according to the difference value between the actual output alternating current fundamental wave voltage and the expected output alternating current fundamental wave voltage, so that the actual output alternating current fundamental wave voltage approaches the expected output alternating current fundamental wave voltage.
4. The method for controlling voltage regulation of a full-bridge inverter circuit of claim 3,
under the condition of direct current input voltage variation, constant actual output alternating current fundamental wave voltage output is realized by adjusting the duty ratio of the driving signal of the other bridge arm to be varied between 0 and 50 percent.
5. The method for controlling voltage regulation of a full-bridge inverter circuit of claim 3,
the duty ratios of the two bridge arm driving signals are in phase, and the duty ratios of the upper and lower bridge arm driving signals of each bridge arm are complementary.
6. The method for voltage regulation control of a full-bridge inverter circuit of claim 5, wherein,
assuming that the time of the commutation point of the actual output AC voltage from negative to positive is 0, the actual output AC voltage is expressed as u in ：
U in in Is a direct current input voltage, T is a period of a switching tube driving signal, T is time, D is an upper bridge arm switching tube Q of the other bridge arm 1 Duty cycle of the drive signal.
7. The method of controlling voltage regulation of a full-bridge inverter circuit of claim 6, wherein,
actual output AC fundamental voltage amplitude U in1 The relation with the duty ratio D is obtained by the following steps:
fourier decomposition of formula (1) yields:
omega in 1 For actually outputting the fundamental wave angular frequency of the alternating voltage, a n And b n Is an intermediate variable;
obtaining the actual output AC fundamental voltage amplitude U from (2) in1 Relationship with duty cycle D:
8. the method for voltage regulation control of a full-bridge inverter circuit of claim 7, wherein,
to actually output the AC fundamental voltage u in The 0 time of (2) is the initial phase, and the actual output AC fundamental wave voltage u is obtained by the equation (2) in Phase angle theta leading initial phase in Greater than critical phase angle theta ZVS When the full-bridge inverter circuit is in a state of realizing zero-voltage on of all switching tubes:
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