CN116996082B - Differential output wake-up receiver radio frequency circuit - Google Patents
Differential output wake-up receiver radio frequency circuit Download PDFInfo
- Publication number
- CN116996082B CN116996082B CN202311243820.9A CN202311243820A CN116996082B CN 116996082 B CN116996082 B CN 116996082B CN 202311243820 A CN202311243820 A CN 202311243820A CN 116996082 B CN116996082 B CN 116996082B
- Authority
- CN
- China
- Prior art keywords
- resonator
- radio frequency
- differential output
- self
- wake
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
- 230000008878 coupling Effects 0.000 claims abstract description 29
- 238000010168 coupling process Methods 0.000 claims abstract description 29
- 238000005859 coupling reaction Methods 0.000 claims abstract description 29
- 230000035945 sensitivity Effects 0.000 claims description 13
- 235000019687 Lamb Nutrition 0.000 claims description 8
- 239000013078 crystal Substances 0.000 claims description 8
- 239000010453 quartz Substances 0.000 claims description 8
- VYPSYNLAJGMNEJ-UHFFFAOYSA-N silicon dioxide Inorganic materials O=[Si]=O VYPSYNLAJGMNEJ-UHFFFAOYSA-N 0.000 claims description 8
- 238000010897 surface acoustic wave method Methods 0.000 claims description 8
- 239000010409 thin film Substances 0.000 claims description 7
- 238000001914 filtration Methods 0.000 abstract description 19
- 239000003990 capacitor Substances 0.000 description 12
- 238000001514 detection method Methods 0.000 description 10
- 238000006243 chemical reaction Methods 0.000 description 8
- 238000005070 sampling Methods 0.000 description 6
- 230000000903 blocking effect Effects 0.000 description 4
- 238000004891 communication Methods 0.000 description 4
- 230000009291 secondary effect Effects 0.000 description 4
- 238000013461 design Methods 0.000 description 3
- 230000001629 suppression Effects 0.000 description 3
- 238000010586 diagram Methods 0.000 description 2
- 230000000694 effects Effects 0.000 description 2
- 239000010408 film Substances 0.000 description 2
- 230000006872 improvement Effects 0.000 description 2
- 238000000034 method Methods 0.000 description 2
- 238000012986 modification Methods 0.000 description 2
- 230000004048 modification Effects 0.000 description 2
- 230000003595 spectral effect Effects 0.000 description 2
- 230000008859 change Effects 0.000 description 1
- 230000001276 controlling effect Effects 0.000 description 1
- 230000007423 decrease Effects 0.000 description 1
- 230000001419 dependent effect Effects 0.000 description 1
- 238000011161 development Methods 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 230000036039 immunity Effects 0.000 description 1
- 239000000463 material Substances 0.000 description 1
- 238000012545 processing Methods 0.000 description 1
- 230000001737 promoting effect Effects 0.000 description 1
- 230000001105 regulatory effect Effects 0.000 description 1
- 238000000926 separation method Methods 0.000 description 1
- 238000006467 substitution reaction Methods 0.000 description 1
- 238000013519 translation Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/06—Receivers
- H04B1/10—Means associated with receiver for limiting or suppressing noise or interference
Abstract
The present disclosure provides a differential output wake-up receiver radio frequency circuit comprising: the self-mixer is filtered based on a differential output of the second resonator based on a filtering matching network of the first resonator. The filter matching network is connected with the antenna to receive an input signal and is used for providing a radio frequency passband with a relative fractional bandwidth of less than 4%; the differential output filter self-mixer is connected with the filter matching network and is used for providing differential output of resonant frequency and antiresonant frequency; the filter matching network can realize matching at the positive resonant frequency and the anti-resonant frequency of the second resonator by adjusting the resonant frequency and the electromechanical coupling coefficient of the first resonator and the second resonator, so that two radio frequency pass bands with approximately equal gains are obtained, and signals of the two radio frequency pass bands are subjected to opposite self-mixing output through the differential output self-mixer, so that interference signals in the two radio frequency pass bands are counteracted.
Description
Technical Field
The disclosure relates to the technical field of radio frequency wireless communication, and in particular relates to a differential output wake-up receiver radio frequency circuit.
Background
The wake-up receiver can monitor the channel with extremely low power consumption, and wake-up the main receiver when the wake-up receiver receives the wake-up signal, so that the standby power consumption of the wireless communication system can be reduced. With the development of wireless communication technology, wake-up receivers require lower power consumption, higher sensitivity and higher interference immunity.
In order to eliminate the high power consumption (> 20 microwatts) introduced by the oscillator, low power wake-up receivers often employ self-mixing architectures to down-convert the radio frequency signals, thereby reducing the system power consumption below microwatts. Existing self-mixers down-convert all input signals within the front-end passband to baseband and produce a co-directional output. The magnitude of the interference signal in the baseband circuit is proportional to the total power density of the interference signal in the system radio frequency passband in the sampling period. The sensitivity of the wake-up receiver requires a power that is higher than the background interference within the radio frequency passband. In practical applications, the wake-up receiver often needs to work in a crowded frequency band such as WiFi and ISM, and the larger in-band interference greatly limits the sensitivity of the system, and reduces the practicability.
Disclosure of Invention
Based on the above-mentioned problems, the present disclosure provides a differential output wake-up receiver radio frequency circuit, so as to alleviate the above-mentioned technical problems in the prior art, and enable signals of two radio frequency pass bands to generate opposite self-mixing output through a differential output self-mixer, and interference signals in the two pass bands can cancel each other, thereby suppressing in-band interference signals of the wake-up receiver, and improving anti-interference capability and robustness of the system.
Technical scheme (one)
The present disclosure provides a differential output wake-up receiver radio frequency circuit comprising: the self-mixer is filtered based on a differential output of the second resonator based on a filtering matching network of the first resonator. The filter matching network is connected with the antenna to receive an input signal and is used for providing a radio frequency passband with a relative fractional bandwidth of less than 4%; the differential output filter self-mixer is connected with the filter matching network and is used for providing differential output of resonant frequency and antiresonant frequency; the filter matching network can realize matching at the positive resonant frequency and the anti-resonant frequency of the second resonator by adjusting the resonant frequency and the electromechanical coupling coefficient of the first resonator and the second resonator, so that two radio frequency pass bands with approximately equal gains are obtained, and signals of the two radio frequency pass bands are subjected to opposite self-mixing output through the differential output self-mixer, so that interference signals in the two radio frequency pass bands are counteracted.
According to the embodiment of the disclosure, the electromechanical coupling coefficient of the second resonator is lower than that of the first resonator, and the Q values of the resonance frequency and the antiresonance frequency are approximately equal.
According to the embodiment of the disclosure, the self-mixing coefficients of the two radio frequency pass bands are the same in size and opposite in direction.
According to an embodiment of the present disclosure, the first resonator is selected from a thin film bulk acoustic resonator, a laterally vibrating piezoelectric resonator, a bulk acoustic resonator, a surface acoustic wave resonator, a lamb wave resonator, a shear piezoelectric resonator, and a quartz crystal resonator.
According to an embodiment of the present disclosure, the second resonator is selected from a surface acoustic wave resonator, a thin film bulk acoustic wave resonator, a transverse vibration piezoelectric resonator, a bulk acoustic wave resonator, a lamb wave resonator, a shear piezoelectric resonator, a quartz crystal resonator, a hollow disk resonator, and a FINBAR resonator.
According to the embodiment of the disclosure, the differential output wake-up receiver radio frequency circuit further comprises an LNA module which is inserted into a front stage or a rear stage of the filtering matching network to improve the sensitivity of the system.
According to an embodiment of the present disclosure, the CMOS transistor structure in the differential output filter self-mixer is selected from a single-stage structure, a multi-stage cascade structure or a pseudo-differential multi-stage cascade structure.
According to embodiments of the present disclosure, the CMOS transistors in the differential output filter self-mixer provide a gate dc bias voltage by using a gate voltage bias circuit, or a drain or source.
According to an embodiment of the present disclosure, an input signal of a differential output filter self-mixer is input to the drain or source of all or part of the transistors through a coupling circuit.
According to the embodiment of the disclosure, the self-mixing conversion coefficients at the series resonance frequency and the anti-resonance frequency of the second resonator are equal in magnitude and opposite in direction.
(II) advantageous effects
As can be seen from the above technical solutions, the wake-up receiver radio frequency circuit with differential output of the present disclosure has at least one or a part of the following advantages:
(1) The filtering matching network based on the micro-electromechanical resonator and the differential output filtering self-mixer based on the high Q value micro-electromechanical resonator are used for cascading, and the reverse output of two radio frequency passband signals is realized by utilizing the change of the impedance of the resonators, so that the baseband interference signals can be reduced along with the improvement of the sampling time, and the anti-interference capability and the robustness of a wake-up receiver are improved;
(2) By alternately transmitting signals in the two radio frequency pass bands, differential output of radio frequency signal self-mixing signals can be realized; the differential output can improve the amplitude of the baseband signal under the same input power signal, improve the sensitivity of the system and improve the wake-up distance of the wake-up receiver. Meanwhile, the common mode level shift and other problems caused by pseudo-differential or single-ended output can be solved, so that the design of a baseband circuit can be simplified and the system power consumption can be reduced;
(3) The total radio frequency passband bandwidth of the system can be reduced, the probability of entering the system by the interference signal is reduced, and the anti-interference capability of the system is improved. The introduction of the differential output filtering self-mixer can also promote the suppression of interference signals outside the passband, and further promote the robustness of the system.
Drawings
Fig. 1 is a schematic diagram of a differential output wake-up receiver radio frequency circuit in accordance with an embodiment of the present disclosure.
Fig. 2 is a schematic diagram of a circuit composition of a filtering self-mixer according to an embodiment of the disclosure.
Detailed Description
The disclosure provides a differential output wake-up receiver radio frequency circuit, which mainly comprises a filtering matching network taking a first radio frequency micro-electromechanical resonator as a core element and a differential output filtering self-mixer based on a second micro-electromechanical resonator. Whether or not to introduce a radio frequency Low Noise Amplifier (LNA) may be selected based on power consumption budget and sensitivity requirements.
Existing wake-up receiver radio circuits include filter matching circuits, radio frequency self-mixers, and may choose whether to introduce a radio frequency Low Noise Amplifier (LNA) based on power consumption budget and sensitivity requirements. Input V of radio frequency self-mixer in To output V out The conversion relation of (2) is:
v out =k ed ×v in 2 ；
for input signals V of arbitrary frequency in Conversion coefficient k ed Is fixed. Thus for the followingAny input signal whose output signal is fixed in sign (dependent on the self-mixer conversion coefficient k ed Positive or negative of (a). The existing self-mixers will therefore produce a co-directional output of all the input signals within the passband of the previous stage. In practical applications, in order to ensure the anti-interference performance and robustness of the wake-up receiver, the sensitivity is limited by the spectral density of the interference signal in its operating frequency band. Accordingly, the present disclosure provides a differentially output wake-up receiver radio frequency circuit.
For the purposes of promoting an understanding of the principles and advantages of the disclosure, reference will now be made to the embodiments illustrated in the drawings and specific language will be used to describe the same.
In an embodiment of the present disclosure, a differential output wake-up receiver radio frequency circuit is provided, and as shown in fig. 1 and 2, the differential output wake-up receiver radio frequency circuit includes:
a filter matching network based on a first resonator coupled to the antenna for receiving an input signal for providing a relative fractional bandwidth radio frequency passband of less than 4%;
a second resonator-based differential output filter self-mixer coupled to the filter matching network for providing a differential output of the resonant frequency and the antiresonant frequency;
the filter matching network can realize matching at the positive resonant frequency and the anti-resonant frequency of the second resonator by adjusting the resonant frequency and the electromechanical coupling coefficient of the first resonator and the second resonator, so that two radio frequency pass bands with approximately equal gains are obtained, and signals of the two radio frequency pass bands are subjected to opposite self-mixing output through the differential output self-mixer, so that interference signals in the two radio frequency pass bands are counteracted. It should be noted that, it is preferable to obtain two rf pass bands with equal gains, but since the gains of the two rf pass bands are difficult to be completely the same in practical situations, the gains can be only approximately equal or tend to be equal, for example, the ratio of the difference between the two gains is not more than 3%, which may be referred to as approximately equal.
Unlike prior structures, the differential output wake-up receiver rf circuit of the present disclosure employs a filter matching network with a first rf microelectromechanical resonator as a core element, and a differential output filter self-mixer based on a second microelectromechanical resonator. The first resonator may be a radio frequency microelectromechanical resonator such as an FBAR (film bulk acoustic resonator), and based on a higher FoM value (> 100) and a Q value greater than 1000, the filter matching network has higher sensitivity and a relative fractional bandwidth of a single frequency band may be lower than 4%. The filter matching network can realize matching at the positive and negative resonance frequency of the second resonator by regulating and controlling the resonance frequency and the electromechanical coupling coefficient of the first resonator and the second resonator. The filter matching network thus has two radio frequency pass bands with approximately equal gains.
The second resonator needs to have an electromechanical coupling coefficient lower than that of the first resonator, and the resonant frequency is similar to the Q value of the antiresonant frequency. Near the resonant frequency of the second resonator (i.e. one of the two radio frequency pass bands, also referred to as pass band one), the resonator impedance is very low, the filtering self-mixer is equivalent to a diode connection, the conversion coefficient of which is negative. In the vicinity of the antiresonant frequency of the second resonator (i.e. the other of the two radio frequency pass bands, which may also be referred to as pass band two), the filter self-mixer is equivalent to a triode connection whose conversion coefficient is positive. When the resonance frequency is similar to the Q value of the antiresonance frequency, the absolute values of the conversion coefficients are similar and the signs are opposite.
By cascading the filter matching network with a differential output filter self-mixer, two radio frequency pass bands can be obtained through fine setting. After the input signals in the two pass bands pass through the radio frequency circuit, input signals with equal magnitudes and opposite directions are generated at the baseband. The interference signal in the baseband is proportional to the difference between the average interference signal power in passband two and the average interference signal power in passband one in the sampling period. The two pass bands are positioned in the same communication frequency band, so that the longer the sampling period is, the closer the value is to 0, the anti-interference capability of the system is greatly improved, and the sensitivity is not limited by the spectral density of interference signals in the working frequency band.
In an embodiment of the present disclosure, as shown in fig. 2, a filtered self-mixer of a differential output includes: input signal terminal IN, capable ofThe quantity detection circuit unit 10, the bias voltage unit, the coupling branch unit, the micro-electromechanical resonator branch. The input signal end IN is used for receiving a wake-up signal and an interference signal as input signals; the energy detection circuit unit 10 includes at least one CMOS tube, preferably 30 to 50 CMOS tubes, four CMOS tubes in fig. 2, four CMOS tubes of an N-type CMOS tube 11, a P-type CMOS tube 12, an N-type CMOS tube 13, and a P-type CMOS tube 14, which are sequentially connected. The energy detection circuit unit 10 is used for mixing input signals through the secondary effect of the CMOS tube and outputting baseband signals; the bias voltage unit is used for providing the grid voltage of the CMOS tube so as to adjust the channel impedance of the CMOS tube; the coupling branch unit is arranged between the input signal end and the energy detection circuit unit, and is used for coupling the input signal to the drain electrodes or the source electrodes of the CMOS tubes in the energy detection circuit unit, and as shown in fig. 2, the input signal is respectively coupled to the drain electrodes of the four CMOS tubes through a coupling capacitor C1 and a coupling capacitor C2; the micro-electromechanical resonator branch is arranged between the input signal end IN and the bias voltage unit and the energy detection circuit unit 10, and can output different grid signals under different frequencies to adjust the secondary effect, so as to realize the filtering of interference signals IN the input signals. A coupling capacitor C is also connected between the signal output terminal OUT and the source of the N-type CMOS tube 11 C And the sources of the N-type CMOS tube 11 and the P-type CMOS tube 12 are connected with a coupling capacitor C C And is grounded. The source of the P-type CMOS transistor 14 is connected to a common mode level VC.
According to the embodiment of the disclosure, the energy detection circuit is a triode type energy detection circuit, and the CMOS tube in the energy detection circuit unit is selected from an N type CMOS tube and a P type CMOS tube; the CMOS tube arrangement in the energy detection circuit unit includes a single-stage form, a multi-stage cascade form or a multi-stage cascade form of pseudo-differential form. When both the N-type CMOS transistor and the P-type CMOS transistor are present, the N-type CMOS transistor and the P-type CMOS transistor are alternately connected, for example, in the form of N-P-N-P or P-N-P-N connection.
According to an embodiment of the disclosure, the bias voltage unit comprises at least one bias voltage branch, and each bias voltage branch comprises a bias voltage source and a bias resistor which are sequentially connected. As shown in fig. 2, the bias voltage unit includes two bias voltage branchesRespectively, is a bias voltage source V for providing grid voltage to two N-type CMOS tubes 11 and 13 GN And bias voltage source V GN Connected bias resistor R B1 The method comprises the steps of carrying out a first treatment on the surface of the And a bias voltage source V providing a gate voltage to the two P-type CMOS transistors 12, 14 GP And bias voltage source V GP Connected bias resistor R B2 。
According to an embodiment of the present disclosure, the coupling-leg unit comprises at least one coupling leg, each coupling leg comprising a coupling capacitance connected to the input signal terminal, said coupling capacitance being connected to the drain or source of the corresponding CMOS transistor. As shown IN fig. 2, the coupling-arm unit includes two coupling arms, one of which has one end connected to the input signal terminal IN and the other end connected to the drains of the N-type CMOS pipe 11 and the P-type CMOS pipe 12 through the coupling capacitor C1; the other coupling branch is connected to the input signal terminal IN at one end and to the drains of the N-type CMOS tube 13 and the P-type CMOS tube 14 via a coupling capacitor C2 at the other end.
According to an embodiment of the present disclosure, the microelectromechanical resonator branch includes a microelectromechanical resonator 21, a blocking capacitor 22. One end of the microelectromechanical resonator 21 is connected to the input signal terminal IN, and the other end is connected to the gate of the CMOS pipe, as shown IN fig. 2, and the other end of the microelectromechanical resonator 21 is connected to the gates of the N-type CMOS pipe 11, 13; one end of the blocking capacitor 22 is connected with the micro-electromechanical resonator 21, and the two ends are connected to the grid electrode of the CMOS tube for isolating the direct current level of the CMOS tube. As shown in fig. 2, the other end of the blocking capacitor 22 is connected to the gate of the P-type CMOS transistor 12, 14.
According to the embodiment of the disclosure, when the frequency of the interference signal in the input signal is far away from the anti-resonant frequency of the microelectromechanical resonator 21, the microelectromechanical resonator 21 corresponds to an equivalent capacitance, and the capacitance of the equivalent capacitance is adjusted by adjusting the geometry of the resonator so as to adjust the size of the gate signal coupled to the gate of the CMOS transistor, so that the secondary effects of the gate and the drain or the drain of the transistor cancel each other, and thus the baseband signal is not output.
According to an embodiment of the present disclosure, a bias voltage source (V GN、 V GP ) Grid DC bias can be provided by a grid voltage bias circuitSetting a voltage or providing a gate dc bias voltage through the drain or source of the transistor.
According to the embodiment of the disclosure, as shown in fig. 2, the number of stages of the self-mixer is 4 (i.e. the number of cascaded CMOS transistors is 4), and other stages, preferably 30 stages or 40 stages, may be used in practical application, and a pseudo-differential cascade manner may also be used. A microelectromechanical resonator 21 is introduced between the gate and drain of the CMOS transistor and adjusts and blocks the channel resistance of the transistor by means of a bias resistor and a blocking capacitor. The rf microelectromechanical resonator 21 exhibits high-impedance characteristics near the anti-resonant frequency, and the filtered self-mixer is equivalent to a conventional self-mixer. Outside the antiresonant frequency, the impedance of the microelectromechanical resonator decreases, which reduces the input impedance from the mixer, destroying the matching conditions with the previous stage, reducing the input signal size from the mixer. Thus, the input signal of the same magnitude, the output signal generated by the input at the antiresonant frequency is larger than the other frequencies, and the self-mixer achieves the filtering effect. Because the Q of the microelectromechanical resonator is higher at the antiresonant frequency, a lower passband bandwidth is achieved. At a distance from the antiresonance frequency, the resonator is equivalent to a capacitor, and the capacitance of the equivalent capacitor can be adjusted by adjusting the geometry of the resonator. By adjusting the capacitance value, the magnitude of the signal coupled to the gate of the CMOS transistor can be adjusted, so that the secondary effects of the gate and the drain of the transistor are mutually offset, and the output signal of the baseband is not generated. The input signal at a distance from the antiresonant frequency produces little output signal.
According to the embodiment of the disclosure, the electromechanical coupling coefficient of the second resonator is lower than that of the first resonator by adjusting, and the resonance frequency of the second resonator is approximately equal to or tends to be equal to the Q value of the antiresonance frequency. It should be noted that, in actual operation, it is difficult to make the Q values of the resonant frequency and the antiresonant frequency identical, and only the Q values of the resonant frequency and the antiresonant frequency are approximately identical, for example, the ratio of the difference between the Q values of the resonant frequency and the antiresonant frequency is not more than 3%, and the resonant frequency and the antiresonant frequency may be referred to as approximately identical.
According to the embodiment of the disclosure, the self-mixing coefficients of the two radio frequency pass bands are the same in size and opposite in direction.
According to an embodiment of the present disclosure, the first resonator is selected from a thin film bulk acoustic resonator, a laterally vibrating piezoelectric resonator, a bulk acoustic resonator, a surface acoustic wave resonator, a lamb wave resonator, a shear piezoelectric resonator, and a quartz crystal resonator.
According to an embodiment of the present disclosure, the second resonator is selected from the group consisting of a surface acoustic wave resonator, a thin film bulk acoustic wave resonator, a laterally vibrating piezoelectric resonator, a bulk acoustic wave resonator, a lamb wave resonator, a shear piezoelectric resonator, a quartz crystal resonator, a hollow disk resonator, and a FINBAR resonator.
According to an embodiment of the disclosure, the wake-up receiver radio frequency circuit with differential output may further include an LNA module inserted in a front stage or a rear stage of the filtering matching network to improve sensitivity of the system.
According to the embodiment of the disclosure, the structure form of the CMOS transistor in the differential output filtering self-mixer can be a single-stage structure form, a multi-stage cascade structure form or a multi-stage cascade structure form of pseudo-differential form.
According to embodiments of the present disclosure, CMOS transistors in a differential output filtered self-mixer may provide a gate dc bias voltage by using a gate voltage bias circuit, or may provide a dc bias voltage by either the drain or the source.
According to an embodiment of the present disclosure, an input signal of a differential output filter self-mixer is input to the drain or source of all or part of the transistors through a coupling circuit.
According to the embodiment of the disclosure, the self-mixing conversion coefficients at the series resonance frequency and the anti-resonance frequency of the second resonator are equal in magnitude and opposite in direction.
In some embodiments, the filtering matching network employs a first resonator, preferably a Film Bulk Acoustic Resonator (FBAR), and other types of resonators may be employed including, but not limited to: a transverse vibration piezoelectric resonator, a bulk acoustic wave resonator, a surface acoustic wave resonator, a lamb wave resonator, a shear piezoelectric resonator, a quartz crystal resonator, and the like. The structure of the filtering matching network is a transformer type matching network based on a micro-electromechanical resonator, and matching networks with other structures can be adopted; and a structure of cascade connection of a matching network based on off-chip high Q value inductance and a narrow-band filter based on a micro-electromechanical resonator can also be adopted. The resonator used in the differential output filter self-mixer is a second resonator, preferably a surface acoustic wave resonator, and other types of resonators may be used including, but not limited to: thin film bulk acoustic resonators, laterally vibrating piezoelectric resonators, bulk acoustic resonators, lamb wave resonators, shear piezoelectric resonators, quartz crystal resonators, hollow disk resonators, FINBAR resonators, and the like.
In some embodiments, the first resonator and the second resonator may be manufactured monolithically or may be manufactured separately and packaged. LNA modules can be inserted in front of the filter matching network to improve the sensitivity of the system.
In some embodiments, the alternative arrangement of CMOS transistors in the differential output filter self-mixer includes, but is not limited to, a single stage version, a multi-stage cascade version, or a multi-stage cascade version of a pseudo-differential version.
In some embodiments, the CMOS transistors in the differential output filtered self-mixer may provide a gate dc bias voltage using a gate voltage bias circuit; the dc bias voltage may also be provided by the drain or source of the pipe.
In some embodiments, the input signal of the differential output filter self-mixer may be input to the drain of the transistor through the coupling circuit, may be input to the source of the transistor through the coupling circuit, and may be input to the drain of a portion of the transistor and the source of a portion of the transistor.
By reasonably selecting materials, modes, geometric structures and the like of the first resonator and the second resonator, the input impedance of the differential output filtering self-mixing at the positive and negative resonance frequency of the second resonator can be matched with the filtering matching network of the front stage. The size of the second resonator is adjusted, so that the suppression of the differential output filtering self-mixer to out-of-band signals can be improved.
By the arrangement, the wake-up receiver can have two radio frequency pass bands, and the self-mixing coefficients of the two pass bands are the same in size and opposite in direction. By prolonging the sampling period, the total self-mixing signal generated by the interference signals of the two pass bands in the sampling period can be reduced, and the suppression capability of the in-band interference signals is further improved.
Thus, embodiments of the present disclosure have been described in detail with reference to the accompanying drawings. It should be noted that, in the drawings or the text of the specification, implementations not shown or described are all forms known to those of ordinary skill in the art, and not described in detail. Furthermore, the above definitions of the elements and methods are not limited to the specific structures, shapes or modes mentioned in the embodiments, and may be simply modified or replaced by those of ordinary skill in the art.
From the foregoing description, it should be apparent to those skilled in the art that the wake-up receiver radio frequency circuit of the differential output of the present disclosure.
In summary, the disclosure provides a differential output wake-up receiver radio frequency circuit, which enables signals of two radio frequency pass bands to generate opposite self-mixing output through a differential output self-mixing device, and interference signals in the two pass bands can cancel each other, so as to inhibit in-band interference signals of the wake-up receiver, and improve anti-interference capability and robustness of a system.
It should also be noted that the foregoing describes various embodiments of the present disclosure. These examples are provided to illustrate the technical content of the present disclosure, and are not intended to limit the scope of the claims of the present disclosure. A feature of one embodiment may be applied to other embodiments by suitable modifications, substitutions, combinations, and separations.
It should be noted that in this document, having "an" element is not limited to having a single element, but may have one or more elements unless specifically indicated.
In addition, unless specifically stated otherwise, herein, "first," "second," etc. are used for distinguishing between multiple elements having the same name and not for indicating a level, a hierarchy, an order of execution, or a sequence of processing. A "first" element may occur together with a "second" element in the same component, or may occur in different components. The presence of an element with a larger ordinal number does not necessarily indicate the presence of another element with a smaller ordinal number.
In this context, the so-called feature A "or" (or) or "and/or" (and/or) feature B, unless specifically indicated, refers to the presence of B alone, or both A and B; the feature A "and" (and) or "AND" (and) or "and" (and) feature B, means that the nail and the B coexist; the terms "comprising," "including," "having," "containing," and "containing" are intended to be inclusive and not limited to.
Further, in this document, terms such as "upper," "lower," "left," "right," "front," "back," or "between" are used merely to describe relative positions between elements and are expressly intended to encompass situations of translation, rotation, or mirroring. In addition, in this document, unless specifically indicated otherwise, "an element is on another element" or similar recitation does not necessarily mean that the element contacts the other element.
Furthermore, unless specifically described or steps must occur in sequence, the order of the above steps is not limited to the list above and may be changed or rearranged according to the desired design. In addition, the above embodiments may be mixed with each other or other embodiments based on design and reliability, i.e. the technical features of the different embodiments may be freely combined to form more embodiments.
While the foregoing embodiments have been described in some detail for purposes of clarity of understanding, it will be understood that the foregoing embodiments are merely illustrative of the invention and are not intended to limit the invention, and that any modifications, equivalents, improvements, etc. that fall within the spirit and principles of the present disclosure are intended to be included within the scope of the present disclosure.
Claims (10)
1. A differentially output wake-up receiver radio frequency circuit comprising:
a filter matching network based on a first resonator coupled to the antenna for receiving an input signal for providing a relative fractional bandwidth radio frequency passband of less than 4%;
a second resonator-based differential output filter self-mixer coupled to the filter matching network for providing a differential output of the resonant frequency and the antiresonant frequency;
the filter matching network can realize matching at the positive resonant frequency and the anti-resonant frequency of the second resonator by adjusting the resonant frequency and the electromechanical coupling coefficient of the first resonator and the second resonator, so that two radio frequency pass bands with approximately equal gains are obtained, and signals of the two radio frequency pass bands are subjected to opposite self-mixing output through the differential output self-mixer, so that interference signals in the two radio frequency pass bands are counteracted.
2. The differentially output wake-up receiver radio frequency circuit of claim 1, wherein the second resonator has an electromechanical coupling coefficient lower than that of the first resonator, and wherein the resonant frequency is approximately equal to the Q value of the antiresonant frequency.
3. The differentially output wake-up receiver radio frequency circuit of claim 1, wherein the self-mixing coefficients of the two radio frequency pass bands are equal in magnitude and opposite in direction.
4. A differentially output wake-up receiver radio frequency circuit as claimed in any one of claims 1 to 3, said first resonator being selected from a thin film bulk acoustic resonator, a laterally vibrating piezoelectric resonator, a bulk acoustic resonator, a surface acoustic wave resonator, a lamb wave resonator, a shear piezoelectric resonator, a quartz crystal resonator.
5. A differentially output wake-up receiver radio frequency circuit as claimed in any one of claims 1 to 3, said second resonator being selected from the group consisting of a surface acoustic wave resonator, a thin film bulk acoustic resonator, a transverse vibration piezoelectric resonator, a bulk acoustic resonator, a lamb wave resonator, a shear piezoelectric resonator, a quartz crystal resonator, a hollow disk resonator, a FINBAR resonator.
6. The wake-up receiver radio frequency circuit of claim 1, further comprising an LNA module inserted in a preceding stage or a following stage of the filter matching network to improve sensitivity of the system.
7. The differential output wake-up receiver radio frequency circuit of claim 1, wherein the CMOS transistor structure in the differential output filter self-mixer is selected from a single-stage structure, a multi-stage cascade structure or a pseudo-differential multi-stage cascade structure.
8. The differential output wake-up receiver radio frequency circuit of claim 7, wherein the differential output filter is provided by a gate voltage bias circuit to provide a gate dc bias voltage from CMOS transistors in the mixer, or by a drain or source to provide a dc bias voltage.
9. The wake-up receiver radio frequency circuit of claim 1, wherein the input signal from the mixer is input to the drain or source of all or a portion of the transistors through a coupling circuit.
10. The wake-up receiver rf circuit of claim 1, wherein the self-mixing transfer coefficients at the series resonant frequency and the anti-resonant frequency of the second resonator are equal in magnitude and opposite in direction.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202311243820.9A CN116996082B (en) | 2023-09-26 | 2023-09-26 | Differential output wake-up receiver radio frequency circuit |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202311243820.9A CN116996082B (en) | 2023-09-26 | 2023-09-26 | Differential output wake-up receiver radio frequency circuit |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN116996082A CN116996082A (en) | 2023-11-03 |
| CN116996082B true CN116996082B (en) | 2023-12-05 |
Family
ID=88526896
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202311243820.9A Active CN116996082B (en) | 2023-09-26 | 2023-09-26 | Differential output wake-up receiver radio frequency circuit |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN116996082B (en) |
Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101816130A (en) * | 2007-10-03 | 2010-08-25 | Nxp股份有限公司 | Method and system for impulse radio wakeup |
| FR3016102A1 (en) * | 2013-12-31 | 2015-07-03 | Commissariat Energie Atomique | RADIOFREQUENCY RECEPTION CIRCUIT WITH VERY LOW CONSUMPTION |
| CN114614845A (en) * | 2022-04-02 | 2022-06-10 | 中国科学技术大学 | Wake-up receiver |
| CN115765772A (en) * | 2022-10-25 | 2023-03-07 | 天津大学 | Low-power-consumption frequency-mixing priority type broadband receiver front-end module |
| CN116107377A (en) * | 2023-02-10 | 2023-05-12 | 中国科学技术大学 | Circuit for generating bias voltage of passive self-mixer |
| CN116470924A (en) * | 2023-04-18 | 2023-07-21 | 复旦大学 | Broadband full duplex receiver sharing interference elimination circuit |
Family Cites Families (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US9743354B2 (en) * | 2015-01-02 | 2017-08-22 | Texas Instruments Incorporated | Low power harmonic wake up radio |
| WO2020142792A1 (en) * | 2019-01-04 | 2020-07-09 | The Trustees Of Columbia University In The City Of New York | Circuits and methods for wake-up receivers |
| MX2022006571A (en) * | 2019-12-02 | 2022-07-01 | Ericsson Telefon Ab L M | Wakeup communication in a wireless communication system. |
-
2023
- 2023-09-26 CN CN202311243820.9A patent/CN116996082B/en active Active
Patent Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101816130A (en) * | 2007-10-03 | 2010-08-25 | Nxp股份有限公司 | Method and system for impulse radio wakeup |
| FR3016102A1 (en) * | 2013-12-31 | 2015-07-03 | Commissariat Energie Atomique | RADIOFREQUENCY RECEPTION CIRCUIT WITH VERY LOW CONSUMPTION |
| CN114614845A (en) * | 2022-04-02 | 2022-06-10 | 中国科学技术大学 | Wake-up receiver |
| CN115765772A (en) * | 2022-10-25 | 2023-03-07 | 天津大学 | Low-power-consumption frequency-mixing priority type broadband receiver front-end module |
| CN116107377A (en) * | 2023-02-10 | 2023-05-12 | 中国科学技术大学 | Circuit for generating bias voltage of passive self-mixer |
| CN116470924A (en) * | 2023-04-18 | 2023-07-21 | 复旦大学 | Broadband full duplex receiver sharing interference elimination circuit |
Non-Patent Citations (1)
| Title |
|---|
| A Wake-Up Receiver With a Multi-Stage Self-Mixer and With Enhanced Sensitivity When Using an Interferer as Local Oscillator;Vivek Mangal, et al.;《IEEE JOURNAL OF SOLID-STATE CIRCUITS》;第54卷(第3期);第808~820页 * |
Also Published As
| Publication number | Publication date |
|---|---|
| CN116996082A (en) | 2023-11-03 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| EP2242183B1 (en) | High dynamic range time-varying integrated receiver for elimination of off-chip filters | |
| US7809349B1 (en) | Radio frequency filter using intermediate frequency impedance translation | |
| WO2013091351A1 (en) | Transconductance-enhancing passive frequency mixer | |
| EP1958327A2 (en) | Common-gate common-source transconductance stage for rf downconversion mixer | |
| US20060091944A1 (en) | I/Q quadrature demodulator | |
| CN114124123B (en) | Broadband integrated CMOS global feedback receiver front-end circuit | |
| CN113193840B (en) | High-linearity trans-impedance amplifier applied to silent surface filter receiver | |
| Nguyen et al. | Tunable, switchable, high-Q VHF microelectromechanical bandpass filters | |
| CN116996082B (en) | Differential output wake-up receiver radio frequency circuit | |
| WO2016127823A1 (en) | Radio frequency high-q value band-pass filter | |
| CN116996081B (en) | In-band interference suppression wake-up receiver radio frequency circuit | |
| CN116996026B (en) | Filtering self-mixer | |
| CN116996080B (en) | Radio frequency circuit of wake-up receiver | |
| US7613440B2 (en) | Mixer circuit | |
| JP3853604B2 (en) | Frequency conversion circuit | |
| JP4963376B2 (en) | Bandpass filter network and method for bandpass filtering a signal using a plurality of acoustic resonators | |
| US20050264339A1 (en) | Transconductance amplifier with substantially constant resistance and mixer using same | |
| CN110719087B (en) | Reconfigurable harmonic suppression complex filter | |
| CN108540106B (en) | Current mode radio frequency band-pass filter | |
| CN111082778B (en) | Novel high image rejection ratio active CMOS (complementary Metal oxide semiconductor) multiphase filter circuit | |
| KR100689614B1 (en) | Ultra-wideband front-end receiver apparatus and method for transforming signals by using it | |
| Bernier et al. | BAW filters for ultra-low power narrow-band applications | |
| CN116318214A (en) | Broadband anti-blocking radio frequency receiver based on N-path filtering technology | |
| Nguyen et al. | MP 4.7 Tunable, Switchable, High-Q VHF Microelectromechanical Bandpass Filters | |
| CN112436810A (en) | Low noise amplifier, receiver and electronic equipment based on inverter |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |