CN116996080B - Radio frequency circuit of wake-up receiver - Google Patents
Radio frequency circuit of wake-up receiver Download PDFInfo
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- CN116996080B CN116996080B CN202311243355.9A CN202311243355A CN116996080B CN 116996080 B CN116996080 B CN 116996080B CN 202311243355 A CN202311243355 A CN 202311243355A CN 116996080 B CN116996080 B CN 116996080B
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
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Abstract
The present disclosure provides a wake-up receiver radio frequency circuit comprising: the filter based on the first resonator is matched with the network, and the filter based on the second resonator is a self-mixer. A filter matching network coupled to the antenna for providing a single radio frequency passband of less than 4% of the relative fractional bandwidth; the filtering self-mixer is connected with the filtering matching network and is used for providing a plurality of extremely narrow radio frequency pass bands; the frequency interval is regulated and controlled by changing the thicknesses of the substrates of the filtering matching network and the filtering self-mixer, so that the radio frequency passband bandwidth of the filtering matching network is smaller than the frequency interval between different passbands of the filtering self-mixer.
Description
Technical Field
The present disclosure relates to the field of radio frequency wireless communications, and in particular, to a wake-up receiver radio frequency circuit.
Background
The wake-up receiver can monitor the channel with extremely low power consumption, and wake-up the main receiver when the wake-up receiver receives the wake-up signal, so that the standby power consumption of the wireless communication system can be reduced.
With the development of wireless communication technology, wake-up receivers require lower power consumption, higher sensitivity and higher interference immunity. In order to eliminate the high power consumption (> 20 microwatts) introduced by the oscillator, low power wake-up receivers often employ self-mixing architectures to down-convert the radio frequency signals, thereby reducing the system power consumption below microwatts. The existing self-mixer can down-convert all input signals in the front-stage passband to baseband, and the self-mixing output spectrum of interference and signals can be aliased and indistinguishable at baseband. Therefore, the antijamming capability of wake-up receivers based on self-mixing architecture is in need of improvement.
To improve the anti-interference capability of the wake-up receiver, the probability of the interference signal entering the wake-up receiver is reduced, and the most effective way is to reduce the radio frequency passband bandwidth of the wake-up receiver. The rf passband bandwidth of the existing wake-up receiver is mainly determined by the filter matching network, and its core element is an off-chip high Q value inductor or rf microelectromechanical resonator (FBAR SAW, etc.). Because the Q values of the rf inductor and the microelectromechanical resonator are limited (the inductor is about 80 and the resonator is about 1000), the relative fractional bandwidth of the existing filter matching network is limited to over 0.4% and cannot meet the requirement of the wake-up receiver for extremely narrow bandwidth.
Disclosure of Invention
Based on the above problems, the present disclosure provides a wake-up receiver radio frequency circuit to alleviate the above technical problems in the prior art, where the relative fractional bandwidth of the wake-up receiver radio frequency circuit is lower than 0.01%, and meanwhile, the wake-up receiver radio frequency circuit has better in-band interpolation loss and out-of-band suppression, so as to greatly improve the anti-interference performance of the wake-up receiver.
Technical scheme (one)
The present disclosure provides a wake-up receiver radio frequency circuit comprising: the filter based on the first resonator is matched with the network, and the filter based on the second resonator is a self-mixer. A filter matching network coupled to the antenna for providing a single radio frequency passband of less than 4% of the relative fractional bandwidth; the filtering self-mixer is connected with the filtering matching network and is used for providing a plurality of extremely narrow radio frequency pass bands; the frequency interval is regulated and controlled by changing the thicknesses of the substrates of the filtering matching network and the second resonator, so that the radio frequency passband bandwidth of the filtering matching network is smaller than the frequency interval between different passbands of the filtering self-mixer.
According to the embodiment of the disclosure, the input impedance of the filtering self-mixer at different frequencies can be adjusted by adjusting and controlling the center frequencies and the coupling capacitances of the first resonator and the second resonator, so that the in-band interpolation loss and the out-of-band suppression of the radio frequency circuit of the wake-up receiver are adjusted and controlled.
According to an embodiment of the present disclosure, the radio frequency passband of the wake-up receiver radio frequency circuit is below a relative fractional bandwidth of 0.1%.
According to an embodiment of the present disclosure, the first resonator is selected from a thin film bulk acoustic resonator, a laterally vibrating piezoelectric resonator, a bulk acoustic resonator, a surface acoustic wave resonator, a lamb wave resonator, a shear piezoelectric resonator, and a quartz crystal resonator.
According to an embodiment of the present disclosure, the second resonator is selected from the group consisting of a higher harmonic bulk acoustic wave resonator, a single crystal piezoelectric thin film resonator, a transverse overmode acoustic wave resonator, a piezoelectric thin film resonator on insulator, a hollow disk resonator, and a FINBAR resonator.
According to the embodiment of the disclosure, the wake-up receiver radio frequency circuit further comprises an LNA module inserted in a front stage or a rear stage of the filtering matching network to improve the sensitivity of the system.
According to the embodiment of the disclosure, the wake-up receiver radio frequency circuit further comprises a band reject filter inserted in a front stage or a rear stage of the filtering matching network to further inhibit the adjacent passband of the filtering self-mixer, thereby improving the anti-interference capability.
According to embodiments of the present disclosure, wake-up receiver radio frequency circuits may employ resonator-based matching circuits or employ inductive matching networks in cascade with resonator-based narrowband filters.
According to an embodiment of the present disclosure, the filtering self-mixer operates at a resonant frequency or an antiresonant frequency of the second resonator.
According to the embodiment of the disclosure, the wake-up receiver radio frequency circuit selects a series resonance point or a parallel resonance point of the first resonator and the second resonator as an operating frequency of the wake-up receiver.
(II) advantageous effects
As can be seen from the above technical solutions, the wake-up receiver radio frequency circuit of the present disclosure has at least one or a part of the following advantages:
(1) The filter matching network based on the high FoM micro-electromechanical resonator is used for cascading with the filter self-mixer based on the high Q micro-electromechanical resonator, and the single radio frequency passband characteristic of the high FoM resonator and the multi-passband and ultra-narrow bandwidth characteristics of the high Q micro-electromechanical resonator are utilized to ensure that the radio frequency circuit of the wake-up receiver only keeps one ultra-narrow radio frequency passband, so that the anti-interference capability of the wake-up receiver is greatly improved;
(2) The filter self-mixer based on the high Q value micro-electromechanical resonator is adopted, and the sharp change of the output impedance of the filter self-mixer under different frequencies is utilized, so that the filter matching network in the radio frequency passband and out-of-band has large load impedance difference, and better in-band insertion loss and out-of-band rejection are obtained;
(3) The adopted filtering matching network and the filtering self-mixer can reduce the insertion loss in the radio frequency passband and inhibit the adjacent radio frequency passband by optimizing the topological structures of the first micro-electromechanical resonator and the second micro-electromechanical resonator. Thereby further optimizing the in-band impairments and out-of-band rejection capabilities of the radio frequency circuit.
Drawings
Fig. 1 is a schematic diagram of a wake-up receiver radio frequency circuit according to an embodiment of the present disclosure.
Fig. 2 is a schematic diagram of a circuit composition of a filtering self-mixer according to an embodiment of the disclosure.
Detailed Description
The present disclosure provides a wake-up receiver radio frequency circuit comprising: matching circuits based on radio frequency microelectromechanical resonators, and filtering self-mixers based on high Q radio frequency microelectromechanical resonators. Unlike existing circuit structures, the wake-up receiver rf circuit of the present disclosure employs a filtering matching network with a first rf microelectromechanical resonator as a core element, and a filtering self-mixer based on a second microelectromechanical resonator. Whether or not to introduce a radio frequency Low Noise Amplifier (LNA) may be selected based on power consumption budget and sensitivity requirements. The first resonator may be a radio frequency microelectromechanical resonator such as an FBAR (film bulk acoustic resonator), and the filtering is matched with a single radio frequency passband having a higher sensitivity and a relative fractional bandwidth lower than 4% based on a higher FoM value (> 100) and a Q value greater than 1000. The second resonator can adopt a high-Q value resonator of an HBAR (high-order harmonic bulk acoustic wave resonator), and the resonator is characterized by extremely high Q value (> 20000), relatively low FoM value and a plurality of resonance modes with equal frequency intervals, and the frequency intervals of the HBAR are usually in the order of 10 MHz. The filtered self-mixer also has a plurality of extremely narrow radio frequency pass bands based on the extremely high Q of the second microelectromechanical resonator and the characteristics of the multiple resonant modes. The bandwidth of the filtering matching network can be smaller than the frequency interval between different pass bands of the filtering self-mixer by adjusting and controlling the frequency interval through changing the thickness of the substrate. The input impedance of the filtering self-mixer at different frequencies can be adjusted by adjusting and controlling the center frequencies and the coupling capacitances of the first resonator and the second resonator, so that the in-band insertion loss and the out-of-band suppression of the radio frequency circuit of the wake-up receiver are adjusted and controlled. Through the specific arrangement, after the filtering matching network and the filtering self-mixer are cascaded, only one extremely narrow radio frequency passband (< 0.1%) is reserved, and meanwhile, higher out-of-band rejection, lower insertion loss and higher sensitivity of the wake-up receiver are obtained.
Existing wake-up receiver radio frequency circuit structures include filter matching circuits, radio frequency self mixers, which may choose whether to introduce a radio frequency Low Noise Amplifier (LNA) based on power consumption budget and sensitivity requirements. Since the bandwidth of the existing radio frequency self-mixer and LNA is high, the bandwidth of the wake-up receiver architecture is mainly dependent on the Q of the filter matching circuit, especially its core components. Because the Q of a rf microelectromechanical resonator (off-chip inductance about 80 and resonator about 1000), the Q of a filter matching network based on a single inductor/resonator structure is limited. While the use of higher order filtering can reduce the system bandwidth, it can greatly increase the loss and module volume. Therefore, the existing structure is difficult to realize extremely low bandwidth and cannot meet the severe anti-interference requirement of the wake-up receiver. Thus, the present disclosure provides a wake-up receiver radio frequency circuit.
For the purposes of promoting an understanding of the principles and advantages of the disclosure, reference will now be made to the embodiments illustrated in the drawings and specific language will be used to describe the same.
In an embodiment of the present disclosure, there is provided a wake-up receiver radio frequency circuit, as shown in fig. 1, including: the filter based on the first resonator is matched with the network, and the filter based on the second resonator is a self-mixer. Wherein:
a first resonator-based filter matching network coupled to the antenna for providing a single radio frequency passband of less than 4% of the relative fractional bandwidth;
a second resonator-based filtering self-mixer coupled to the filtering matching network for providing a plurality of extremely narrow radio frequency pass bands;
the frequency spacing is regulated by changing the thicknesses of the substrates of the filter matching network and the filter self-mixer so that the radio frequency passband bandwidth of the filter matching network is smaller than the frequency spacing between different passbands of the filter self-mixer. The best matching frequency of the filter matching network is the operating frequency of the wake-up receiver.
According to embodiments of the present disclosure, the topology of the filter matching network includes, but is not limited to: a transformer type matching network based on a resonator, an L type matching network based on the resonator, a T type matching network based on the resonator, a pi type matching network based on the resonator, a narrow-band filter cascade based on the inductor and the like.
According to the embodiment of the disclosure, the input impedance of the filtering self-mixer at different frequencies can be adjusted by adjusting and controlling the center frequencies and the coupling capacitances of the first resonator and the second resonator, so that the in-band interpolation loss and the out-of-band suppression of the radio frequency circuit of the wake-up receiver are adjusted and controlled.
According to the embodiment of the disclosure, by utilizing the characteristics of a single-passband narrow band of a filtering matching network based on a radio frequency micro-electromechanical resonator and the characteristics of a multi-passband of a filtering self-mixer based on a high Q value resonator, the wake-up receiver can have a very narrow radio frequency passband (< 0.1% relative fractional bandwidth), and simultaneously obtain higher out-of-band rejection, lower insertion loss and higher sensitivity.
According to an embodiment of the present disclosure, the filter matching network comprises at least one microelectromechanical resonator, for example, the first resonator is of a type selected from the group consisting of a Film Bulk Acoustic Resonator (FBAR), a laterally vibrating piezoelectric resonator, a bulk acoustic resonator, a surface acoustic wave resonator, a lamb wave resonator, a shear piezoelectric resonator, and a quartz crystal resonator.
In an embodiment of the present disclosure, as shown in fig. 2, a filtered self-mixer includes: input signal terminal IN, energy detection circuit unit 10, bias voltage unit, coupling branching unit, microelectromechanical resonator branch. The input signal end IN is used for receiving a wake-up signal and an interference signal as input signals; the energy detection circuit unit 10 includes at least one CMOS tube, preferably 30 to 50 CMOS tubes, four CMOS tubes in fig. 2, four CMOS tubes of an N-type CMOS tube 11, a P-type CMOS tube 12, an N-type CMOS tube 13, and a P-type CMOS tube 14, which are sequentially connected. The energy detection circuit unit 10 is used for mixing input signals through the secondary effect of the CMOS tube and outputting baseband signals; the bias voltage unit is used for providing the grid voltage of the CMOS tube so as to adjust the channel impedance of the CMOS tube; the coupling branch unit is arranged between the input signal end and the energy detection circuit unit, and is used for coupling the input signal to the drain electrodes or the source electrodes of the CMOS tubes in the energy detection circuit unit, and as shown in fig. 2, the input signal is respectively coupled to the drain electrodes of the four CMOS tubes through a coupling capacitor C1 and a coupling capacitor C2; the micro-electromechanical resonator branch is arranged between the input signal end IN and the bias voltage unit and the energy detection circuit unit 10, and can output different grid signals under different frequencies to adjust the secondary effect, so as to realize the filtering of interference signals IN the input signals. A coupling capacitor C is also connected between the signal output terminal OUT and the source of the N-type CMOS tube 11 C And the sources of the N-type CMOS tube 11 and the P-type CMOS tube 12 are connected with a coupling capacitor C C And is grounded. The source of the P-type CMOS transistor 14 is connected to a common mode level VC.
According to the embodiment of the disclosure, the energy detection circuit is a triode type energy detection circuit, and the CMOS tube in the energy detection circuit unit is selected from an N type CMOS tube and a P type CMOS tube; the CMOS tube arrangement in the energy detection circuit unit includes a single-stage form, a multi-stage cascade form or a multi-stage cascade form of pseudo-differential form. When both the N-type CMOS transistor and the P-type CMOS transistor are present, the N-type CMOS transistor and the P-type CMOS transistor are alternately connected, for example, in the form of N-P-N-P or P-N-P-N connection.
According to an embodiment of the disclosure, the bias voltage unit comprises at least one bias voltage branch, and each bias voltage branch comprises a bias voltage source and a bias resistor which are sequentially connected. As shown in fig. 2, the bias voltage unit includes two bias voltage branches, which are bias voltage sources V for providing gate voltages to two N-type CMOS transistors 11 and 13 GN And bias voltage source V GN Connected bias resistor R B1 The method comprises the steps of carrying out a first treatment on the surface of the And a bias voltage source V providing a gate voltage to the two P-type CMOS transistors 12, 14 GP And bias voltage source V GP Connected bias resistor R B2 。
According to an embodiment of the present disclosure, the coupling-leg unit comprises at least one coupling leg, each coupling leg comprising a coupling capacitance connected to the input signal terminal, said coupling capacitance being connected to the drain or source of the corresponding CMOS transistor. As shown IN fig. 2, the coupling-arm unit includes two coupling arms, one of which has one end connected to the input signal terminal IN and the other end connected to the drains of the N-type CMOS pipe 11 and the P-type CMOS pipe 12 through the coupling capacitor C1; the other coupling branch is connected to the input signal terminal IN at one end and to the drains of the N-type CMOS tube 13 and the P-type CMOS tube 14 via a coupling capacitor C2 at the other end.
According to an embodiment of the present disclosure, the microelectromechanical resonator branch includes a microelectromechanical resonator 21, a blocking capacitor 22. One end of the microelectromechanical resonator 21 is connected to the input signal terminal IN, and the other end is connected to the gate of the CMOS pipe, as shown IN fig. 2, and the other end of the microelectromechanical resonator 21 is connected to the gates of the N-type CMOS pipe 11, 13; one end of the blocking capacitor 22 is connected with the micro-electromechanical resonator 21, and the two ends are connected to the grid electrode of the CMOS tube for isolating the direct current level of the CMOS tube. As shown in fig. 2, the other end of the blocking capacitor 22 is connected to the gate of the P-type CMOS transistor 12, 14.
According to the embodiment of the disclosure, when the frequency of the interference signal in the input signal is far away from the anti-resonant frequency of the microelectromechanical resonator 21, the microelectromechanical resonator 21 corresponds to an equivalent capacitance, and the capacitance of the equivalent capacitance is adjusted by adjusting the geometry of the resonator so as to adjust the size of the gate signal coupled to the gate of the CMOS transistor, so that the secondary effects of the gate and the drain or the drain of the transistor cancel each other, and thus the baseband signal is not output.
As shown in fig. 2, the number of stages of the self-mixer is 4 (i.e. the number of cascaded CMOS transistors is 4), and other stages, preferably 30 stages or 40 stages, may be used in practical use, and a pseudo-differential cascade mode may also be used. A microelectromechanical resonator 21 is introduced between the gate and drain of the CMOS transistor and adjusts and blocks the channel resistance of the transistor by means of a bias resistor and a blocking capacitor. The rf microelectromechanical resonator 21 exhibits high-impedance characteristics near the anti-resonant frequency, and the filtered self-mixer is equivalent to a conventional self-mixer. Outside the antiresonant frequency, the impedance of the microelectromechanical resonator decreases, which reduces the input impedance from the mixer, destroying the matching conditions with the previous stage, reducing the input signal size from the mixer. Thus, the input signal of the same magnitude, the output signal generated by the input at the antiresonant frequency is larger than the other frequencies, and the self-mixer achieves the filtering effect. Because the Q of the microelectromechanical resonator is higher at the antiresonant frequency, a lower passband bandwidth is achieved. At a distance from the antiresonance frequency, the resonator is equivalent to a capacitor, and the capacitance of the equivalent capacitor can be adjusted by adjusting the geometry of the resonator. By adjusting the capacitance value, the magnitude of the signal coupled to the gate of the CMOS transistor can be adjusted, so that the secondary effects of the gate and the drain of the transistor are mutually offset, and the output signal of the baseband is not generated. The input signal at a distance from the antiresonant frequency produces little output signal.
According to an embodiment of the present disclosure, a bias voltage source (V GN、 V GP ) The gate dc bias voltage may be provided by a gate voltage bias circuit or may be provided by the drain or source of a transistor.
According to an embodiment of the present disclosure, the filtered self-mixer comprises at least one high Q resonator, for example, the second resonator is of a type selected from the group consisting of a higher harmonic bulk acoustic wave resonator (HBAR), a single crystal piezoelectric thin film resonator, a transverse overdie acoustic wave resonator, a piezoelectric thin film resonator on insulator, a hollow disk resonator, and a FINBAR resonator.
The structure of the filtering matching network is a transformer type matching network based on a micro-electromechanical resonator, and matching networks with other structures can be adopted; and a structure of cascade connection of a matching network based on off-chip high Q value inductance and a narrow-band filter based on a micro-electromechanical resonator can also be adopted.
According to embodiments of the present disclosure, two or more resonators used above may be fabricated either monolithically or separately.
According to the embodiment of the disclosure, a radio frequency low noise amplifier, a band-stop filter and other modules can be added for waking up a radio frequency circuit of a receiver according to actual requirements.
According to the embodiment of the disclosure, the wake-up receiver radio frequency circuit further comprises an LNA module inserted in a front stage or a rear stage of the filter matching network to improve the sensitivity of the system.
According to the embodiment of the disclosure, the wake-up receiver radio frequency circuit may further include a band reject filter inserted in a front stage or a rear stage of the filtering matching network to further suppress the adjacent passband of the filtering self-mixer, thereby improving the anti-interference capability.
According to embodiments of the present disclosure, resonator-based matching circuits or cascaded with resonator-based narrowband filters using inductive matching networks may be employed.
According to an embodiment of the present disclosure, the filtering self-mixer operates at a resonant frequency or an antiresonant frequency of the second resonator.
According to an embodiment of the present disclosure, a series resonance point or a parallel resonance point of the first resonator and the second resonator is selected as an operating frequency of the wake-up receiver.
After simulation of the radio frequency circuit of the wake-up receiver, the radio frequency bandwidth of the radio frequency circuit of the wake-up receiver is only 194KHz, the filtering Q value of the radio frequency circuit of the wake-up receiver is larger than 12000, and the radio frequency circuit of the wake-up receiver has strong out-of-band rejection capability (rejection of the center frequency of 1MHz frequency offset is more than 15 dB) and can greatly improve the anti-interference capability of the wake-up receiver.
Setting parameters such as the piezoelectric film product of the second resonator to enable the second resonator to be an expected working frequency at a series resonance frequency or a parallel resonance frequency; the geometry of the first resonator is then adjusted, which achieves an optimal match with the filtered self-mixer at the operating frequency. The substrate of the second resonator is adjusted, the interval between the adjacent pass bands of the self-mixer can be adjusted, and the thickness of the substrate is properly adjusted, so that the suppression of the adjacent pass bands of the working frequency of the self-mixer can be realized. Through careful design, the wake-up receiver can have an extremely narrow radio frequency passband (< 0.1%), while achieving higher out-of-band rejection, lower insertion loss, and higher sensitivity.
Thus, embodiments of the present disclosure have been described in detail with reference to the accompanying drawings. It should be noted that, in the drawings or the text of the specification, implementations not shown or described are all forms known to those of ordinary skill in the art, and not described in detail. Furthermore, the above definitions of the elements and methods are not limited to the specific structures, shapes or modes mentioned in the embodiments, and may be simply modified or replaced by those of ordinary skill in the art.
From the foregoing description, those skilled in the art will readily recognize that the present disclosure wakes up the receiver radio frequency circuitry.
In summary, the present disclosure provides a wake-up receiver rf circuit having an extremely narrow rf passband (< 0.1%), while achieving higher out-of-band rejection, lower insertion loss, and higher sensitivity of the wake-up receiver.
It should also be noted that the foregoing describes various embodiments of the present disclosure. These examples are provided to illustrate the technical content of the present disclosure, and are not intended to limit the scope of the claims of the present disclosure. A feature of one embodiment may be applied to other embodiments by suitable modifications, substitutions, combinations, and separations.
It should be noted that in this document, having "an" element is not limited to having a single element, but may have one or more elements unless specifically indicated.
In addition, unless specifically stated otherwise, herein, "first," "second," etc. are used for distinguishing between multiple elements having the same name and not for indicating a level, a hierarchy, an order of execution, or a sequence of processing. A "first" element may occur together with a "second" element in the same component, or may occur in different components. The presence of an element with a larger ordinal number does not necessarily indicate the presence of another element with a smaller ordinal number.
Further, in this document, terms such as "upper," "lower," "left," "right," "front," "back," or "between" are used merely to describe relative positions between elements and are expressly intended to encompass situations of translation, rotation, or mirroring. In addition, in this document, unless specifically indicated otherwise, "an element is on another element" or similar recitation does not necessarily mean that the element contacts the other element.
Furthermore, unless specifically described or steps must occur in sequence, the order of the above steps is not limited to the list above and may be changed or rearranged according to the desired design. In addition, the above embodiments may be mixed with each other or other embodiments based on design and reliability, i.e. the technical features of the different embodiments may be freely combined to form more embodiments.
While the foregoing embodiments have been described in some detail for purposes of clarity of understanding, it will be understood that the foregoing embodiments are merely illustrative of the invention and are not intended to limit the invention, and that any modifications, equivalents, improvements, etc. that fall within the spirit and principles of the present disclosure are intended to be included within the scope of the present disclosure.
Claims (9)
1. A wake-up receiver radio frequency circuit comprising:
a first resonator based filter matching network coupled to the antenna for providing a single radio frequency passband of less than 4% of the relative fractional bandwidth;
a second resonator-based filtering self-mixer coupled to the filtering matching network for providing a plurality of extremely narrow radio frequency pass bands;
the frequency interval is regulated and controlled by changing the thicknesses of the substrates of the filtering matching network and the second resonator, so that the radio frequency passband bandwidth of the filtering matching network is smaller than the frequency interval between different passbands of the filtering self-mixer; the input impedance of the filtering self-mixer at different frequencies is adjusted by adjusting and controlling the center frequencies and the coupling capacitances of the first resonator and the second resonator, so that the in-band insertion loss and the out-of-band suppression of the radio frequency circuit of the wake-up receiver are adjusted and controlled.
2. The wake-up receiver radio frequency circuit of claim 1, wherein the radio frequency passband is less than 0.1% of the relative fractional bandwidth.
3. The wake-up receiver radio frequency circuit of any of claims 1-2, the first resonator being selected from the group consisting of a thin film bulk acoustic resonator, a laterally vibrating piezoelectric resonator, a bulk acoustic resonator, a surface acoustic wave resonator, a lamb wave resonator, a shear piezoelectric resonator, and a quartz crystal resonator.
4. The wake-up receiver radio frequency circuit of any of claims 1-2, the second resonator being selected from the group consisting of a higher harmonic bulk acoustic wave resonator, a single crystal piezoelectric thin film resonator, a transverse over-die acoustic wave resonator, a piezoelectric thin film resonator on insulator, a hollow disk resonator, and a FINBAR resonator.
5. The wake-up receiver radio frequency circuit of claim 1, further comprising an LNA module inserted in a preceding stage or a succeeding stage of the filter matching network to improve sensitivity of a system.
6. The wake-up receiver radio frequency circuit of claim 1, further comprising a band reject filter inserted in a preceding stage or a succeeding stage of the filter matching network to further reject filter self-mixer adjacent pass-bands to improve immunity to interference.
7. The wake-up receiver radio frequency circuit of claim 1, wherein a resonator-based matching circuit or an inductive matching network is used in cascade with a resonator-based narrowband filter.
8. The wake-up receiver radio frequency circuit of claim 1, the filtering self-mixer operating at a resonant or anti-resonant frequency of the second resonator.
9. The wake-up receiver radio frequency circuit of claim 1, wherein a series resonance point or a parallel resonance point of the first resonator and the second resonator is selected as an operating frequency of the wake-up receiver.
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Citations (8)
| Publication number | Priority date | Publication date | Assignee | Title |
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| WO2012092516A2 (en) * | 2010-12-29 | 2012-07-05 | Secureall Corporation | Methods and systems for interference rejection for low signals |
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