CN116827133A - CLLC resonant converter based on variable inductance and control method thereof - Google Patents

CLLC resonant converter based on variable inductance and control method thereof Download PDF

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Publication number
CN116827133A
CN116827133A CN202310755684.5A CN202310755684A CN116827133A CN 116827133 A CN116827133 A CN 116827133A CN 202310755684 A CN202310755684 A CN 202310755684A CN 116827133 A CN116827133 A CN 116827133A
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CN
China
Prior art keywords
switching tube
side resonance
primary side
resonant converter
direct current
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Pending
Application number
CN202310755684.5A
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Chinese (zh)
Inventor
陈兆岭
陈成友
方伟光
凌辉
张群峰
王传斌
王致远
秦鹏
徐焱
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Jiangsu University
Jiangsu Zhenan Power Equipment Co Ltd
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Jiangsu University
Jiangsu Zhenan Power Equipment Co Ltd
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Priority to CN202310755684.5A priority Critical patent/CN116827133A/en
Publication of CN116827133A publication Critical patent/CN116827133A/en
Pending legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33573—Full-bridge at primary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/01—Resonant DC/DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention discloses a CLLC resonant converter based on a variable inductor and a control method thereof, wherein the CLLC resonant converter comprises a primary side resonant inductor, a primary side resonant capacitor, an equivalent excitation inductor, a transformer, a secondary side resonant capacitor and a secondary side resonant inductor; the primary side resonance inductance and the secondary side resonance inductance are variable inductances; the primary side resonance inductor and the primary side resonance capacitor are connected in series to the primary side of the transformer, and the equivalent excitation inductor is connected in parallel to the primary side of the transformer; the direct current source is also included; the primary side resonance inductor, the secondary side resonance inductor and the direct current source are sequentially connected to form a complete loop; the primary side resonance inductance and the secondary side resonance inductance are controlled by the output current of the direct current source. The invention can expand the voltage gain range, reduce the frequency modulation range and improve the electromagnetic compatibility of the traditional CLLC resonant converter while ensuring the excellent characteristics of the CLLC resonant converter.

Description

CLLC resonant converter based on variable inductance and control method thereof
Technical Field
The invention relates to the technical field of power electronic power conversion, in particular to a CLLC resonant converter based on variable inductance and a control method thereof.
Background
The CLLC resonant converter is arranged between the direct current bus and the energy storage equipment, can realize the bidirectional transmission of electric energy between the direct current bus and the energy storage equipment, and can realize soft switching in a full-load range, so that the transmission efficiency of the electric energy is greatly improved, and the CLLC resonant converter is widely applied to the fields of micro-grids and electric automobiles.
In a conventional CLLC resonant converter, in order to obtain a wide voltage gain, the wide voltage gain is generally achieved by increasing a frequency modulation range or a phase shift range of the resonant converter, which is easy to cause the CLLC resonant converter to lose a Zero Voltage Switch (ZVS) or a Zero Current Switch (ZCS), increase power loss, and damage the CLLC resonant converter when a phase shift angle is too large, two switches on the same bridge arm up and down are directly connected.
In order to solve the above problems, researchers have proposed a method of combining Pulse Width Modulation (PWM) control with variable frequency control to expand the gain range of the output voltage of the CLLC resonant converter. However, the control of the CLLC resonant converter by the method is very complex, the fault tolerance rate of a control system is low, and faults are easy to occur.
In order to ensure the characteristics of the CLLC resonant converter, expand the voltage gain range of the CLLC resonant converter, reduce the frequency modulation range of the CLLC resonant converter and improve the electromagnetic compatibility of the CLLC resonant converter, the invention provides a variable inductance-based CLLC resonant converter and a control method thereof.
Disclosure of Invention
The invention provides a CLLC resonant converter based on a variable inductance and a control method thereof, which can expand the voltage gain range of the CLLC resonant converter, reduce the frequency modulation range of the CLLC resonant converter and improve the electromagnetic compatibility of the CLLC resonant converter while ensuring the characteristics of the CLLC resonant converter.
In order to achieve the above purpose, the invention adopts the following technical scheme:
in a first aspect, the present invention provides a CLLC resonant converter based on variable inductance, including a primary full-bridge circuit, a resonant cavity circuit, and a secondary full-bridge circuit connected in sequence and disposed between a dc bus and an energy storage power source, the resonant cavity circuit comprising: primary side resonance inductance, primary side resonance capacitance, equivalent excitation inductance, transformer, secondary side resonance capacitance and secondary side resonance inductance; the primary side resonance inductance and the secondary side resonance inductance are variable inductances;
the primary side resonance inductor and the primary side resonance capacitor are arranged at the primary side of the transformer in series, and the equivalent excitation inductor is connected at the primary side of the transformer in parallel; the secondary side resonance capacitor and the secondary side resonance inductor are connected in series to the secondary side of the transformer;
the direct current source is also included; the primary side resonance inductor, the secondary side resonance inductor and the direct current source are sequentially connected to form a complete loop;
the primary side resonance inductor and the secondary side resonance inductor are controlled by the output current of the direct current source.
In one possible implementation manner, the primary full-bridge circuit comprises a primary filter capacitor, a first switch tube, a second switch tube, a third switch tube and a fourth switch tube;
the primary side filter capacitor is connected in parallel with two ends of the direct current bus;
the positive electrode of the direct current bus is connected with the drain electrode of the first switching tube and the drain electrode of the third switching tube, the negative electrode of the direct current bus is connected with the source electrode of the second switching tube and the source electrode of the fourth switching tube, the source electrode of the first switching tube is connected with the drain electrode of the second switching tube, and the source electrode of the third switching tube is connected with the drain electrode of the fourth switching tube;
one end of the primary side resonance inductor is connected with the source electrode of the first switching tube and the drain electrode of the second switching tube, the other end of the primary side resonance inductor is connected with one end of the primary side resonance capacitor, the other end of the primary side resonance capacitor is connected with one end of the equivalent excitation inductor and one end of the primary side of the transformer, and the other end of the equivalent excitation inductor is connected with the other end of the primary side of the transformer, and the source electrode of the third switching tube is connected with the drain electrode of the fourth switching tube.
In one possible implementation manner, the secondary full-bridge circuit comprises a secondary filter capacitor, a fifth switching tube, a sixth switching tube, a seventh switching tube and an eighth switching tube;
the secondary side filter capacitor is connected in parallel with two ends of the energy storage power supply;
the positive electrode of the energy storage power supply is connected with the drain electrode of the fifth switching tube and the drain electrode of the seventh switching tube, the negative electrode of the energy storage power supply is connected with the source electrode of the sixth switching tube and the source electrode of the eighth switching tube, the source electrode of the fifth switching tube is connected with the drain electrode of the sixth switching tube, and the source electrode of the seventh switching tube is connected with the drain electrode of the eighth switching tube;
one end of the secondary side resonance inductor is connected with the source electrode of the fifth switching tube and the drain electrode of the sixth switching tube, the other end of the secondary side resonance inductor is connected with one end of the secondary side resonance capacitor, the other end of the secondary side resonance capacitor is connected with one end of the secondary side of the transformer, and the other end of the secondary side of the transformer is connected with the source electrode of the seventh switching tube and the drain electrode of the eighth switching tube.
In one possible implementation, the resonant converter includes a forward operating state and a reverse operating state; the forward running state is a state that electric energy is transmitted from the direct current power supply to the energy storage power supply through the primary full-bridge circuit, the resonant cavity circuit and the secondary full-bridge circuit in sequence; the reverse running state is a state that electric energy is transmitted from the energy storage power supply to the direct current power supply through the secondary side full-bridge circuit, the resonant cavity circuit and the primary side full-bridge circuit in sequence;
when the forward running state is adopted, driving signals of the first switching tube and the second switching tube are complementary, driving signals of the third switching tube and the fourth switching tube are complementary, driving signals of the first switching tube and the fourth switching tube are identical, and driving signals of the second switching tube and the third switching tube are identical; the fifth switching tube, the sixth switching tube, the seventh switching tube and the eighth switching tube have no driving signals, the primary full-bridge circuit works in an inversion state, and the secondary full-bridge circuit works in a rectification state;
in the reverse running state, the driving signals of the fifth switching tube and the sixth switching tube are complementary, and the driving signals of the seventh switching tube and the eighth switching tube are complementary; the driving signals of the fifth switching tube and the eighth switching tube are the same, and the driving signals of the sixth switching tube and the seventh switching tube are the same; the first switching tube, the second switching tube, the third switching tube and the fourth switching tube have no driving signals, the primary full-bridge circuit works in a rectifying state, and the secondary full-bridge circuit works in an inversion state.
In a second aspect, the present invention provides a control method of a CLLC resonant converter based on variable inductance, comprising: acquiring a voltage fluctuation value of the direct current bus within a preset time period;
determining a first scheme or a second scheme as a scheme for adjusting the output of the resonant converter according to the voltage fluctuation value and a preset threshold value; the first scheme is to adjust the output current of the direct current source only, and the second scheme is to adjust the output current of the direct current source and the switching frequency of the resonant converter simultaneously.
In one possible implementation manner, the determining the first scheme or the second scheme according to the magnitude of the voltage fluctuation value and a preset threshold value as a scheme for adjusting the output of the resonant converter specifically includes:
when the voltage fluctuation value of the direct current bus is smaller than the preset threshold value, the first scheme is used as a scheme for adjusting the output of the resonant converter;
and when the voltage fluctuation value of the direct current bus is larger than the preset threshold value, taking the second scheme as a scheme for adjusting the output of the resonant converter.
In one possible implementation manner, the adjusting the output current of the direct current source includes:
obtaining the output voltage of the resonant converter;
when the output voltage is larger than the target voltage, reducing the output current of the direct current source to reduce the output voltage;
and when the output voltage is smaller than the target voltage, increasing the output current of the direct current source to increase the output voltage.
In one possible implementation manner, the adjusting the output current of the direct current source and the switching frequency of the resonant converter at the same time specifically includes:
obtaining the output voltage and the switching frequency of the resonant converter;
when the output voltage is larger than a target voltage, reducing the output current of the direct current source to a minimum value, and then increasing the switching frequency to reduce the output voltage;
and when the output voltage is smaller than the target voltage, increasing the output current of the direct current source to a maximum value, and then reducing the switching frequency to increase the output voltage.
According to the CLLC resonant converter based on the variable inductor, electric isolation is achieved between the primary side and the secondary side of the CLLC resonant converter based on the variable inductor, and the variable inductor replaces the primary side resonant inductor and the secondary side resonant inductor with fixed values in the prior art, so that the output voltage gain of the CLLC resonant converter can be adjusted by adjusting the inductance of the primary side resonant inductor and the secondary side resonant inductor; the primary side resonance inductance, the secondary side resonance inductance and the direct current source are sequentially connected to form a complete loop, so that the control mode of the CLLC resonance converter is changed from the traditional frequency modulation or phase-shifting frequency modulation control mode into a inductance modulation mode, namely, the inductance values of the primary side resonance inductance and the secondary side resonance inductance can be adjusted only by adjusting the output current of the direct current source, thereby enabling the control mode to be simpler; after the inductance values of the primary side resonance inductance and the secondary side resonance inductance are adjusted to limit values, the switching frequency of the resonance converter can be adjusted to further realize the adjustment of the bidirectional wide voltage gain of the converter, so that the compatibility of the resonance converter is improved. The invention can ensure the characteristics of the CLLC resonant converter, expand the voltage gain range of the CLLC resonant converter, reduce the frequency modulation range of the CLLC resonant converter and improve the electromagnetic compatibility of the CLLC resonant converter.
Drawings
Fig. 1 is a topology diagram of a CLLC resonant converter based on variable inductance according to an embodiment of the present invention;
FIG. 2 is a control winding diagram for providing primary and secondary side resonant inductances according to an embodiment of the present invention;
fig. 3 is a step diagram of a control method of a CLLC resonant converter based on variable inductance according to an embodiment of the present invention;
FIG. 4 is a graph of a resonant cavity current waveform of a variable inductance-based CLLC resonant converter in an under-resonant state according to an embodiment of the present invention;
FIG. 5 is a diagram showing a resonant cavity current waveform of a CLLC resonant converter based on variable inductance in a quasi-resonant state according to an embodiment of the present invention;
FIG. 6 is a graph of a resonant cavity current waveform of a variable inductance-based CLLC resonant converter according to an embodiment of the present invention in an over-resonant state;
fig. 7 is a working mode diagram of the CLLC resonant converter based on the variable inductance in half period under the under-resonant state according to the embodiment of the present invention; wherein FIG. 7 (a) shows the resonant converter in an under-resonant state t 0 ～t 0′ FIG. 7 (b) is a diagram of the working mode of the deviceThe converter is in an under-resonant state t 0′ ～t 1 Fig. 7 (c) shows the resonant converter in the under-resonant state t 1 ～t 2 FIG. 7 (d) shows the resonant converter in the under-resonant state t 2 ～t 3 Fig. 7 (e) shows the resonant converter in the under-resonant state t 3 ～t 4 Is a working mode diagram of the system.
Reference numerals and description:
1. a direct current bus; 2. an energy storage power supply; 3. a primary full bridge circuit; 4. a resonant cavity circuit; 5. secondary full bridge circuit.
Detailed Description
The following description of the embodiments of the present invention will be made clearly and completely with reference to the accompanying drawings, in which it is apparent that the embodiments described are only some embodiments of the present invention, but not all embodiments. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
The terms "first" and "second" are used below for descriptive purposes only and are not to be construed as indicating or implying relative importance or implicitly indicating the number of technical features indicated. Thus, a feature defining "a first" or "a second" may explicitly or implicitly include one or more such feature. In the description of the embodiments of the present disclosure, unless otherwise indicated, the meaning of "a plurality" is two or more. In addition, the use of "based on" or "according to" is intended to be open and inclusive in that a process, step, calculation, or other action "based on" or "according to" one or more of the stated conditions or values may in practice be based on additional conditions or beyond the stated values.
As shown in fig. 1, the embodiment of the invention provides a CLLC resonant converter based on variable inductance, which comprises a primary full-bridge circuit 3, a resonant cavity circuit 4 and a secondary full-bridge circuit 5 which are sequentially connected and arranged between a direct current bus 1 and an energy storage power supply 2.
Specifically, in the present embodiment, the dc busThe line 1 is to change alternating current into direct current after carrying and rectifying in a converter, and the direct current is changed into alternating current in an inverter, and the voltage at two ends of a direct current bus 1 is V 1 The method comprises the steps of carrying out a first treatment on the surface of the The energy storage power supply 2 is a storage battery, and the voltage at two ends of the energy storage power supply 2 is V 2 。
The resonant cavity circuit 4 includes: primary side resonant inductance L vi1 Primary side resonance capacitor C r1 Equivalent excitation inductance L m Transformer T, secondary side resonance capacitor C r2 Secondary side resonant inductance L vi2 The method comprises the steps of carrying out a first treatment on the surface of the Primary side resonant inductance L vi1 And secondary side resonance inductance L vi2 Are all variable inductances.
Primary side resonant inductance L vi1 With primary resonance capacitor C r1 The equivalent excitation inductance L is arranged at the primary of the transformer T in series m The primary of the transformer T is connected in parallel; secondary side resonance capacitor C r2 Resonant inductor L with secondary side vi2 Is arranged in series in the secondary of the transformer T.
As shown in fig. 2, the variable inductance based CLLC resonant converter further includes a direct current source.
Primary side resonant inductance L vi1 Secondary side resonant inductance L vi2 And the direct current source is sequentially connected to form a complete loop.
Primary side resonant inductance L vi1 And secondary side resonance inductance L vi2 Through the output current I of the DC current source c And controlling the size.
Specifically, the variable inductance is a variable inductor having a saturable core with three core legs including a central core leg around which a control coil is wound and two outer core legs around which two outer coils are wound in parallel, the inductance of the outer coils on the outer core legs varying with the current through the control coil. Therefore, when the primary side resonance inductor and the secondary side resonance inductor are connected in series, the sizes of the primary side resonance inductor and the secondary side resonance inductor can be adjusted by adjusting the output current of the direct current source connected in series with the primary side resonance inductor and the secondary side resonance inductor.
That is, the primary side resonant inductance L vi1 And secondary side resonance inductance L vi2 Can be controlled by varying the inductance value of DCOutput current I of current source c And change when outputting current I c When increasing, primary side resonance inductance L vi1 And secondary side resonance inductance L vi2 Is reduced when the inductance value of the output current I c When decreasing, primary side resonance inductance L vi1 And secondary side resonance inductance L vi2 The inductance value of (2) increases.
When changing the output current I c When the size is large, primary side resonance inductance L vi1 And secondary side resonance inductance L vi2 Simultaneously increases or simultaneously decreases, and plays a role in enhancing the voltage gain of the resonant converter in the same direction.
Further, as shown in fig. 1, the primary full-bridge circuit 3 includes a primary filter capacitor C 1 First switch tube Q 1 Second switch tube Q 2 Third switch tube Q 3 Fourth switching tube Q 4 ；
Primary side filter capacitor C 1 The two ends of the direct current bus 1 are connected in parallel;
positive pole of DC bus 1 and first switch tube Q 1 And a third switching tube Q 3 The negative electrode of the DC bus 1 is connected with the second switch tube Q 2 Source and fourth switching tube Q 4 Source connection of the first switch tube Q 1 Source electrode of (C) and second switch tube Q 2 Drain electrode of the third switch tube is connected with source electrode Q 3 And a fourth switching tube Q 4 Is connected with the drain electrode of the transistor;
primary side resonant inductance L vi1 One end of (a) is connected with a first switch tube Q 1 Source of (d) and second switching tube Q 2 Drain electrode of primary side resonance inductance L vi1 The other end of (C) is connected with the primary side resonance capacitor C r1 Primary side resonance capacitor C r1 And the other end of the inductor is equivalent to the exciting inductance L m One end of the transformer T is connected with one end of the primary of the transformer T, the equivalent excitation inductance L m And the other end of the primary of the transformer T, a third switching tube Q 3 Source and fourth switching tube Q 4 Is connected to the drain of the transistor.
Further, the secondary full-bridge circuit 5 includes a secondary filter capacitor C 2 Fifth switch tube Q 5 Sixth switchTube Q 6 Seventh switch tube Q 7 Eighth switching tube Q 8 ；
Secondary side filter capacitor C 2 The two ends of the energy storage power supply 2 are connected in parallel;
the positive pole of the energy storage power supply 2 is connected with a fifth switch tube Q 5 Drain electrode of (d) and seventh switching tube Q 7 The negative electrode of the energy storage power supply 2 is connected with a sixth switching tube Q 6 Source of (d) and eighth switching tube Q 8 Source of fifth switch tube Q 5 Source electrode of (d) and sixth switch tube Q 6 Drain electrode connection of the seventh switching tube Q 7 Source electrode of (d) and eighth switching tube Q 8 Is connected with the drain electrode of the transistor;
secondary side resonant inductance L vi2 One end of (a) is connected with a fifth switch tube Q 5 Source and sixth switching tube Q 6 Drain electrode of the secondary side resonance inductance L vi2 The other end of the capacitor is connected with a secondary side resonance capacitor C r2 One end of the secondary side resonance capacitor C r2 The other end of the secondary side of the transformer T is connected with a seventh switching tube Q 7 Source of (d) and eighth switching tube Q 8 Is formed on the drain electrode of the transistor.
Further, the resonant converter includes a forward operating state and a reverse operating state.
The forward running state is a state that electric energy is transmitted from a direct-current power supply to the energy storage power supply 2 through the primary full-bridge circuit 3, the resonant cavity circuit 4 and the secondary full-bridge circuit 5 in sequence; the reverse running state is a state in which electric energy is transmitted from the energy storage power supply 2 to the direct current power supply through the secondary side full-bridge circuit 5, the resonant cavity circuit 4 and the primary side full-bridge circuit 3 in sequence.
In fig. 1, the arrow above the resonant cavity circuit 4 indicates forward operation of the resonant converter, and the arrow below the resonant cavity circuit 4 indicates reverse operation of the resonant converter.
In the forward running state, the first switching tube Q 1 And a second switching tube Q 2 Is complementary to the drive signal of the third switching tube Q 3 And a fourth switching tube Q 4 Is complementary to the drive signal of (a); first switch tube Q 1 And a fourth switching tube Q 4 Is the same as the driving signal of the second switch tube Q 2 And a third switching tubeQ 3 Is the same as the drive signal of (a); fifth switch tube Q 5 Sixth switching tube Q 6 Seventh switch tube Q 7 Eighth switching tube Q 8 The primary full-bridge circuit 3 works in an inversion state, and the secondary full-bridge circuit 5 works in a rectification state without driving signals;
in the reverse running state, the fifth switch tube Q 5 And a sixth switching tube Q 6 Is complementary to the drive signal of the seventh switching tube Q 7 And an eighth switching tube Q 8 Is complementary to the drive signal of (a); fifth switch tube Q 5 And an eighth switching tube Q 8 The driving signals of the sixth switch tube Q are the same 6 And a seventh switching tube Q 7 Is the same as the drive signal of (a); first switch tube Q 1 Second switch tube Q 2 Third switch tube Q 3 Fourth switching tube Q 4 The primary full-bridge circuit 3 works in a rectifying state, and the secondary full-bridge circuit 5 works in an inverting state without driving signals.
That is, by combining the on and off of the switching transistors in the primary full-bridge circuit 3 and the secondary full-bridge circuit 5, the input voltage of the resonant cavity circuit 4 can be maintained at 0V or V 1 Two different levels.
Specifically, in the forward running state of the resonant converter of the invention, the primary side resonant inductance L vi1 The inductance value change of (2) plays a dominant role in the influence of voltage gain, and the secondary resonance inductance L vi2 Is used to assist the effect of the change in inductance on the voltage gain, i.e. when the output current I c When in change, the primary side resonance inductance L vi1 Has obvious influence on the voltage gain of the resonant converter, plays a leading role and has a secondary side resonant inductance L vi2 The voltage gain of the resonant converter is not obviously influenced, and the auxiliary voltage regulation function is realized.
The secondary side resonant inductor L of the resonant converter in the reverse running state vi2 The inductance value change of (2) plays a dominant role in the influence of voltage gain, and the primary side resonance inductance L vi1 Is used to assist the effect of the change in inductance on the voltage gain, i.e. when the output current I c Secondary side resonant inductance L when changing vi2 Voltage gain influence on resonant converterObviously, plays a leading role, and the primary side resonance inductance L vi1 The voltage gain of the resonant converter is not obviously influenced, and the auxiliary voltage regulation function is realized.
Further, in the present embodiment, the first switching tube Q 1 And a second switching tube Q 2 Is complementary to the drive signal of the third switching tube Q 3 And a fourth switching tube Q 4 Is specifically:
first switch tube Q 1 Conducting, second switch tube Q 2 Turn-off, third switch tube Q 3 Turn-off, fourth switch tube turn-on Q 4 。
Fifth switch tube Q 5 And a sixth switching tube Q 6 Is complementary to the drive signal of the seventh switching tube Q 7 And an eighth switching tube Q 8 Is specifically:
fifth switch tube Q 5 Conduction, sixth switch tube Q 6 Turn off, seventh switch tube Q 7 Turn off, eighth switch tube Q 8 Conducting.
According to the CLLC resonant converter based on the variable inductor, electric isolation is achieved between the primary side and the secondary side of the CLLC resonant converter based on the variable inductor, and the variable inductor replaces the primary side resonant inductor and the secondary side resonant inductor with fixed values in the prior art, so that the output voltage gain of the CLLC resonant converter can be adjusted by adjusting the inductance of the primary side resonant inductor and the secondary side resonant inductor; the primary side resonance inductance, the secondary side resonance inductance and the direct current source are sequentially connected to form a complete loop, so that the control mode of the CLLC resonance converter is changed from the traditional frequency modulation or phase-shifting frequency modulation control mode into a inductance modulation mode, namely, the inductance values of the primary side resonance inductance and the secondary side resonance inductance can be adjusted only by adjusting the output current of the direct current source, thereby enabling the control mode to be simpler; after the inductance values of the primary side resonance inductance and the secondary side resonance inductance are adjusted to the limit value, the switching frequency f of the resonant converter can be adjusted s The bidirectional wide voltage gain of the converter is further adjusted, so that the compatibility of the resonant converter is improved. Namely, the invention can ensure CLLC resonanceThe voltage gain range of the CLLC resonant converter is expanded, the frequency modulation range of the CLLC resonant converter is reduced, and the electromagnetic compatibility of the CLLC resonant converter is improved while the characteristics of the converter are improved.
The embodiment of the invention also provides a control method of the CLLC resonant converter based on the variable inductance in any one of the above steps, as shown in fig. 3, the method comprises the following steps:
and 101, acquiring a voltage fluctuation value of a direct current bus within a preset time period. I.e. V in a preset time period is obtained 1 Is a range of variation values.
Step 102, determining a first scheme or a second scheme as a scheme for adjusting the output of the resonant converter according to the voltage fluctuation value and the magnitude of a preset threshold value.
Wherein the first scheme is to regulate the output current I of the direct current source only c The second scheme is to adjust the output current I of the direct current source at the same time c Size and switching frequency f of resonant converter s Is of a size of (a) and (b).
Further, the determining of the first scheme or the second scheme as a scheme for adjusting the output of the resonant converter according to the voltage fluctuation value and the magnitude of the preset threshold specifically includes:
and when the voltage fluctuation value of the direct current bus is smaller than a preset threshold value, taking the first scheme as a scheme for regulating the output of the resonant converter.
And when the voltage fluctuation value of the direct current bus is larger than a preset threshold value, taking the second scheme as a scheme for adjusting the output of the resonant converter.
Further, only the output current I of the DC current source is regulated c The size specifically comprises:
obtaining the output voltage of the resonant converter;
when the output voltage is greater than the target voltage, the output current I of the direct current source is reduced c The output voltage is reduced.
Specifically, when the output voltage is greater than the target voltage, the output current I is reduced c Further, the inductance values of the primary side resonance inductance and the secondary side resonance inductance are increased, so that the resonance frequency f of the resonant converter of the invention is increased r The degree of freedom of the device is reduced,thereby entering an over-resonant state and the output voltage decreases.
Resonant frequency f of resonant converter r And determining according to the primary side resonance inductance, the primary side resonance capacitance, the equivalent excitation inductance, the transformer, the secondary side resonance capacitance and the secondary side resonance inductance.
When the output voltage is smaller than the target voltage, the output current I of the direct current source is increased c The output voltage rises.
Specifically, when the output voltage is smaller than the target voltage, the output current I is increased c Further reducing the inductance value of the primary side resonance inductance and the secondary side resonance inductance, so that the resonance frequency f of the resonance converter of the invention r And rises to enter an under-resonant state, and the output voltage rises.
Further, the output current I of the direct current source is regulated simultaneously c Size and switching frequency f of resonant converter s Specifically including:
obtaining the output voltage of the resonant converter;
when the output voltage is greater than the target voltage, the output current I of the direct current source is reduced c To a minimum value, and then increasing the switching frequency f s The output voltage is reduced.
Specifically, when the output voltage is far greater than the target voltage, the output current I is reduced c To its minimum value, then the switching frequency f is increased s Further aggravate the over-resonance state, lowering the output voltage.
When the output voltage is smaller than the target voltage, the output current I of the direct current source is increased c To a maximum value, then reducing the switching frequency f s The output voltage rises.
Specifically, when the output voltage is far smaller than the target voltage, the output current I is increased c To its maximum value, then the switching frequency f is reduced s Further aggravate the under-resonance state, improve output voltage.
When the output voltage is equal to the target voltage, the resonant converter operates in a quasi-resonant state.
Under-resonant state of resonant converter when user needs to switchIn the state and the over-resonance state, the output current I is required to be outputted in order to prevent the current spike and ensure the safety of the resonant converter c And the current peak caused by switching of the working state is restrained by reducing the primary side resonance inductance to zero so that the primary side resonance inductance and the secondary side resonance inductance reach the maximum value.
In this embodiment, when energy is transferred between the dc bus and the energy storage power supply, and the voltage fluctuation value of the dc bus is smaller than a preset threshold, the output voltage of the resonant converter may be adjusted by only adjusting the inductance values of the primary side resonant inductor and the secondary side resonant inductor. At this time, the driving signals of the first switching tube and the second switching tube are complementary, and the driving signals of the third switching tube and the fourth switching tube are complementary; the first switching tube and the fourth switching tube are simultaneously conducted, and the duty ratio is kept unchanged at 0.5; the second switching tube and the third switching tube are simultaneously conducted, and the duty ratio is kept unchanged at 0.5. The output voltage is regulated by adjusting the inductance value of the variable inductor.
When the voltage fluctuation value of the direct current bus is larger than the preset threshold value, the requirement of the voltage gain of the resonant converter cannot be met by only adjusting the inductance value of the variable inductor, and at the moment, the switching frequency f needs to be adjusted s . That is, when the output voltage is greater than or less than the target voltage, the switching frequency f of the CLLC resonant converter is continuously adjusted after the inductance value of the variable inductor is adjusted to the maximum value or the minimum value s The output voltage is continuously increased or decreased, and the voltage can be adjusted in a large range through small-range frequency modulation.
The resonant converter comprises three working states of an under-resonant state, a quasi-resonant state and an over-resonant state, and current waveforms of the resonant cavities in different areas of the three working states are shown in fig. 4, 5 and 6 respectively.
As shown in fig. 4, in the under-resonant state, one period of the resonant converter includes t 0 ～t 8 A time node, where t 0 ～t 4 For the first half period, t 4 ～t 8 For the latter half period, the first half period and the second half period operate on the same principle, and each half period comprises 5 modes. For example: the 5 modes of the first half period are respectively t 0 ～t 0 ′、t 0′ ～t 1 、t 1 ～t 2 、t 2 ～t 3 T 3 ～t 4 。
As shown in fig. 5 and 6, one period of the resonant converter includes t in the quasi-resonant state and the over-resonant state 0 ～t 6 A time node, where t 0 ～t 3 For the first half period, t 3 ～t 6 For the latter half period, the first half period and the latter half period operate on the same principle, and each half period comprises 4 modes. For example: the 5 modes of the first half period are respectively t 0 ～t 0 ′、t 0′ ～t 1 、t 1 ～t 2 T 2 ～t 3 。
It can be seen that the resonant converter is in a quasi-resonant state or an over-resonant state, and the over-resonant state is only one mode less than the under-resonant state.
In this embodiment, the analysis of the working mode is performed only by taking the under-resonant state as an example, and since the working principle of the first half period and the second half period is the same in the under-resonant state, the present embodiment only shows the first half period, i.e., t 0 ～t 4 The working principle of the segment resonant converter.
As shown in fig. 4, 7 (a) and 7 (b), at t 0 At the moment, the first switching tube Q 1 And a fourth switching tube Q 4 On, via primary resonance inductance L vi1 Is the current i of (2) Lvi1 By parasitic diode D of switching tube Q1 And D Q4 Freewheel at this time Q 1 And Q 4 The drain-source voltage is zero, creating conditions for its zero voltage on (ZVS). The voltage across A, B in FIG. 1 is the input voltage V 1 ，i Lvi1 The equivalent excitation inductance L is increased according to sine rule m Is the current i of (2) Lm Linearly increasing the current i Lvi1 Is greater than the current i Lm Fast. Parasitic diode D of secondary side switching tube Q5 And D Q8 Conducting rectification, wherein the voltage at two ends of C, D is output by the voltage V at the end 2 Clamping. At t 0′ Time, i Lvi1 Decreasing to zero and then changing direction, passing through the transverse axis, until t 1 Time of day, Q 1 And Q 4 Maintaining on state, resonant current i Lvi1 Equal to the exciting current i Lm ，t 0 ～t 1 Ending the working mode of (a). t is t 0 ～t 1 In the process of (2), whether t is 0 -t 0′ Time period is also t 0′ -t 1 The time periods are all L vi1 、C r1 、L vi2 、C r2 Four-element resonant process, L m Does not participate in the resonance process.
As shown in FIG. 7 (c), Q 1 And Q 4 Still keep on, resonant current i Lvi1 And excitation current i Lm The secondary side current of the transformer is equal to zero, and the parasitic diode D of the secondary side switching tube Q5 And D Q8 The secondary side current is naturally turned off because of zero, so that zero current turn-off (ZCS) is realized, and the reverse recovery problem is avoided; simultaneously, the primary side and the secondary side of the transformer are separated, and the resonant inductance L vi2 And a resonance capacitor C r2 No longer participates in resonance but becomes equivalent excitation inductance L m And resonant inductance L vi1 Resonance capacitor C r1 Resonance occurs together, the resonance period of the resonance of the three is far longer than the switching period, i of the time period Lm And i Lvi1 Can be regarded as approximately constant. t is t 2 Time of day, Q 1 、Q 4 Shut off, t 1 ～t 2 The process of the working mode is ended.
As shown in FIG. 7 (d), t 2 Time of day, Q 1 、Q 4 At this time, all the switching tubes are in an off state, i.e., enter dead time. Resonant current i Lvi1 Parasitic capacitance C to switch tube Q1 And C Q4 Charging, switch tube Q 1 And Q 4 The drain-source voltage of (2) rises linearly; resonant current i Lvi1 At the same time give parasitic capacitance C Q2 And C Q3 Discharge, Q 2 And Q 3 The drain-source voltage of (c) drops linearly. t is t 3 Time of day, Q 1 And Q 4 Is equal to V 1 ，Q 2 And Q 3 Is equal to 0, t 2 ～t 3 Ending the working mode of (a).
As shown in fig. 7 (e), t 3 At the moment, all the switching tubes are still in an off state, Q 1 And Q 4 The parasitic capacitance charging process of (1) is completed, Q 2 And Q 3 The parasitic capacitance discharging process of (1) is completed, and the resonant current i is obtained Lvi1 Only through Q 2 And Q 3 Parasitic diode D of (2) Q2 And D Q3 Freewheel, thereby making Q 2 And Q 3 Drain-source voltage of zero, Q 2 And Q 3 The turn-on at this stage enables zero voltage turn-on. The voltage across this stage A, B is-V 1 The voltage across C, D is-V 2 Reach t 4 At this point, the first half cycle ends and begins to enter the second half cycle.
Because the control mode of the traditional CLLC resonant converter is mostly phase-shifting frequency modulation control, the control mode is complex, and a large frequency adjustment range is required for obtaining wide voltage gain, which is not beneficial to the optimal design of the magnetic element. Therefore, on the basis of keeping the advantages of the traditional CLLC resonant converter, the control mode of the CLLC resonant converter is simplified, and the voltage gain is widened and the frequency modulation range is narrowed. Therefore, the invention provides a CLLC resonant converter based on variable inductance and a control method thereof.
The invention replaces the fixed value resonant inductance of the primary side and the secondary side in the resonant cavity of the traditional CLLC resonant converter by the variable inductance, realizes the bidirectional voltage regulation function of the resonant converter by regulating the inductance value of the variable inductance, combines frequency modulation control on the basis of regulating the inductance value of the variable inductance, namely combines the regulation of the switching frequency of the resonant converter, and widens the gain range of output voltage.
The invention does not change the topological structure of the CLLC resonant converter, so that the gain range of the output voltage can be further widened on the premise of keeping the advantages of the soft switch of the traditional CLLC resonant converter, the frequency modulation range is reduced, the operation requirement of the CLLC resonant converter under the limit working condition can be met, and the high conversion efficiency can be kept in the wide voltage gain range.
The foregoing is merely illustrative of specific embodiments of the present invention, and the scope of the present invention is not limited thereto, but any changes or substitutions within the technical scope of the present invention should be covered by the scope of the present invention. Therefore, the protection scope of the present invention shall be subject to the protection scope of the claims.

Claims (8)

1. The utility model provides a CLLC resonant converter based on variable inductance, includes primary full-bridge circuit, resonant cavity circuit and the secondary full-bridge circuit that connects gradually and set up between direct current busbar and energy storage power supply, its characterized in that, resonant cavity circuit includes: primary side resonance inductance, primary side resonance capacitance, equivalent excitation inductance, transformer, secondary side resonance capacitance and secondary side resonance inductance; the primary side resonance inductance and the secondary side resonance inductance are variable inductances;
the primary side resonance inductor and the primary side resonance capacitor are arranged at the primary side of the transformer in series, and the equivalent excitation inductor is connected at the primary side of the transformer in parallel; the secondary side resonance capacitor and the secondary side resonance inductor are connected in series to the secondary side of the transformer;
the direct current source is also included; the primary side resonance inductor, the secondary side resonance inductor and the direct current source are sequentially connected to form a complete loop;
the primary side resonance inductor and the secondary side resonance inductor are controlled by the output current of the direct current source.
2. The resonant converter of claim 1, wherein the primary full-bridge circuit comprises a primary filter capacitor, a first switching tube, a second switching tube, a third switching tube, and a fourth switching tube;
the primary side filter capacitor is connected in parallel with two ends of the direct current bus;
the positive electrode of the direct current bus is connected with the drain electrode of the first switching tube and the drain electrode of the third switching tube, the negative electrode of the direct current bus is connected with the source electrode of the second switching tube and the source electrode of the fourth switching tube, the source electrode of the first switching tube is connected with the drain electrode of the second switching tube, and the source electrode of the third switching tube is connected with the drain electrode of the fourth switching tube;
one end of the primary side resonance inductor is connected with the source electrode of the first switching tube and the drain electrode of the second switching tube, the other end of the primary side resonance inductor is connected with one end of the primary side resonance capacitor, the other end of the primary side resonance capacitor is connected with one end of the equivalent excitation inductor and one end of the primary side of the transformer, and the other end of the equivalent excitation inductor is connected with the other end of the primary side of the transformer, and the source electrode of the third switching tube is connected with the drain electrode of the fourth switching tube.
3. The resonant converter of claim 2, wherein the secondary full-bridge circuit comprises a secondary filter capacitor, a fifth switching tube, a sixth switching tube, a seventh switching tube, and an eighth switching tube;
the secondary side filter capacitor is connected in parallel with two ends of the energy storage power supply;
the positive electrode of the energy storage power supply is connected with the drain electrode of the fifth switching tube and the drain electrode of the seventh switching tube, the negative electrode of the energy storage power supply is connected with the source electrode of the sixth switching tube and the source electrode of the eighth switching tube, the source electrode of the fifth switching tube is connected with the drain electrode of the sixth switching tube, and the source electrode of the seventh switching tube is connected with the drain electrode of the eighth switching tube;
one end of the secondary side resonance inductor is connected with the source electrode of the fifth switching tube and the drain electrode of the sixth switching tube, the other end of the secondary side resonance inductor is connected with one end of the secondary side resonance capacitor, the other end of the secondary side resonance capacitor is connected with one end of the secondary side of the transformer, and the other end of the secondary side of the transformer is connected with the source electrode of the seventh switching tube and the drain electrode of the eighth switching tube.
4. A resonant converter according to claim 3, wherein the resonant converter comprises a forward operating condition and a reverse operating condition; the forward running state is a state that electric energy is transmitted from the direct current power supply to the energy storage power supply through the primary full-bridge circuit, the resonant cavity circuit and the secondary full-bridge circuit in sequence; the reverse running state is a state that electric energy is transmitted from the energy storage power supply to the direct current power supply through the secondary side full-bridge circuit, the resonant cavity circuit and the primary side full-bridge circuit in sequence;
when the forward running state is adopted, driving signals of the first switching tube and the second switching tube are complementary, driving signals of the third switching tube and the fourth switching tube are complementary, driving signals of the first switching tube and the fourth switching tube are identical, and driving signals of the second switching tube and the third switching tube are identical; the fifth switching tube, the sixth switching tube, the seventh switching tube and the eighth switching tube have no driving signals, the primary full-bridge circuit works in an inversion state, and the secondary full-bridge circuit works in a rectification state;
in the reverse running state, the driving signals of the fifth switching tube and the sixth switching tube are complementary, and the driving signals of the seventh switching tube and the eighth switching tube are complementary; the driving signals of the fifth switching tube and the eighth switching tube are the same, and the driving signals of the sixth switching tube and the seventh switching tube are the same; the first switching tube, the second switching tube, the third switching tube and the fourth switching tube have no driving signals, the primary full-bridge circuit works in a rectifying state, and the secondary full-bridge circuit works in an inversion state.
5. A control method applied to the variable inductance-based CLLC resonant converter of any one of claims 1-4, characterized in that:
acquiring a voltage fluctuation value of the direct current bus within a preset time period;
determining a first scheme or a second scheme as a scheme for adjusting the output of the resonant converter according to the voltage fluctuation value and a preset threshold value; the first scheme is to adjust the output current of the direct current source only, and the second scheme is to adjust the output current of the direct current source and the switching frequency of the resonant converter simultaneously.
6. The control method according to claim 5, wherein the determining the first scheme or the second scheme as the scheme for adjusting the output of the resonant converter according to the magnitude of the voltage fluctuation value and a preset threshold value specifically includes:
when the voltage fluctuation value of the direct current bus is smaller than the preset threshold value, the first scheme is used as a scheme for adjusting the output of the resonant converter;
and when the voltage fluctuation value of the direct current bus is larger than the preset threshold value, taking the second scheme as a scheme for adjusting the output of the resonant converter.
7. The control method according to claim 5, wherein the adjusting only the output current of the dc current source specifically includes:
obtaining the output voltage of the resonant converter;
when the output voltage is larger than the target voltage, reducing the output current of the direct current source to reduce the output voltage;
and when the output voltage is smaller than the target voltage, decreasing and increasing the output current of the direct current source to increase the output voltage.
8. The control method according to claim 5, wherein the simultaneously adjusting the output current of the dc current source and the switching frequency of the resonant converter comprises:
obtaining the output voltage and the switching frequency of the resonant converter;
when the output voltage is larger than a target voltage, reducing the output current of the direct current source to a minimum value, and then increasing the switching frequency to reduce the output voltage;
and when the output voltage is smaller than the target voltage, increasing the output current of the direct current source to a maximum value, and then reducing the switching frequency to increase the output voltage.
CN202310755684.5A 2023-06-26 2023-06-26 CLLC resonant converter based on variable inductance and control method thereof Pending CN116827133A (en)

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