CN114400886A - Frequency conversion self-adaptive dead time totem pole PFC control method - Google Patents
Frequency conversion self-adaptive dead time totem pole PFC control method Download PDFInfo
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- CN114400886A CN114400886A CN202210050258.7A CN202210050258A CN114400886A CN 114400886 A CN114400886 A CN 114400886A CN 202210050258 A CN202210050258 A CN 202210050258A CN 114400886 A CN114400886 A CN 114400886A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4233—Arrangements for improving power factor of AC input using a bridge converter comprising active switches
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/083—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the ignition at the zero crossing of the voltage or the current
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The invention relates to the field of power electronics, in particular to a totem-pole PFC (power factor correction) control method of variable-frequency self-adaptive dead time, which adopts variable frequency to realize soft switching, adopts the self-adaptive dead time to reduce the loss caused by reverse conduction of a switching tube in the dead time, and improves the working efficiency of a converter; the method adopts double closed-loop control of an output voltage outer loop and an inductive current inner loop and input-output voltage calculation to generate duty ratiodCalculating frequency by sampling input/output voltage and inductance currentfAnd dead timeT dDuty ratio ofdAnd frequencyfAnd dead timeT dGenerating a PWM signal to control a high-frequency bridge arm switching tube of a totem-pole PFC (power factor correction) so as to realize stable output voltage and soft switching of a high-frequency bridge arm; the power frequency bridge arm driving signal generates a PWM signal with the same frequency and the same phase as the input alternating voltage by phase locking the input voltage; the invention realizes the PWM control of the variable frequency self-adaptive dead time, realizes the full-range soft switching, and has simple method and no need ofAn inductive current zero-crossing detection circuit is required, and the efficiency of the converter can be improved.
Description
Technical Field
The invention relates to the technical field of power electronics, in particular to a totem-pole PFC control method with variable-frequency self-adaptive dead-time.
Background
The totem pole PFC circuit is a PFC circuit which is widely researched in the fields of server power supplies, data centers and the like at present. With the pursuit of high operating efficiency of circuits for server power supplies, data centers, and the like, research into the efficiency of totem-pole PFC circuits has been increasing, and realization of ZVS can effectively reduce switching loss in order to improve the operating efficiency of totem-pole PFC. In the existing ZVS control method of totem-pole PFC, most documents adopt a TCM mode for control, or the TCM mode is improved, in the control, each time of a switching tube needs to be calculated, an expression is complex, an additional inductive current ZCD detection circuit needs to be added to control a driving signal, and the control method and the control circuit are complex. In addition, if the dead time is too long, the switching tube is conducted in the reverse direction, so that large reverse conduction loss in the dead time is caused.
Disclosure of Invention
Aiming at the defects of the prior art, the invention provides a variable-frequency self-adaptive dead-time totem-pole PFC control method, which solves the problems that the loss caused by reverse conduction of a switching tube is not considered in the conventional control method, the control is complex, the calculated amount is large, an additional inductive current ZCD detection circuit is required, and the like.
In order to solve the technical problems, the technical method adopted by the invention is as follows:
a totem pole PFC control method of frequency conversion self-adaptive dead time comprises the following steps:
A. collecting input voltage v of totem pole PFCinInductor current iLAnd an output voltage VoThe double closed loops are used for outputting a voltage outer loop and an inductive current inner loop, and the duty ratio d is obtained by calculating the output voltage and the input-output voltage of the double closed loops;
B. carrying out frequency f and dead time T on the collected input voltage, inductive current and output voltage in a controller according to an expressiondObtaining the frequency and the dead time by the calculation of (1);
C. duty cycle d, frequency f and dead time TdGenerating a driving signal of a high-frequency bridge arm;
D. and performing phase locking on the input voltage to obtain a phase-locked signal omega t with the same phase as the input voltage, and obtaining a driving signal of the power frequency bridge arm from the phase-locked signal.
The technical method of the invention is further improved in that: in step A, the input AC voltage is analyzed by working in the positive half cycle, and the input voltage v of the totem-pole PFC is analyzedinInductor current iLAnd an output voltage VoThe voltage is transmitted to a control chip DSP through a sampling circuit, double closed-loop control is carried out in the control chip DSP for stabilizing output voltage, the output voltage is used as a voltage outer loop, inductive current is used as a current inner loop, and a given value V of the output voltage isorefAnd the output voltage sampling value VoSubtracting, passing through an outer ring regulator, and outputting voltage which is direct current, so that the output passing through the voltage outer ring regulator is a constant value, and because the filtered inductive current is sinusoidal and is required to well follow the input voltage and has the same frequency and the same phase with the input voltage, the output of the voltage outer ring regulator needs to be multiplied by the input voltage vinK obtaining given value i of inductive currentLrefWherein k is the peak value of the input voltage, the current inner loop mainly functions to realize the power factor correction of the inductive current, namely, the inductive current and the input voltage have the same frequency and the same phase through the current inner loop, and the given value i of the inductive currentLrefAnd the value of the filtered inductance current iLThe error value obtained by subtraction is output after passing through the current inner loop regulator, and the duty ratio d is calculated together with the input and output voltage after outputWhen the circuit is disturbed, the output voltage is stabilized by adjusting the duty ratio d.
The technical method of the invention is further improved in that: in the step B, the condition that the totem-pole PFC implements soft switching is that the reverse value of the inductor current is sufficient to pump out the charge in the parasitic capacitance of the switching tube before the inductor current becomes positive and the switching tube needs to be turned on in time, which must be turned on before the inductor current becomes positive, if the dead time is too long, the switching tube will be turned on in reverse direction, which will cause large reverse conduction loss, so the dead time needs to be optimized to reduce the loss;
analyzing the working process of the circuit to obtain an expression of frequency and dead time:
a. the frequency expression is:
when V iso>2vinThe method comprises the following steps:
when V iso<2vinThe method comprises the following steps:
b. the dead time expression is:
when V iso>2vinThe method comprises the following steps:
when V iso<2vinThe method comprises the following steps:
in the above formula, f represents the switching frequency, TdRepresenting dead time, VoRepresenting the output voltage, vinRepresenting the input AC voltage, LRepresents the totem-pole PFC inductance, iLavgRepresenting the mean value of the inductor current, CossThe output capacitance of the switch tube is represented;
and substituting each value obtained by sampling into the expression to obtain the frequency and the dead time.
The technical method of the invention is further improved in that: in the step C, the high-frequency bridge arm switch tube comprises a switch tube I and a switch tube II, wherein in the positive half period of the input alternating voltage, the switch tube I is an auxiliary tube, and the switch tube II is a main tube; in the negative half period of the input current and voltage, the first switch tube is a main tube, and the second switch tube is an auxiliary tube.
The technical method of the invention is further improved in that: the high-frequency bridge arm driving signals are as follows: converting the calculated frequency value into a carrier wave with corresponding frequency, comparing the carrier wave with a modulation wave to obtain an original driving waveform, then enabling the driving waveform to enter a dead zone generation module, delaying the rising edge of the driving waveform, wherein the delay time is the calculated dead zone time, so that a driving waveform of a main switching tube of a high-frequency bridge arm of a totem-pole PFC is obtained, and the driving waveform is supplied to a second switching tube in the positive half period of the input alternating voltage and is supplied to the first switching tube in the negative half period of the input alternating voltage; and delaying the falling edge of the driving waveform, wherein the delay time is dead time obtained by calculation, obtaining the driving waveform of the auxiliary switching tube of the high-frequency bridge arm of the totem-pole PFC after negation, and the driving waveform is supplied to the first switching tube in the positive half period of the input alternating voltage and is supplied to the second switching tube in the negative half period of the input alternating voltage.
Compared with the prior art, the totem pole PFC control method with the variable-frequency self-adaptive dead-time has the following beneficial effects:
1. according to the totem pole PFC control method based on the variable-frequency self-adaptive dead time, reverse conduction loss caused by reverse conduction of the switching tube is reduced by optimizing the dead time, and the working efficiency of the totem pole PFC is improved.
2. The invention relates to a frequency conversion self-adaptive dead time totem-pole PFC control method, which aims to reduce switching loss and adopts frequency conversion control to realize ZVS of a high-frequency bridge arm switching tube of the totem-pole PFC, wherein a frequency expression is obtained by accurately analyzing the working process of a totem-pole PFC circuit.
3. The invention relates to a variable-frequency self-adaptive dead-time totem-pole PFC control method, which respectively obtains frequency, duty ratio and dead-time, and obtains the driving waveform of a high-frequency bridge arm switching tube by the three, so that an extra inductive current ZCD detection circuit is avoided, the high-frequency bridge arm switching tube ZVS of the totem-pole PFC is realized while the output voltage is stabilized, the dead-time is optimized, and the self-adaptive change of the dead-time is realized.
4. The invention relates to a variable-frequency self-adaptive dead-time totem-pole PFC control method, which only needs to calculate frequency and dead-time, and the expressions of the frequency and the dead-time are simple and easy to realize in control.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical methods in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly described below, it is obvious that the drawings in the following description are only some embodiments of the present invention, and other drawings can be obtained by those skilled in the art without creative efforts.
Fig. 1 is a schematic diagram of a totem-pole PFC circuit topology according to the present invention.
Fig. 2 is a control block diagram of the control method of the present invention.
FIG. 3 shows the circuit topology of the present invention at Vo>2vinTheoretical working waveform diagram of time.
FIG. 4 shows the circuit topology of the present invention at Vo<2vinTheoretical working waveform diagram of time.
Fig. 5 is a simulated waveform diagram of input voltage, inductor current, output voltage, and frequency for the circuit topology of the present invention.
FIG. 6 is a circuit topology of the present invention at Vo>2vinA simulated waveform diagram.
FIG. 7 shows the circuit topology of the present invention at Vo<2vinA simulated waveform diagram.
Detailed Description
The present invention will be described in further detail with reference to the following examples:
as shown in fig. 1, totem-pole PFC circuit topology, vinFor inputting an AC voltage, L1Is an inductor, G1And G2For high-frequency bridge arm switch tube, i.e. switch tube one and switch tube two, G3And G4Is a power frequency bridge arm switching tube, C1For outputting filter capacitors, VoIs a dc output voltage. Input AC voltage VinEnd L and inductor L1Is connected to one end of an inductor L1The other end of the bridge arm is connected with the middle point of the bridge arm of the high-frequency bridge arm. High frequency switch tube G1Source electrode of and high frequency switch tube G2Is connected with the drain of the inductor L and serves as a middle point of a high-frequency bridge arm1And the other end of the two are connected. Power frequency switch tube G3Source electrode and power frequency switch tube G4Is connected with the drain electrode of the power frequency bridge arm and is used as the midpoint of the power frequency bridge arm to be connected with the input voltage vinAre connected. High frequency switch tube G1Drain electrode of and power frequency switch tube G3Is connected to the output filter capacitor C1Is connected as a DC output voltage VoThe positive terminal of (a). High frequency switch tube G2Source electrode and power frequency switch tube G4Is connected to the output filter capacitor C1Is connected as a DC output voltage VoThe negative terminal of (a).
As shown in FIG. 2, the input voltage v of the totem-pole PFCinInductor current iLAnd an output voltage VoThe voltage is sent to a control chip DSP through a sampling circuit, and double closed-loop control is carried out in the control chip DSP for stabilizing output voltage. The output voltage is used as a voltage loop, and the inductive current is used as a current inner loop. Given value V of output voltageorefAnd the output voltage sampling value VoThe subtraction is performed through a voltage outer ring regulator, the output voltage is a direct current quantity, so the output through the voltage ring regulator is a constant value, the filtered inductive current is a sine quantity and is required to well follow the input voltage and have the same frequency and the same phase with the input voltage,the output of the voltage loop regulator therefore needs to be multiplied by the input voltage vinK obtaining given value i of inductive currentLrefWhere k is the peak value of the input voltage. The main function of the current inner loop is to realize the power factor correction of the inductive current, namely, the inductive current and the input voltage have the same frequency and the same phase through the current loop. Given value of inductive current iLrefAnd the value of the filtered inductance current iLAnd the output and the input and output voltages after the subtraction and the passing through the current inner ring regulator jointly generate a duty ratio d, and when the circuit is disturbed, the output voltage is stabilized by regulating the duty ratio d. Frequency f and dead time T of converterdInput voltage v obtained according to sampling in control chip DSPinOutput voltage VoAnd the inductor current iLAnd (6) performing calculation. Duty cycle d, frequency f and dead time TdTo generate a driving signal of the high-frequency bridge arm switching tube. Input AC voltage v of power frequency bridge arm switch tube signalinIs determined by the phase-locked signal, input voltage vinObtaining a phase-locked signal omega t through phase locking, comparing the phase-locked signal with pi, and when the phase-locked signal is between 0 and pi, obtaining a power frequency switch tube G4On, G3Cut-off, between pi-2 pi, power frequency switch tube G3On, G4And (6) turning off.
As shown in FIG. 3, when V is analyzed by taking the positive half cycle of the input AC voltage as an exampleo>2vinWhen the inductive current reaches 0, the high-frequency bridge arm switch tube G1Turn off, at the moment, the high-frequency bridge arm switch tube G2The drain-source voltage of the bridge arm switch tube G begins to decrease, the inductive current and the high frequency1And G2The parasitic capacitance of the bridge arm performs resonance when the high-frequency bridge arm switching tube G2When the drain-source voltage is reduced to 0, the inductive current is a negative value, and the high-frequency bridge arm switching tube G is switched on in the period from the moment to the time when the inductive current is increased to 02，G2Soft switching can be achieved. High-frequency bridge arm switching tube G1Bridge arm switch tube G for switching off to high frequency2The period of time that is switched on is the dead time.
As shown in FIG. 4, when V is analyzed by taking the positive half cycle of the input AC voltage as an exampleo<2vinWhen the inductive current reaches 0, if the high-frequency bridge arm switch tube G is closed at the moment1At this time, the inductor current cannot complete resonance when the inductor current reaches 0 again, and soft switching cannot be realized. Therefore, it is necessary to make the high frequency bridge arm switch tube G1Prolonging conduction, and making high-frequency bridge arm switch tube G after conducting for a period of time1Turning off to increase the inductive current in negative direction, and switching tube G of high-frequency bridge arm1When the circuit is switched off, the current value of the inductor is enough to completely exhaust the charges of the parasitic capacitor, namely, the resonance can be completed. High-frequency bridge arm switch tube G2The drain-source voltage of the bridge arm switch tube G begins to decrease, the inductive current and the high frequency1And G2The parasitic capacitance of the bridge arm performs resonance when the high-frequency bridge arm switching tube G2When the drain-source voltage is reduced to 0, the inductive current is a negative value, and the high-frequency bridge arm switching tube G is switched on in the period from the moment to the time when the inductive current is increased to 02，G2Soft switching can be achieved. High-frequency bridge arm switching tube G1Bridge arm switch tube G for switching off to high frequency2The period of time that is switched on is the dead time.
FIG. 5 is a simulated waveform diagram of the simulation according to the control method of the present invention, in which the output voltage V is shown from top to bottomoEnlargement of the inductor current iLAnd an input voltage vin/90, frequency f. It can be seen from the waveform diagram that when the control method is adopted, the output voltage is stable and has power frequency pulsation of 2 times, the inductive current has a negative value and has the same frequency and phase with the input voltage, and the control method has good follow-up property. And within one power frequency period, the switching frequency is changing to realize soft switching.
As shown in fig. 6, at Vo>2vinThe waveform of the high-frequency bridge arm switching tube G is sequentially from top to bottom1Driving waveform (auxiliary tube) and high-frequency bridge arm switch tube G2The drive and drain-source voltage waveforms (main switching tube), the inductor current waveform, and the frequency waveform. As can be seen from the figure, in the steady state of the converter, the high-frequency bridge arm switching tube G can be seen1When the inductive current is 0, the driving signal is turned off, and the high-frequency bridge arm switching tube G2Is driven byAfter the drain-source voltage of the signal is reduced to 0, the signal is switched on before the inductive current is 0, and soft switching can be realized. The dead time is 282ns and the switching frequency 194 kHz.
As shown in fig. 7, at Vo<2vinThe waveform of the high-frequency bridge arm switching tube G is sequentially from top to bottom1Driving waveform (auxiliary tube) and high-frequency bridge arm switch tube G2The drive and drain-source voltage waveforms (main switching tube), the inductor current waveform, and the frequency waveform. As can be seen from the figure, in the steady state of the converter, the high-frequency bridge arm switching tube G can be seen1The drive signal is not turned off when the inductive current is 0 but is turned off after being prolonged and conducted for a period of time, and the high-frequency bridge arm switching tube G2The driving signal of (2) is turned on before the inductor current is 0, so that soft switching can be realized. The dead time is 320ns and the switching frequency is 72 kHz.
Compared with the common totem-pole PFC control method at present, the invention can realize ZVS in a full range, reduce switching loss, optimize dead time, reduce reverse conduction loss in the dead time, and simplify a hardware circuit without an inductive current ZCD detection circuit.
The above-mentioned embodiments are merely illustrative of the preferred embodiments of the present invention, and do not limit the scope of the present invention, and various modifications and improvements of the technical method of the present invention by those skilled in the art should fall within the protection scope defined by the appended claims of the apparatus of the present invention without departing from the spirit of the present invention.
Claims (5)
1. A totem pole PFC control method of frequency conversion self-adaptive dead time is characterized by comprising the following steps:
A. collecting input voltage v of totem pole PFCinInductor current iLAnd an output voltage VoThe double closed loops are used for outputting a voltage outer loop and an inductive current inner loop, and the duty ratio d is obtained by calculating the output voltage and the input-output voltage of the double closed loops;
B. the collected input voltage, the collected inductive current and the collected output voltage are subjected to frequency f and dead zone in a controller according to an expressionInter TdObtaining the frequency and the dead time by the calculation of (1);
C. duty cycle d, frequency f and dead time TdGenerating a driving signal of a high-frequency bridge arm;
D. and performing phase locking on the input voltage to obtain a phase-locked signal omega t with the same phase as the input voltage, and obtaining a driving signal of the power frequency bridge arm from the phase-locked signal.
2. The method for controlling the frequency conversion adaptive dead time totem pole PFC according to claim 1, characterized in that: in step A, the input AC voltage is analyzed by working in the positive half cycle, and the input voltage v of the totem-pole PFC is analyzedinInductor current iLAnd an output voltage VoThe voltage is transmitted to a control chip DSP through a sampling circuit, double closed-loop control is carried out in the control chip DSP for stabilizing output voltage, the output voltage is used as a voltage outer loop, inductive current is used as a current inner loop, and a given value V of the output voltage isorefAnd the output voltage sampling value VoSubtracting, passing through an outer ring regulator, and outputting voltage which is direct current, so that the output passing through the voltage outer ring regulator is a constant value, and because the filtered inductive current is sinusoidal and is required to well follow the input voltage and has the same frequency and the same phase with the input voltage, the output of the voltage outer ring regulator needs to be multiplied by the input voltage vinK obtaining given value i of inductive currentLrefWherein k is the peak value of the input voltage, the current inner loop mainly functions to realize the power factor correction of the inductive current, namely, the inductive current and the input voltage have the same frequency and the same phase through the current inner loop, and the given value i of the inductive currentLrefAnd the value of the filtered inductance current iLAnd outputting the error value obtained by subtracting the difference value through the current inner ring regulator, calculating a duty ratio d together with the input and output voltage after outputting the error value, and realizing the stability of the output voltage by regulating the duty ratio d when the circuit is disturbed.
3. The method for controlling the frequency conversion adaptive dead time totem pole PFC according to claim 1, characterized in that: in the step B, the condition that the totem-pole PFC implements soft switching is that the reverse value of the inductor current is sufficient to pump out the charge in the parasitic capacitance of the switching tube before the inductor current becomes positive and the switching tube needs to be turned on in time, which must be turned on before the inductor current becomes positive, if the dead time is too long, the switching tube will be turned on in reverse direction, which will cause large reverse conduction loss, so the dead time needs to be optimized to reduce the loss;
analyzing the working process of the circuit to obtain an expression of frequency and dead time:
a. the frequency expression is:
when V iso>2vinThe method comprises the following steps:
when V iso<2vinThe method comprises the following steps:
b. the dead time expression is:
when V iso>2vinThe method comprises the following steps:
when V iso<2vinThe method comprises the following steps:
in the above formula, f represents the switching frequency, TdRepresenting dead time, VoRepresenting the output voltage, vinRepresenting the input ac voltage, L representing the totem-pole PFC inductance, iLavgRepresenting the mean value of the inductor current, CossThe output capacitance of the switch tube is represented;
and substituting each value obtained by sampling into the expression to obtain the frequency and the dead time.
4. The method for controlling the frequency conversion adaptive dead time totem pole PFC according to claim 1, characterized in that: in the step C, the high-frequency bridge arm switch tube comprises a switch tube I and a switch tube II, wherein in the positive half period of the input alternating voltage, the switch tube I is an auxiliary tube, and the switch tube II is a main tube; in the negative half period of the input current and voltage, the first switch tube is a main tube, and the second switch tube is an auxiliary tube.
5. The method for controlling the totem-pole PFC with the variable-frequency self-adaptive dead time according to claim 4, wherein the high-frequency bridge arm driving signals are as follows: converting the calculated frequency value into a carrier wave with corresponding frequency, comparing the carrier wave with a modulation wave to obtain an original driving waveform, then enabling the driving waveform to enter a dead zone generation module, delaying the rising edge of the driving waveform, wherein the delay time is the calculated dead zone time, so that a driving waveform of a main switching tube of a high-frequency bridge arm of a totem-pole PFC is obtained, and the driving waveform is supplied to a second switching tube in the positive half period of the input alternating voltage and is supplied to the first switching tube in the negative half period of the input alternating voltage; and delaying the falling edge of the driving waveform, wherein the delay time is dead time obtained by calculation, obtaining the driving waveform of the auxiliary switching tube of the high-frequency bridge arm of the totem-pole PFC after negation, and the driving waveform is supplied to the first switching tube in the positive half period of the input alternating voltage and is supplied to the second switching tube in the negative half period of the input alternating voltage.
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN115425834A (en) * | 2022-09-07 | 2022-12-02 | 上海交通大学 | Totem-pole inductive current waveform correction method and system for variable high-frequency carrier |
| CN115811241A (en) * | 2023-02-08 | 2023-03-17 | 四川大学 | Single-stage bridgeless staggered parallel Boost-LLC AC-DC converter hybrid control method |
| CN115425834B (en) * | 2022-09-07 | 2024-05-14 | 上海交通大学 | Totem-pole inductance current waveform correction method and system with variable high-frequency carrier |
-
2022
- 2022-01-17 CN CN202210050258.7A patent/CN114400886A/en active Pending
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN115425834A (en) * | 2022-09-07 | 2022-12-02 | 上海交通大学 | Totem-pole inductive current waveform correction method and system for variable high-frequency carrier |
| CN115425834B (en) * | 2022-09-07 | 2024-05-14 | 上海交通大学 | Totem-pole inductance current waveform correction method and system with variable high-frequency carrier |
| CN115811241A (en) * | 2023-02-08 | 2023-03-17 | 四川大学 | Single-stage bridgeless staggered parallel Boost-LLC AC-DC converter hybrid control method |
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