CN110611444A - Novel bridgeless integrated AC-DC rectifying circuit and rectifying method - Google Patents

Novel bridgeless integrated AC-DC rectifying circuit and rectifying method Download PDF

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Publication number
CN110611444A
CN110611444A CN201910871624.3A CN201910871624A CN110611444A CN 110611444 A CN110611444 A CN 110611444A CN 201910871624 A CN201910871624 A CN 201910871624A CN 110611444 A CN110611444 A CN 110611444A
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switching tube
circuit
capacitor
stage
switch tube
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CN201910871624.3A
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CN110611444B (en
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潘尚智
王明龙
宫金武
查晓明
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Wuhan University WHU
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Wuhan University WHU
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Rectifiers (AREA)

Abstract

The invention provides a novel bridgeless integrated AC-DC rectifying circuit and a rectifying method, comprising the following steps: single-phase ac power, first inductor, etc. The post-stage DC-DC circuit includes, but is not limited to, a half-bridge LLC resonant circuit, a full-bridge LLC resonant circuit, a dual-active full-bridge conversion circuit, a dual-active half-bridge conversion circuit, and the like. The invention possesses two degrees of freedom of control, including: preceding stage control: the control object is a first bridge arm (low frequency), and the duty ratio of a switch tube of the bridge arm is adjusted in real time by a sine pulse width modulation method so as to realize the function of power factor correction and the adjustment of voltage on the direct current side output by the PFC; and (3) post-stage control: the control object is a second bridge arm (high frequency), and the output voltage of the rear-stage DC-DC circuit is adjusted in real time through frequency conversion control or phase-shift control; the control method enables the front and rear stages to be controlled separately. Meanwhile, the bridge arm can be shared with a post-stage DC-DC conversion circuit, so that the aim of improving the efficiency is fulfilled.

Description

Novel bridgeless integrated AC-DC rectifying circuit and rectifying method
Technical Field
The invention relates to the technical field of power electronic conversion, in particular to a novel bridgeless integrated AC-DC rectifying circuit and a method.
Background
At present, a large amount of bridge type uncontrolled rectification is used, so that not only is serious harmonic pollution caused to a power grid, but also waste of electric energy is caused due to low power factor of an alternating current side. The power factor correction technology can realize that the alternating current side current tracks the alternating current side voltage, and can improve the power factor of the alternating current side.
Power factor correction techniques must be able to achieve high power factor and low input current harmonics to meet IEC61000-3-2 harmonic standards. Therefore, a conventional power supply generally includes a two-stage power conversion structure, a Boost circuit used as a Power Factor Correction (PFC) circuit for realizing a high power factor and a low input current harmonic, and a DC-DC conversion circuit for outputting a required DC voltage. The two-stage circuit topology can enable the circuit to achieve optimal performance, such as high power factor, stable PFC output DC side voltage, and stable DC-DC output voltage. However, the two-stage structure has too many components, so that the power consumption is high, the efficiency is relatively low, the circuit control is complex, and most of the system loss is consumed in the rectifier diode.
Aiming at the problem of efficiency reduction caused by excessive number of components, two solutions are mainly provided, one is to improve the topological structure of the first-stage power factor correction circuit to form a bridgeless PFC structure so as to reduce the number of diodes and switching tubes as much as possible. At present, various bridgeless PFC circuits are available, such as a double-Boost PFC circuit, a double-inductor PFC circuit, a totem-pole PFC circuit and the like; the other method is to integrate the first-stage PFC circuit and the second-stage DC-DC circuit by sharing one bridge arm.
The learners combine the two solutions together, and provide a topological structure in which the totem-pole PFC and the post-stage DC-DC conversion circuit are integrated by sharing one bridge arm, so that the number of switching devices can be further reduced, but the circuit topology has only one control degree of freedom, the voltage on the output direct current side of the PFC is uncontrollable, and when the input voltage is increased to a certain degree, the voltage stress on the output direct current side of the PFC and the voltage stress on the switching devices are too high, so that the devices are easily damaged; in addition, because the voltage of the output direct current side of the PFC is uncontrollable, the voltage change is too large, and the parameter design of a post-stage DC-DC circuit is poor.
In order to solve the problem that the output dc voltage of the PFC is not controllable, some researchers have proposed a solution to achieve the purpose of controlling the output dc voltage of the PFC by combining pulse frequency modulation and pulse width modulation. When the voltage of the direct current side output by the PFC does not exceed a specified limit value, pulse frequency modulation is adopted; when the voltage of the output direct current side of the PFC approaches or exceeds a specified limit value, the purpose of reducing the voltage of the output direct current side of the PFC is achieved by changing the duty ratio in a mode of combining pulse frequency modulation and pulse width modulation, however, input harmonic current is increased, the power factor is reduced, and the duty ratio is limited by input voltage change, so that the working condition of a rear-stage DC-DC circuit is deteriorated, the design cannot be optimized, and the efficiency of the whole circuit is influenced to a certain extent.
Disclosure of Invention
The present invention is directed to overcoming the above-mentioned problems, and provides 1. a novel bridgeless integrated AC-DC rectifier circuit and method, comprising: the single-phase alternating current power supply, a first inductor, a first switching tube, a second switching tube, a third switching tube, a fourth switching tube and a rear-stage DC-DC circuit;
one end of the single-phase alternating current power supply is connected with one end of the first inductor; the other end of the single-phase alternating current power supply is connected with a drain electrode of the fourth switching tube; the other end of the first inductor and the first switch tube S1Is connected to the source of (a); the drain electrode of the first switching tube is connected with the drain electrode of the third switching tube; the source electrode of the first switch tube is connected with the drain electrode of the second switch tube; the source electrode of the third switching tube is connected with the drain electrode of the second switching tube; the source electrode of the second switching tube is connected with the source electrode of the fourth switching tube; the rear-stage DC-DC circuit is connected with the drain electrode of the third switching tube and the source electrode of the fourth switching tube;
the latter stage DC-DC circuit adopts half-bridge LLC resonant circuit, includes: the single-phase alternating-current power supply comprises a single-phase alternating-current power supply, a first inductor, a first switching tube, a second switching tube, a third switching tube, a fourth switching tube, a dc capacitor, a first capacitor, a second capacitor, a first transformer, a first diode, a second diode, a third capacitor and a first load resistor;
one end of the single-phase alternating current power supply is connected with one end of the first inductor; the other end of the single-phase alternating current power supply is connected with a drain electrode of the fourth switching tube; the other end of the first inductor and the first switch tube S1Is connected to the source of (a); the drain electrode of the first switching tube, the drain electrode of the third switching tube and the dc capacitor are connected with the anode of the first capacitor; the source electrode of the first switch tube is connected with the drain electrode of the second switch tube; the source electrode of the third switching tube and the drain electrode of the second switching tube are connected with one end of the primary side of the first transformer; the negative electrode of the first capacitor and the positive electrode of the second capacitor are connected with the other end of the primary side of the first transformer; the source electrode of the second switch tube, the source electrode of the fourth switch tube and the dc capacitor are connected with the negative electrode of the second capacitor; one end of the secondary side of the first transformer is connected with the anode of the first diode; the middle end of the first transformer is connected with the negative electrode of the third capacitor and one end of the first resistor; the third end of the secondary side of the first transformer is connected with the anode of a second diode; and the anodes of the first diode, the second diode and the third capacitor are connected with the other end of the first resistor.
2. The novel bridgeless integrated AC-DC rectification circuit according to claim 1, wherein the post-stage DC-DC circuit is a half-bridge LLC resonant circuit, a full-bridge LLC resonant circuit, a dual-active full-bridge conversion circuit, or a dual-active half-bridge conversion circuit.
The single-phase alternating current power supply is used for providing input alternating current power supply; the first inductor is used for storing and releasing energy; the first switching tube is used for controlling the output of direct-current voltage; the second switching tube is used for controlling the output of direct-current voltage; the third switching tube is used for controlling the output of direct-current voltage; the fourth switching tube is used for controlling the output of direct-current voltage; the dc capacitor is used for filtering and outputting direct-current voltage ripples; the first capacitor and the second capacitor are used for generating resonance with the inductor; the first load resistor is used for providing direct current voltage output; the first transformer is used for transmitting energy to an output side; the first diode is used for providing a current circulation path; the second diode is used for providing a current circulation path; and the third capacitor is used for filtering the direct-current voltage ripple at the output side.
A method of rectification using a novel bridgeless integrated AC-DC rectifier circuit, comprising:
preceding stage control: the control object is a first bridge arm, the first bridge arm is low-frequency, and the duty ratio of a switch tube of the bridge arm is adjusted in real time by a sine pulse width modulation method so as to realize the function of power factor correction and the adjustment of voltage on a PFC output direct current side;
and (3) post-stage control: the control object is a second bridge arm, the second bridge arm is high-frequency, and the output voltage of the rear-stage DC-DC circuit is adjusted in real time through frequency conversion control or phase-shift control;
the control method enables the front stage and the rear stage to be controlled respectively; meanwhile, the bridge arm can be shared with a rear-stage DC-DC conversion circuit, so that the aim of improving the efficiency is fulfilled;
the expression of the voltage on the DC side of the PFC output is as follows:
wherein, VdcRepresents the output voltage of the PFC direct current side; viRepresents an alternating-current-side input voltage; d1Bridge arm switch tube S with low frequency representation2Duty cycle of (d); d2Indicating high frequency bridge arm switch tube S3The duty cycle of (c).
Compared with the prior art, the invention has the following advantages:
the invention has two degrees of freedom of control. The first bridge arm is a low-frequency bridge arm, and the duty ratio of a switch tube of the bridge arm is adjusted in real time by a sine pulse width modulation method so as to realize the function of power factor correction and the adjustment of voltage on a PFC output direct current side; the second bridge arm is a high-frequency bridge arm, the duty ratio is fixed, the second bridge arm can share the bridge arm with a half-bridge LLC resonant DC-DC circuit, integration is realized, a soft switching effect is brought, and the purpose of improving efficiency is achieved.
Drawings
Fig. 1 is a circuit diagram of the system of the present invention.
Fig. 2 is a typical circuit diagram of a half-bridge LLC resonant DC-DC circuit followed by the system of the present invention.
FIG. 3: the driving signals of the switching tubes S3 and S4, input inductive current, resonant current, excitation inductive current and current waveforms flowing through the first diode and the second diode are in a stable working state of a typical circuit of the system.
Fig. 4 is an equivalent circuit diagram of a typical circuit of the system of the present invention during mode 1 of operation.
Fig. 5 is an equivalent circuit diagram of an exemplary circuit of the system of the present invention during mode 2 of operation.
Fig. 6 is an equivalent circuit diagram of an exemplary circuit of the system of the present invention during mode 3 of operation.
Fig. 7 is an equivalent circuit diagram of an exemplary circuit of the system of the present invention during mode 4 of operation.
Fig. 8 is an equivalent circuit diagram of an exemplary circuit of the system of the present invention during mode 5 of operation.
Fig. 9 is an equivalent circuit diagram of an exemplary circuit of the system of the present invention during mode of operation 6.
Detailed Description
In order to facilitate the understanding and implementation of the present invention for those of ordinary skill in the art, the present invention is further described in detail with reference to the accompanying drawings and examples, it is to be understood that the embodiments described herein are merely illustrative and explanatory of the present invention and are not restrictive thereof.
The circuit of this embodiment is shown in figure 1,
single phase ac power supply vinFirst inductance L1A first switch tube S1A second switch tube S2A third switching tube S3Fourth switch tube S4Dc capacitor CdcFirst capacitor C1First capacitor C2First transformer T1First diode D1Second, secondDiode D2Third capacitor C3And a first load resistor R1；
The single-phase AC power supply vinOne end of (1) and the first inductor L1Is connected with one end of the connecting rod; the single-phase AC power supply vinAnd the other end of the second switch tube S4Is connected with the drain electrode of the transistor; the first inductor L1And the other end of the first switch tube S1Is connected to the source of (a); the first switch tube S1The drain electrode of the third switching tube S3The positive electrode of the dc capacitor and the first capacitor C1The positive electrode of (1) is connected; the first switch tube S1Source electrode of and the second switch tube S2Is connected with the drain electrode of the transistor; the third switch tube S3Source electrode of, the fourth switching tube S4And the first transformer T1One end of the primary side is connected; the first capacitor C1Negative pole of (1), the second capacitor C2And the first transformer T1The other end of the primary side is connected; the second switch tube S2Source electrode of, the fourth switching tube S4Source of the dc capacitor, a cathode of the dc capacitor and the second capacitor C2The negative electrode of (1) is connected; the first transformer T1One end of the secondary side and the first diode D1The anode of (2) is connected; the first transformer T1An intermediate terminal and the third capacitor C3Negative electrode of (1), first resistor R1Is connected with one end of the connecting rod; the first transformer T1The third end of the secondary side and a second diode D2The anode of (2) is connected; the first diode D1The second diode D2The third capacitor C3And the first resistor R1The other end of the connecting rod is connected.
The following describes the embodiments of the present invention with reference to fig. 2 to 9:
setting a first inductance L1Has a current of iinAt a voltage vLFirst capacitor C1Has a voltage of vC1A second capacitor C2Has a voltage of vC2Third capacitor C3Has a voltage of vC3Output power from the DC side of PFCPressure vdc，vdc＝vC1+vC2Flows through the first diode D1Has a current of iD1Flows through the first diode D2Has a current of iD2Flows through the first transformer T1Current of leakage inductance is iLrFlows through the first transformer T1Current of exciting inductor is imFirst load resistance R1A voltage vo。
Due to S1，S2The working processes of the upper pipe and the lower pipe are symmetrical, so that only S is analyzed16 working stages when the upper pipe is opened. FIGS. 4-9 are circuit diagrams S of the circuit shown in FIG. 11A schematic diagram of an equivalent circuit of a working mode when the upper tube is turned on, wherein FIG. 4 is a first switch tube S1A third switch tube S3Conducting the second switch tube S2And a fourth switching tube S4Off, the first diode D1Forward conducting, second diode D2An equivalent circuit schematic diagram when reverse turn-off is performed; FIG. 5 shows the first switch tube S1A third switch tube S3Conducting the second switch tube S2And a fourth switching tube S4Off, the first diode D1A second diode D2An equivalent circuit schematic diagram when reverse turn-off is performed; FIG. 6 shows the first switch tube S1Conducting the second switch tube S2A third switch tube S3Turn-off and fourth switch tube S4Off, the first diode D1A second diode D2An equivalent circuit schematic diagram when reverse turn-off is performed; FIG. 7 shows the first switch tube S1And a fourth switching tube S4Conducting the second switch tube S2A third switch tube S3Turn-off, first diode D1Reverse turn-off, second diode D2An equivalent circuit schematic diagram when conducting in the forward direction; FIG. 8 shows the first switch tube S1A second switch tube S2A third switch tube S3Turn-off, fourth switch tube S4Conducting the first diode D1A second diode D2An equivalent circuit schematic diagram when reverse turn-off is performed; FIG. 9 shows the first switch tube S1A second switch tube S2A third switch tube S3And a fourth switching tube S4Off, the first diode D1A second diode D2And an equivalent circuit schematic diagram in reverse turn-off.
The working conditions of the modes are specifically analyzed, and the adjustment of the output voltage at the direct current side can be realized by adjusting the duty ratio of the low-frequency bridge arm, so that the first inductor L1Average current i in a single switching cycle ofLaveIs constant and i will not be listed again in each modal analysisinAnd vC1、vC2、vC3Using i in the steady state analysisLaveInstead of the first inductor L1Current value i ofin. It is to be noted that the following processes or parameters, if any, which are not specifically described in detail are understood or implemented by those skilled in the art with reference to the prior art.
As shown in FIG. 4, modality 1 corresponds to t of FIG. 30～t1Time period:
at t ═ t0While, the first switch tube S1A third switch tube S3Zero voltage on, second switch tube S2And a fourth switching tube S4Off, input current iinPasses through the first inductor L once1A first switch tube S1A third switch tube S3Then returns to the single-phase AC power supply vin. At this time, the inductor energy is increased and the inductor current iinLinearly rising, inductor current iinCan be expressed as:
at the same time, the first capacitor C1A third switch tube S3First transformer leakage inductance LrA first transformer resonant inductor LmA second capacitor C2Forming a resonant circuit, resonant current iLrSpecific exciting inductance current imLarge so that the current flowing through the primary side of the transformer is positive and negative, and the amplitude is the difference between the resonant current and the exciting current, therefore, the first diode D on the secondary side of the transformer1And conducting. The primary voltage of the transformer is clamped at nVoExciting inductance current is linearly increased, exciting inductance current iLrCan be expressed as:
at this stage, the resonant frequency is:at t1And at the moment, when the resonant inductor current is equal to the excitation inductor current, ending the mode 1 working mode.
As shown in FIG. 5, modality 2 corresponds to t of FIG. 31～t2Time period:
at t ═ t1While, the first switch tube S1A third switch tube S3Continuously turning on, inputting an inductive current iinThe linear increase continues until t is reached2The time reaches a maximum value. In addition, at t1Time of day, resonant inductor current iLrEqual to exciting inductance current imWhen the first diode is turned off, the first diode is turned off with zero current. In this mode, the first capacitor C1A third switch tube S3First transformer leakage inductance LrA first transformer resonant inductor LmA second capacitor C2Forming a resonant circuit, wherein the resonant frequency is as follows:in this mode, since the resonant current is equal to the exciting inductor current, the first and second diodes on the secondary side of the transformer are turned off in reverse directions, so that no energy is transferred to the secondary side. At t ═ t2While, the third switch tube S3Off, modality 2 ends.
As shown in FIG. 6, modality 3 corresponds to t of FIG. 32～t3Time period:
in this mode, corresponding to the dead time of the switching signal, the third switch tube S is now in the process3And a fourth switching tube S4Turn off, input of inductor current iinLinear decrease, the relation of the relevant electrical parameters in this modeComprises the following steps:
due to the third switch tube S3And a fourth switching tube S4The presence of parasitic capacitances, to which the excitation current is discharged, thus realizes the fourth switching tube S4The zero voltage of (2) turns on. When t is equal to t3While, the fourth switch tube S4And (4) opening.
As shown in FIG. 7, modality 4, corresponding to t of FIG. 33～t4Time period:
at t ═ t3While, the fourth switch tube S4The drain-source voltage will be zero, therefore, the fourth switch tube S4The zero voltage turns on. In this mode, the inductor current i is inputinContinuing to linearly decrease; because the fourth switch tube S4Conducting so that the input voltage of the resonant tank is zero. In this mode, the resonance current is larger than the exciting inductance current, and the secondary side of the transformer is provided with a second diode D according to the polarity relation of the transformer2The forward direction is conducted, the primary voltage of the transformer is clamped at-nVoExcitation inductance current imThe linear decrease, the magnetizing inductor current can be expressed as:
at t ═ t4When the resonant current is equal to the exciting inductance current, the mode 4 is finished.
As shown in FIG. 8, modality 5 corresponds to t of FIG. 34～t5Time period:
fourth switch tube S4Keeping on state, when t is t4While the resonance current is equal to the exciting inductor current, a second diode D2Zero current turn-off, at t ═ t5While, the fourth switch tube S4The switch-off, the mode 5 end,
as shown in FIG. 9, modality 6, corresponding to t of FIG. 35～t6Time period:
in this mode, all the primary side switching tubes and the secondary side diodes are in the off state, which is the same as mode 3, because the third switching tube S3And a fourth switching tube S4Due to the existence of the parasitic capacitors, the excitation current discharges to the parasitic capacitors, and zero-voltage switching-on of the third switching tube is realized. When t is equal to t6While, the third switch tube S3And (4) opening.
The 6 working stages when the second switch tube is switched on are similar to the above, and are not described in detail herein.
According to the analysis of the above modes, the first inductance L is1And analyzing the relation among all parameters of the system under the steady state condition by using a volt-second balance principle, wherein variables represented by capital characters below are steady state values of corresponding variables. Provided with a first switch tube S1The time of opening is (1-D)1)Ts1A second switch tube S2Time of opening is D1Ts1A third switching tube S3Time of opening is D2Ts2Fourth switch tube S4The time of opening is (1-D)2)Ts2Wherein D is1Is a first switch tube S1Duty cycle of (1-D)1) Is a second switch tube S2Duty ratio of D2For a third switching tube S3Duty cycle of (1-D)4) Is a fourth switching tube S4The duty cycle of (c). T iss1，Ts2Is a switching period, and Ts1Greater than Ts2. For the first inductance L1The method is obtained by applying a volt-second balance principle:
finishing the formula (5) to obtain:
the above-mentioned embodiment is a typical circuit of the system of the present invention, but the implementation manner of the present invention is not limited by the above-mentioned embodiment, and a typical circuit formed by changing the DC-DC circuit (including but not limited to a half-bridge LLC resonant circuit, a full-bridge LLC resonant circuit, a dual-active full-bridge inverter circuit, a dual-active half-bridge inverter circuit, etc.) of the latter stage of the system of the present invention is included in the protection scope of the present invention.
The above-mentioned embodiments are preferred embodiments of the present invention, but the present invention is not limited to the above-mentioned embodiments, and any other changes, modifications, substitutions, combinations, and simplifications which do not depart from the spirit and principle of the present invention should be construed as equivalents thereof, and all such changes, modifications, substitutions, combinations, and simplifications are intended to be included in the scope of the present invention.
It should be understood that the above description of the preferred embodiments is given for clarity and not for any purpose of limitation, and that various changes, substitutions and alterations can be made herein without departing from the spirit and scope of the invention as defined by the appended claims.

Claims (3)

1. A novel bridgeless integrated AC-DC rectification circuit and method are characterized by comprising the following steps: the single-phase alternating current power supply, a first inductor, a first switching tube, a second switching tube, a third switching tube, a fourth switching tube and a rear-stage DC-DC circuit;
one end of the single-phase alternating current power supply is connected with one end of the first inductor; the other end of the single-phase alternating current power supply is connected with a drain electrode of the fourth switching tube; the other end of the first inductor and the first switch tube S1Is connected to the source of (a); the drain electrode of the first switching tube is connected with the drain electrode of the third switching tube; the source electrode of the first switch tube is connected with the drain electrode of the second switch tube; the source electrode of the third switching tube is connected with the drain electrode of the second switching tube; the source electrode of the second switching tube is connected with the source electrode of the fourth switching tube; the rear-stage DC-DC circuit is connected with the drain electrode of the third switching tube and the source electrode of the fourth switching tube;
the latter stage DC-DC circuit adopts half-bridge LLC resonant circuit, includes: the single-phase alternating-current power supply comprises a single-phase alternating-current power supply, a first inductor, a first switching tube, a second switching tube, a third switching tube, a fourth switching tube, a dc capacitor, a first capacitor, a second capacitor, a first transformer, a first diode, a second diode, a third capacitor and a first load resistor;
one end of the single-phase alternating current power supply is connected with one end of the first inductor; the other end of the single-phase alternating current power supply is connected with a drain electrode of the fourth switching tube; the other end of the first inductor and the first switch tube S1Is connected to the source of (a); the drain electrode of the first switching tube, the drain electrode of the third switching tube and the dc capacitor are connected with the anode of the first capacitor; the source electrode of the first switch tube is connected with the drain electrode of the second switch tube; the source electrode of the third switching tube and the drain electrode of the second switching tube are connected with one end of the primary side of the first transformer; the negative electrode of the first capacitor and the positive electrode of the second capacitor are connected with the other end of the primary side of the first transformer; the source electrode of the second switch tube, the source electrode of the fourth switch tube and the dc capacitor are connected with the negative electrode of the second capacitor; one end of the secondary side of the first transformer is connected with the anode of the first diode; the middle end of the first transformer is connected with the negative electrode of the third capacitor and one end of the first resistor; the third end of the secondary side of the first transformer is connected with the anode of a second diode; and the anodes of the first diode, the second diode and the third capacitor are connected with the other end of the first resistor.
2. The novel bridgeless integrated AC-DC rectification circuit according to claim 1, wherein the post-stage DC-DC circuit is a half-bridge LLC resonant circuit, a full-bridge LLC resonant circuit, a dual-active full-bridge conversion circuit, or a dual-active half-bridge conversion circuit.
3. A method of rectification using the novel bridgeless integrated AC-DC rectifier circuit of claim 1, comprising:
preceding stage control: the control object is a first bridge arm, the first bridge arm is low-frequency, and the duty ratio of a switch tube of the bridge arm is adjusted in real time by a sine pulse width modulation method so as to realize the function of power factor correction and the adjustment of voltage on a PFC output direct current side;
and (3) post-stage control: the control object is a second bridge arm, the second bridge arm is high-frequency, and the output voltage of the rear-stage DC-DC circuit is adjusted in real time through frequency conversion control or phase-shift control;
the control method enables the front stage and the rear stage to be controlled respectively; meanwhile, the bridge arm can be shared with a rear-stage DC-DC conversion circuit, so that the aim of improving the efficiency is fulfilled;
the expression of the voltage on the DC side of the PFC output is as follows:
wherein, VdcRepresents the output voltage of the PFC direct current side; viRepresents an alternating-current-side input voltage; d1Bridge arm switch tube S with low frequency representation2Duty cycle of (d); d2Indicating high frequency bridge arm switch tube S3The duty cycle of (c).
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