CN114257097A - Multi-mode switching wide-output direct current converter and switching control thereof - Google Patents

Multi-mode switching wide-output direct current converter and switching control thereof Download PDF

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CN114257097A
CN114257097A CN202111588111.5A CN202111588111A CN114257097A CN 114257097 A CN114257097 A CN 114257097A CN 202111588111 A CN202111588111 A CN 202111588111A CN 114257097 A CN114257097 A CN 114257097A
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mode
output
converter
inductor
voltage
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CN114257097B (en
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何志兴
刘阳
侯仁杰
董宏宇
罗安
管仁锋
李宗鉴
周芊帆
陈燕东
周乐明
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Hunan University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention discloses a multi-mode switching wide-output direct current converter and switching control thereof1、S2、S3、S4The duty cycle controls the output voltage. The multi-mode switching wide output DC converter can work in three modes, namely a High Gain (HG) mode, a Medium Gain (MG) mode and a Low Gain (LG) mode. In different modes, the coupling inductance circuit not only plays the role of a filter inductance, but also plays the role of a transformer, so that the power density is improved, and meanwhile, the direct current converter can realize zero voltage switching-on of all switching tubes in a wide input working range in an HG mode and an MG mode, thereby effectively reducing the switching-on and switching-off frequencyLoss is reduced and conversion efficiency is improved.

Description

Multi-mode switching wide-output direct current converter and switching control thereof
Technical Field
The invention relates to the technical field of switching converters, in particular to a method for realizing wide-range work of a direct current converter in the technical field of power electronics.
Background
With the rapid development of complex applications such as renewable energy power generation, hybrid electric vehicles, submarine cable observation stations and the like, the demand for realizing high-efficiency electric energy conversion in a wide range is more and more urgent. Wide voltage gain dc converters have become an integral part of such converters. High efficiency, high power density, wide voltage gain, low cost and stable and reliable operation are key requirements for such converters. In addition, special requirements such as low current ripple are even key technical indexes of the submarine cable observation station.
The LLC resonant converter has the characteristics of zero-voltage switching-on of the main power transistor, high power density, etc., and has been widely applied to high-efficiency power converters, but when the conventional LLC resonant converter is applied in a wide-range output field, the Frequency Modulation (FM) or Pulse Width Modulation (PWM) control methods face respectively an excessively wide frequency range, and ZVS is difficult to achieve in a light-load state, and a large reactive circulating current reduces the converter efficiency, and cannot meet the application requirements of a wider working range.
In addition, in the traditional voltage type direct current converter, the voltage stress of a switching tube is relatively fixed, the output voltage is controlled visually, but a short-circuit protection circuit with rapid action time is needed, the input current ripple is relatively large, and the direct current converter is not suitable for occasions requiring long service life of equipment, such as a submarine cable observation station and the like.
Disclosure of Invention
The invention aims to solve the technical problem that the direct current converter working in a wide range and the control method thereof are provided aiming at the defects of the prior art, so that zero voltage switching-on is realized during the wide-range working, the switching loss of the converter is reduced, and the electric energy conversion of low current ripples at the input end is realized.
In order to solve the technical problems, the technical scheme adopted by the invention is as follows:
a multi-mode switching wide-output direct current converter comprises a coupling inductance circuit 10, wherein the coupling inductance circuit 10 is electrically connected with a staggered parallel circuit 20 and a resonant cavity 30, and the resonant cavity 30 is electrically connected with a transformer 40, a rectifier 50 and an output capacitor in sequence; the coupling inductance circuit 10 is electrically connected to the rectifier 50;
the coupled inductor circuit 10 includes a winding Np1And winding two Np2Winding one Np1And winding two Np2A first diode D is electrically connected after being connected in parallel1First diode D1Electrically connected with windings three N arranged in parallelp1And winding four Np2(ii) a Winding three Np1Excitation inductance L equivalent to coupling inductancem1And a first diode D1Connected leakage inductance-Ls1(ii) a Four N windingsp2Excitation inductor two L equivalent to coupling inductorm2And a first diode D1Connected leakage inductance two Ls2(ii) a Winding three Np1And winding four Np2Electrically connected to the interleaved parallel circuit 20; the interleaved parallel circuit 20 comprises a first bridge arm and a second bridge arm in a half-bridge structure, and the interleaved parallel circuit 20 is connected with a clamping capacitor C in parallelc(ii) a The resonant cavity 30 includes resonant inductors L connected in series in sequencerAnd an excitation inductor LmAnd a resonance capacitor Cr。
In a further improvement, the coupled inductor circuit 10 further includes a coupled inductor N electrically connected to the rectifier 50s1And a coupling inductor two Ns2Coupled inductor one Ns1And a coupling inductor two Ns2Connected in series, and having winding inductance and transformation ratioThe same is true.
In a further development, the coupling inductance is Ns1And a coupling inductor two Ns2After the different name ends are connected, coupling inductance Ns1Serially connected diodes two D in sequence2And an output inductor Lf(ii) a Diode two D2Electrically connected diode three D3Cathode of (2), diode three D3Anode of the inductor is electrically connected with the coupling inductor II Ns2And an output negative terminal.
In a further improvement, the first bridge arm comprises a first switching tube S1 and a third switching tube S2 which are connected in series; the second bridge arm comprises a second switching tube S2 and a fourth switching tube S4 which are connected in series.
The use method of the multi-mode switching wide-output direct current converter comprises the following steps:
s1, collecting input voltage V of direct current converteriOutput voltage Vo；
S2, collecting input voltage ViWith a given output voltage command value Vo *And sending the data to a controller of the direct current converter for mode judgment, and confirming the adjustment control quantity:
s21, when the given output voltage instruction value Vo *Is greater than or equal to the input voltage ViBoundary value M with HG modal gainHGBThe transformer operates in HG mode;
s22, when the given output voltage instruction value Vo *Less than the input voltage ViAnd HG modal gain MHGBAnd is greater than or equal to the input voltage ViBoundary value M with MG modal gainMGBThe converter operates in the MG mode;
s23, when the given output voltage instruction value Vo *Less than the input voltage ViBoundary value M with MG modal gainMGBThe transformer operates in the LG mode;
s3, collecting the output voltage VoSubtracting the given voltage command value Vo to obtain a voltage error, sending the voltage error to a proportional-integral controller, and then sending the output Vcon of the proportional-integral controller to the controller for duty ratioRatio adjustment is carried out to obtain PWM waves meeting corresponding D, Ds and beta; wherein D represents a duty ratio, Ds represents a control amount introduced in the MG mode, and β represents a phase shift angle between the first arm and the second arm;
s4, sending the PWM wave to the drive circuit of the DC converter to obtain a control switch tube S1A second switch tube S2And a switch tube III S3And a switch tube four S4Drive signal g of1、g2、g3、g4。
In a further improvement, when the direct current converter works in an HG mode, the phase shift beta between the switch driving signals in the first bridge arm and the second bridge arm in the staggered parallel network is 180 degrees, the phase shift beta is complementary with the switch driving signals in the bridge arms, and the output voltage is adjusted by adjusting the duty ratio D of the switch tubes on the first bridge arm and the second bridge arm.
In a further improvement, when the direct current converter works in the HG mode, the duty ratio D regulating interval is 0.36-0.7.
In a further improvement, when the direct current converter works in an MG mode, the phase shift beta between the switch driving signals in the first bridge arm and the second bridge arm in the staggered parallel network is 180 degrees, and a control variable D is introduceds，DsIs a switch tube two S2Drive signal g of2And a switching tube S1The phase difference of the drive signal g 1; switch tube three S3And a switch tube four S4Is constant at 0.7 by adjusting DsThe output voltage is regulated.
In a further improvement, when the DC converter operates in the MG mode, DsThe regulating interval is 0-0.15.
In a further improvement, when the direct current converter works in the LG mode, the switch driving signals in the first bridge arm and the second bridge arm in the staggered parallel network have no phase shift, and the input voltage V of the resonant cavityABIs 0, diode two D2Starting to conduct by adjusting the switch tube I S1And a switch tube III S3The duty cycle D of (a) regulates the output voltage.
Compared with the prior art, the invention has the beneficial effects that:
1. the wide-output direct-current converter provided by the invention adopts an interleaving structure, the input current ripple is obviously reduced, and the input current is divided into two transmission paths, so that the current stress of a switch tube in an interleaving parallel circuit is reduced.
2. The LLC resonant cavity is introduced into the wide-output direct-current converter structure provided by the invention, a wider zero-voltage switching-on range can be realized by utilizing resonant current, and the overall efficiency of the converter is higher.
3. The wide-output direct-current converter provided by the invention realizes high power density through multiplexing of the coupling inductor and the switching tube, and the circuit structure is simple and feasible.
4. The wide-output direct current converter provided by the invention can work in three modes by switching the modulation mode, and adjust the output voltage by adjusting the duty ratio, so that the wide-output direct current converter has a wider gain range. And under HG, MG mode of operation, all switch tubes can all realize zero voltage switch, and switching loss is little.
Drawings
FIG. 1 is an example of a topology of a wide output DC converter of the present invention;
FIG. 2a is a first main operating waveform of a wide output DC converter in HG mode according to an embodiment of the present invention;
FIG. 2b is a second main operating waveform of the wide output DC converter in the HG mode according to the embodiment of the present invention;
FIG. 3 shows the main operating waveforms of the wide output DC converter in MG mode according to the embodiment of the present invention;
FIG. 4 shows the main operating waveforms of the wide output DC converter in LG mode according to the present invention;
FIG. 5 is a schematic diagram illustrating the division of the operating ranges of three modes of the wide-output DC converter according to the embodiment of the present invention;
FIG. 6 is a control block diagram of a wide output DC converter in accordance with an embodiment of the present invention;
wherein, 10 coupling inductance circuits, 20 interleaving parallel circuits, 30 resonant cavities, 40 transformers, 50 rectifiers and CcClamping capacitor, CiInput bus capacitance, the couplingThe inductive circuit comprises N connected with the interleaving parallel networkp1、Np2A winding; and D1N in seriesp11、Np21A winding; n at the outputs1、Ns2A winding; wherein L iss1、Ls2Are respectively Np1、Np2Leakage inductance, L of the windingm1、Lm2Excitation inductance equivalent to coupling inductance, S1、S2、S3、S4Switching tube, LrResonant inductor, CrResonant capacitance, LmExcitation inductance, L of transformerfFilter inductor, CoOutput capacitance, D2To and coupling an inductance Ns1、Ns2Diode with series windings, D3Is connected in parallel to the coupling inductor Ns1、Ns2Winding and D2The diodes and R at two ends of the series branch circuit are loads;
g1～g4are respectively S1～S4A driving signal of the switching tube; vABOutputting a voltage for the midpoint of the interleaved parallel circuit; i isLr、ILmAre respectively a current-flowing resonant inductor LrAnd excitation inductance LmThe current of (a); vLs1、VLs2Respectively is leakage inductance Ls1、Ls2The voltage across; vLm1、VLm2Excitation inductance L, each being a coupling inductancem1、Lm2The voltage across; i is1、I2Respectively leakage inductance L flowing through the coupling inductances1、Ls2The current of (a); i isS1、IS2Respectively a flow-through switch tube S1、S2The current of (a); vLfIs a filter inductor LfVoltage across, ID2To flow through a diode D2Current of output voltage Vo。
Detailed Description
The topology structure of the wide-output direct-current converter provided by the invention is shown in fig. 1 and comprises a 10-coupled inductor circuit, a 20-interleaved parallel circuit, a 30-resonant cavity, a 40-transformer and a 50-rectifier. I isiAs a total input current, I1、I2Respectively, the leakage current flowing through the coupling inductorFeeling Ls1、Ls2The current of (a); vABOutputting a voltage for the midpoint of the interleaved parallel circuit; i isLr、ILmAre respectively a current-flowing resonant inductor LrAnd excitation inductance LmThe current of (a); i isS1、IS2Respectively a switching tube S flowing through the first bridge arm1、S2The current of (2).
By changing the modulation method, the wide-output direct-current converter provided by the invention can respectively work in HG, MG and LG working modes: under the HG working mode, the working process of the wide-output direct-current converter is the working process of the traditional LLC resonant converter, and the resonant cavity is formed by an excitation inductor LmResonant inductor LrResonant capacitor CrThe transformer has a transformation ratio n equal to n1:n2(ii) a In MG operation mode, D is introducedsTo adjust the output voltage gain; in LG working mode, the phase shift angle of two half-bridge arms which are connected in parallel in a staggered mode is zero, and a resonant cavity VABThe input voltage of (a) is zero and the output voltage is regulated by a variable duty cycle D, the circuit operating in the same way as a forward converter. Two coupled inductors participate in the circuit as a transformer in a forward converter topology, NP11、NP21The winding is a magnetic field reset winding of a transformer, Ns1、Ns2The winding provides energy output to the load end, and the inductor LfAs output filter inductor, flowing through LfHas a current of ILfDefining the turn ratio n of the primary and secondary windings of the coupled inductorIC＝ns1:np1＝ns2:np2，nIC2＝np11:np1＝np21:np2。
In three working modes, the interleaved parallel circuit always works at a resonance frequency point, and the switching between the modes can be realized by changing a switch pulse signal modulation method:
(1) in HG mode, a fixed switching frequency Pulse Width Modulation (PWM) control method is adopted, and the switching frequency f is in a rated conditionsEqual to LLC resonant frequency fr. And the switches on the same bridge arm run complementarily. S1And S3The duty cycles of the switching pulses of (a) are the same,but with a 180 ° phase shift angle (β 180 °), S2And S4The same is true.
(2) In MG mode, the controlled variable D is introducedsIncreasing the dead time between switching tubes on the same bridge arm at D>At 0.5, a lower voltage gain is achieved, at which time S1And S3With the same duty cycle, but with a 180 ° phase shift angle (β 180 °), S2And S4As well as so.
(3) In LG mode, the switching tube S1And S3Simultaneously switched on or off (beta 0 deg.), S2And S4The same is true.
Input voltage V of resonant cavity in HG and MG working modesABIs an amplitude of VCc(equal to V)iAC square wave of/D), duty ratio equal to minimum value N of D and 1-Ds1And Ns2The total voltage in between is equal to 0. Due to the coupling of the inductor L1、L2Are the same, thus I1、I2Are the same and equal to Iin/2。I1And IiRespectively, is represented as Δ ILsAnd Δ Ii. Definition m ═ Lm/Lr,ωr＝2πfr,Zr＝Lr/Cr,
Figure BDA0003428280430000051
Fig. 2a and 2b show the main operating waveforms of the proposed wide output dc converter operating in HG mode.
In the HG mode, one switching period can be divided into 10 working modes, and the front 5 working modes are mainly described as the front and the rear 5 working modes are symmetrical;
working mode 1[ t ]0-t1]：t0Before time of day, S3Has been turned on, S1At t0The zero voltage is turned on at time. Excitation voltage VLmIs output with a voltage VoClamping, ILmIncreasing in the negative direction. Resonant cavity VABHas an input voltage of zero and a resonant current ILrWith a sinusoidal negative decay. Furthermore, Ls1、Ls2The voltage across both ends being equal to VCc-Vi-VLBoth are discharging. Due to S1And S3Has been turned on, S2And S4Quilt VCcAnd (4) clamping. Current ILr、ILmAnd voltage VCrCan be expressed as:
Figure BDA0003428280430000052
working mode 2[ t ]1-t2]: at t1Time of day, ILrIs equal to ILm. In this mode, the secondary winding of the transformer has no current and does not transfer energy to the secondary. L isr、Lm、CrForm resonance with a resonance frequency fm. Due to LmThe value is far greater than Lr，ILrEssentially unchanged in this mode. In this mode, S1And S3Always conducting, inductor Ls1、Ls2Release energy, S2And S4Voltage V of the capacitorCcAnd (4) clamping. Current ILr、ILmAnd voltage VCrCan be expressed as:
Figure BDA0003428280430000053
working mode 3[ t ]2-t3]: at t2Time of day, S3Off, S1And conducting. The converter enters S3And S4The dead zone section of (2). The diodes of the rectifier bridge are turned off and no energy is transferred to the secondary side. S3And S4The junction capacitance of (a) starts to charge and discharge respectively.
Working mode 4[ t ]3-t4]: at t3Time of day, Coss4The voltage across the two terminals drops to zero, S4Achieving ZVS conduction. In this mode, the resonant cavity VABHas an input voltage of VCc，VLmIs clamped by the output voltage. L isrAnd CrParticipating in resonance and having a dominant resonant current ILrIs in sine curveThe line increases. L iss1And Ls2Respectively at a voltage of VCc–Vi+VHAnd Vi–VH. In addition, since S1And S4Conduction, Ls1And Ls2Are discharged and charged, respectively. S2、S3Voltage V of the capacitorCcAnd (4) clamping. Voltage V of resonant capacitorCrAnd current ILr、ILmCan be expressed as:
Figure BDA0003428280430000061
working mode 5[ t ]4-t5]: at t4Time of day, S4Off, S1And continuing to conduct. The converter enters S again3And S4The dead time of (d). In this mode, S3And S4Respectively through ILrAnd I2Discharging and charging. When S is3When the junction capacitance voltage drops to zero, S3The body diode of (a) starts conducting. Thus, S3Zero voltage turn-on is achieved.
The working mode when D is less than or equal to 0.5 is in a symmetrical state with the description.
Fig. 3 exemplarily shows main operation waveforms of the proposed wide output dc converter operating in the MG mode:
in the MG mode, one switching period can be divided into 8 working modes, and the front and rear 4 working modes are symmetrical and mainly describe the front 4 working modes;
working mode 1[ t ]0-t1]: before this mode, S3Has been turned on, S2Off, Ls1，Ls2Voltage on is equal to VCc-Vi-VLElectrical energy is released. t is t0The latter modality is similar to the working modality 2, t of the HG mode0Time of day, ILrAnd ILmEqual, Lr、Lm、CrForm resonance with a resonance frequency fm. In this mode, the transformer does not transfer energy to the secondary side. Current ILr、ILmAnd electricityPressure VCrCan be expressed as:
Figure BDA0003428280430000062
working mode 2[ t ]1-t2]: in this mode, S3And S4All are turned off and the converter enters dead time, consistent with the HG mode.
Working mode 3[ t ]2-t3]: at t2Time of day, S4Achieving ZVS turn-on. This modality is similar to modality 4 of the HG mode, where Ls1And Ls2Respectively at a voltage of VCc–Vi+V1And Vi–V1. Due to S1And S4Conduction, Ls1And Ls2And respectively discharging and charging. Current ILr、ILmAnd voltage VCrCan be expressed as:
Figure BDA0003428280430000063
working mode 4[ t ]3-t4]: at t3Time of day, S4Off, S1Is still conducting. This mode is the main difference between the HG mode and the LG mode. In this mode, VABIs zero, Ls1、Ls2Voltage across is equal to VCc–Vi–VLBoth release energy, ILrLinearly decreasing. Current ILr、ILmAnd voltage VCrCan be expressed as:
Figure BDA0003428280430000064
t4after that, the circuit enters the next half of the working state, and the working principle is similar to that of the first half period.
Fig. 4 exemplarily shows main operation waveforms of the proposed wide-output dc converter operating in LG mode:
in LG mode, S1And S3Simultaneous on and off (beta 0 deg.), S2And S4The same is true. Resonant cavity input voltage VABAt zero, the output voltage is regulated with a varying duty cycle D, at which point the circuit operates in a manner similar to a forward converter. Under the LG mode, a switching cycle can be divided into 6 working modes, and because front and back 3 modes are symmetrical, the first 3 working modes are mainly described:
working mode 1[ t ]0-t1]：t0Before time of day, S1，S3Has been turned on. During this dead time, S1And S3The junction capacitor starts to charge S2And S4The junction capacitance of (a) starts to discharge. L iss1And Lm1Respectively at a voltage of VL2、Vi–VCc–VL2. By a diode D1Winding Np11、Np21The magnetic reset circuit is connected, and the energy is applied to the input capacitor C1Charging, effectively preventing winding Np1、Np2The too high reverse peak voltage is generated to break down the switch tube of the interleaving parallel circuit. Winding NS1And NS2The sum of the voltages of (A) and (B) is negative, D3On, D2And (5) disconnecting. L isfThe voltage across is-Vo。
Working mode 2[ t ]1-t2]: at t1Time of day, S2，S4And conducting. In this mode, diode D2、D3Secondary winding N of coupling inductor still conductingS1、NS2Are clamped to zero and the current flowing through them increases. L isf、Lm1、Ls1The voltages at both ends are respectively-Vo0 and Vi。
Working mode 3[ t ]2-t3]: at the beginning of this mode, diode D3Is turned off and flows through D2Has a current of ILf. By a coupling inductance L1And L2Power is delivered to the load. L isf、Ls1The voltages at both ends are respectively 2nIC(Vi–VH2)–VoAnd VH2。
Working mode 4[ t ]3-t4]: this interval is the dead time, S1And S3The junction capacitance of (1) begins to discharge, S2And S4The junction capacitance of (a) starts to charge.
Working mode 5[ t ]4-t5]: at the beginning of this mode, S1、S3On, diode D3Continued conduction of winding NS1、NS2The voltage across is clamped to zero and the current flowing through it is reduced. L isf、Lm1、Ls1The voltages at both ends are respectively-Vo0 and Vi–VCc。
Working mode 6[ t ]5-t6]: at t2At the moment, flow through D2Is equal to zero, diode D2And closing. L isf、Lm1、Ls1The voltages at both ends are respectively-Vo、Vi–VCc–VL2And VL2. Diode D1And when the magnetic reset circuit is conducted, the magnetic reset circuit is switched on again to work.
Fig. 5 exemplarily shows an operation region division schematic diagram of the proposed wide output dc converter:
the wide-output direct-current converter provided by the invention adopts a fixed switching frequency pulse width modulation technology to regulate the output voltage, and according to the working mode analysis, the resonant circuit and the forward circuit are connected in parallel at the load end. The voltage gains of the three modes are independent. In the HG mode, the converter can be regarded as a combination of a Boost converter and a full-bridge LLC converter, and their voltage gains do not affect each other. In the MG mode, the duty ratio D is fixed to 0.7 and the controlled variable is Ds. Similarly, the Boost converter and the LLC converter can be analyzed separately in MG mode. In the LG mode, the circuit operates like a forward circuit.
Because the converter works in the HG and MG modes like the combination of a Boost converter and a full-bridge LLC converter, the gain expression is as follows:
Figure BDA0003428280430000081
wherein M isLLCIs the gain, M, of LLC resonant converterBOOSTOutput voltage gain, V, of Boost circuit for coupling inductor with interleaved parallel circuitoTo output a voltage, ViThe input voltage, n is the transformer transformation ratio, and D is the duty ratio of the interleaved parallel circuit. As D increases, the converter gain will decrease.
In MG and LG modes, the gains of the inverters can be expressed as:
Figure BDA0003428280430000082
Figure BDA0003428280430000083
wherein, the intermediate expressions X and Y:
Figure BDA0003428280430000084
fsfor interleaving the switching frequency, L, of the parallel circuits1Is Ns1Leakage inductance of the winding, nICFor primary winding turns ratio of coupled inductor, LfR is the load resistance value.
Under the MG mode, the duty cycle can not be too little in order to guarantee that the magnetic core normally resets, and when output was great among the forward circuit simultaneously, switching loss was great and the gain descends, combines the efficiency and the gain characteristics of HG mode, MG mode, LG mode, divides three mode according to following two conditions with the work area:
(1) boundary conditions of HG and MG modes: d is 0.7, Ds＝0。
(2) Boundary conditions of MG and LG modes: β is 0, D is 0.57, β represents the phase shift angle between the first leg and the second leg.
According to the analysis, the boundary voltage gain M of the HG mode is 0.7D and 0.4QHGBAbout 0.814, the boundary voltage gain M of LG modeLGBBy changing D to 0.57 and minusSubstitution of Loading conditions into MLGAnd obtaining the expression.
Fig. 6 exemplarily shows a control block diagram of the proposed wide output dc converter:
the wide output DC converter adopts voltage single closed loop control. Input voltage V by sensoriAn output voltage VoSet reference value V of output voltageoSent to the controller. Firstly, input voltage V is inputtediAnd an output voltage reference VoAnd sending the data to a mode selection controller, and determining the working mode of the converter by combining the working area division schematic diagram in fig. 5. At the same time, the sampled output voltage VoAnd an output voltage reference VoComparison, the difference is transmitted to Proportional Integral (PI) controller, which outputs signal VconSending the signal to a duty ratio adjusting controller corresponding to the working mode to adjust D or Ds. Different working modes correspond to different duty ratio calculation programs, namely different modulation modes. When V isiAnd VoWhen changed, the circuit will switch smoothly between HG, MG and LG modes.

Claims (10)

1. The multi-mode switching wide-output direct current converter is characterized by comprising a coupling inductance circuit (10), wherein the coupling inductance circuit (10) is electrically connected with a staggered parallel circuit (20) and a resonant cavity (30), and the resonant cavity (30) is sequentially electrically connected with a transformer (40), a rectifier (50) and an output capacitor; the coupling inductance circuit (10) is electrically connected with the rectifier (50); the coupled inductor circuit (10) comprises a winding I (N)p1) And winding two (N)p2) Winding one (N)p1) And winding two (N)p2) A first diode (D) is electrically connected after being connected in parallel1) First diode (D)1) Electrically connected with a winding III (N) arranged in parallelp1) And winding four (N)p2) (ii) a Winding three (N)p1) Excitation inductor I (L) equivalent to coupling inductorm1) And a first diode (D)1) Leakage inductance of connection one (L)s1) (ii) a The winding is four (N)p2) Excitation inductor two (L) comprising equivalent coupling inductorm2) And a first diode (D)1) Connected leakage inductance two (L)s2) (ii) a Winding three (N)p1) And winding four (N)p2) Is electrically connected with the interleaved parallel circuit (20); the staggered parallel circuit (20) comprises a first bridge arm and a second bridge arm in a half-bridge structure, and the staggered parallel circuit (20) is connected with a clamping capacitor (C) in parallelc) (ii) a The resonant cavity (30) comprises resonant inductors (L) which are sequentially connected in seriesr) Excitation inductor (L)m) And a resonance capacitor (C)r)。
2. The multi-mode switching wide output dc converter according to claim 1, wherein the coupled inductor circuit (10) further comprises a coupled inductor one (N) electrically connected to the rectifier (50)s1) And a coupled inductor two (N)s2) Coupled inductor one (N)s1) And a coupled inductor two (N)s2) The series connection, and winding inductance value, transformation ratio all are the same.
3. A multi-mode switching wide output DC converter as claimed in claim 2, wherein said coupled inductor one (N)s1) And a coupled inductor two (N)s2) After the different name ends are connected, the first (N) inductor is coupleds1) A second diode (D) is connected in series in sequence2) And an output inductor (L)f) (ii) a Diode two (D)2) Electrically connected diode three (D)3) Cathode of diode three (D)3) The anode of the second inductor is electrically connected with the coupling inductor II (N)s2) And an output negative terminal.
4. The multi-mode switching wide output dc converter according to claim 3, wherein the first leg includes a first switching tube (S1) and a third switching tube (S2) connected in series; the second bridge arm comprises a second switching tube (S2) and a fourth switching tube (S4) which are connected in series.
5. A method of using a multi-mode switching wide output dc converter according to claim 4, comprising the steps of:
s1, collecting input voltage V of direct current converteriOutput voltage Vo；
S2, collecting input voltage ViWith a given outputVoltage command value Vo *And sending the data to a controller of the direct current converter for mode judgment, and confirming the adjustment control quantity:
s21, when the given output voltage instruction value Vo *Is greater than or equal to the input voltage ViBoundary value M with HG modal gainHGBThe transformer operates in HG mode;
s22, when the given output voltage instruction value Vo *Less than the input voltage ViAnd HG modal gain MHGBAnd is greater than or equal to the input voltage ViBoundary value M with MG modal gainMGBThe converter operates in the MG mode;
s23, when the given output voltage instruction value Vo *Less than the input voltage ViBoundary value M with MG modal gainMGBThe transformer operates in the LG mode;
s3, collecting the output voltage VoSubtracting the given voltage command value Vo to obtain a voltage error, sending the voltage error to a proportional-integral controller, and then sending an output Vcon of the proportional-integral controller to the controller for duty ratio regulation to obtain a PWM wave meeting corresponding D, Ds and beta; wherein D represents a duty ratio, Ds represents a control amount introduced in the MG mode, and β represents a phase shift angle between the first arm and the second arm;
s4, sending the PWM wave to the drive circuit of the DC converter to obtain the control switch tube I (S)1) And a second switch tube (S)2) Switch tube III (S)3) And a fourth switch tube (S)4) Drive signal g of1、g2、g3、g4。
6. The method for using the multi-mode switching wide-output DC converter according to claim 5, wherein when the DC converter operates in HG mode, the phase shift β between the driving signals of the switches in the first bridge arm and the second bridge arm in the interleaved parallel network is 180 °, which is complementary to the driving signals of the switches in the bridge arms, and the output voltage is adjusted by adjusting the duty ratio D of the switching tubes on the first bridge arm and the second bridge arm.
7. The method of using a multi-mode switching wide output DC converter according to claim 6, wherein the DC converter operates in HG mode with a duty cycle D regulation interval of 0.36-0.7.
8. The method of claim 5, wherein the phase shift β between the driving signals of the switches in the first leg and the second leg of the interleaved parallel network is 180 ° and a control variable D is introduced when the DC converter operates in the MG modes，DsIs a second switch tube (S)2) Drive signal g of2And a switch tube I (S)1) The phase difference of the drive signal g 1; switch tube three (S)3) And a fourth switch tube (S)4) Is constant at 0.7 by adjusting DsThe output voltage is regulated.
9. The method of using a multi-mode switching wide output dc converter according to claim 8, wherein the dc converter operates in MG mode, DsThe regulating interval is 0-0.15.
10. The method of claim 5, wherein the DC converter operates in LG mode with no phase shift between the driving signals of the switches in the first leg and the second leg of the interleaved parallel network, and with a cavity input voltage VABIs 0, diode two (D)2) Starting to conduct by adjusting the first switch tube (S)1) Switch tube III (S)3) The duty cycle D of (a) regulates the output voltage.
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