CN110212802B - High-voltage and wide-voltage input range feedback type direct current electronic load circuit - Google Patents
High-voltage and wide-voltage input range feedback type direct current electronic load circuit Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J3/00—Circuit arrangements for ac mains or ac distribution networks
- H02J3/01—Arrangements for reducing harmonics or ripples
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J3/00—Circuit arrangements for ac mains or ac distribution networks
- H02J3/38—Arrangements for parallely feeding a single network by two or more generators, converters or transformers
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
- Y02E40/00—Technologies for an efficient electrical power generation, transmission or distribution
- Y02E40/40—Arrangements for reducing harmonics
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Abstract
The invention discloses a high-voltage and wide-voltage input range feedback type direct current electronic load circuit, which comprises an isolation type DC/DC converter, a DC/AC converter and a control unit, wherein the isolation type DC/DC converter is connected with a power supply; the direct current tested equipment with wide voltage input range realizes grid connection feedback energy through an isolated DC/DC converter and a DC/AC converter; the isolated DC/DC converter adopts a two-stage structure and comprises a two-phase interleaved BOOST converter and an LLC-DCX converter; the DC/AC converter adopts a T-type inverter; the control unit comprises a sampling circuit and a DSP digital control platform. The invention is suitable for discharge tests of various battery combinations, tests of virtual loads of natural energy sources (solar battery arrays and wind power generation) and the like, has the advantages of wide input voltage range, high maximum input voltage, high frequency isolation, high efficiency, energy conservation, environmental protection and the like, and has the advantages which are not possessed by the existing circuit.
Description
Technical Field
The invention belongs to the technical field of power electronic converters, and particularly relates to a high-voltage and wide-voltage input range feedback type direct current electronic load circuit.
Background
The energy crisis is more and more serious in the current society, and the energy crisis can be effectively relieved by recycling the energy. With the rapid development of the fields of national defense, aviation, communication, traffic and the like, energy storage equipment such as batteries are also widely developed, and the discharge test and the aging test of storage batteries are indispensable links. The traditional test adopts an energy consumption type load, so that electric energy is wasted, and a large amount of heat and noise are generated. The feedback type direct current electronic load can recycle the electric energy absorbed by the electronic load to the maximum extent, greatly reduces the cost, conforms to the national policy of energy conservation and environmental protection in the current society, and has wide application prospect. The feedback type direct current electronic load mainly comprises a DC/DC converter and a grid-connected and inverted DC/AC converter. At present, the research of feedback type direct current electronic loads is mainly three, the first type is formed by cascading a BOOST converter and a grid-connected inversion DC/AC converter, but the scheme has no high-frequency transformer isolation, and the inherent defect of a power frequency transformer cannot be avoided by connecting a power frequency transformer behind the DC/AC converter to realize isolation. The second one is composed of a phase-shifted full-bridge converter and a grid-connected inverter cascade, and the scheme can realize high-frequency isolation but is not suitable for a wide voltage input range. The third one is composed of three-level cascade of a BOOST converter, a phase-shifted full-bridge converter and a grid-connected inverter, the scheme can solve the problem of wide input voltage range and has a high-frequency isolation function, but the phase-shifted full-bridge soft switch cannot be realized in the full range, the control is relatively complex, and the complexity of the whole machine is improved.
Disclosure of Invention
In order to solve the defects and shortcomings in the prior art, the invention provides a feedback type direct current electronic load circuit with high voltage and wide voltage input range, namely a three-level cascade topology of a two-phase interleaved parallel BOOST converter, an LLC-DCX converter and a T-type inverter, wherein the first-level two-phase interleaved parallel BOOST converter is used as a load simulation unit, can simulate various load characteristics, and can promote the wide-range input voltage to the bus voltage required by the grid connection of the inverter, so that the problem of wide input voltage range is solved; the LLC-DCX converter always works at a resonance point in a fixed frequency mode, ZVS of a switching tube and ZCS of a secondary side rectifier diode can be realized in a full-load range, the high efficiency of the converter is realized, and meanwhile, the high-frequency isolation function is realized; the T-type inverter can realize high-voltage input inversion grid connection, and the three-level form can reduce harmonic content and effectively improve grid connection waveform quality.
In order to achieve the purpose, the invention adopts the following technical scheme:
a high-voltage and wide-voltage input range feedback type direct current electronic load circuit comprises an isolation type DC/DC converter, a DC/AC converter and a control unit; the direct current tested equipment with wide voltage input range realizes grid connection feedback energy through an isolated DC/DC converter and a DC/AC converter; the isolated DC/DC converter adopts a two-stage structure and comprises a two-phase interleaved BOOST converter and an LLC-DCX converter; the DC/AC converter adopts a T-type inverter; the control unit comprises a sampling circuit and a DSP digital control platform.
The input voltage range of the feedback type direct current electronic load is wide and is more than or equal to 150VinLess than or equal to 750V, through analysis, two-stage conversion is adopted, high-frequency isolation is adopted at the primary stage, and proper topology is difficult to find during low-voltage input, so that three-stage conversion is considered, BOOST is adopted at the primary stage, and V is boostedbus1The voltage is boosted to the voltage requirement that the DC/AC can be connected to the grid, but the three-level conversion efficiency is influenced, so that the soft switching and three-level technology are required to be considered in the later stage; the primary BOOST converter is used as a load simulation unit, controls input current to realize constant current, constant power and constant resistance functions, and controls input voltage to realize a constant voltage function; the two latter stages are respectively a high-frequency isolated DC/DC converter and a grid-connected inversion DC/AC converter, the DC/DC converter with the high-frequency isolation adopts a full-bridge LLC topology, soft switching in a full-load range can be realized, and the efficiency of the whole machine is improved; the DC/AC converter adopts a T-shaped three-level inversion topology, reduces the stress of devices, is suitable for high-voltage work and has high conversion efficiency. The DC/AC converter is not limited to the T-type inverter, but can be other inverters according to the bus voltage Cbus2Other inverters may be selected as appropriate. Bus voltage C in the inventionbus2The inverter is high, belongs to a high-voltage occasion, and has more obvious advantages when a T-type inverter is selected.
Further, the first stage of the two-stage isolated DC/DC converter comprises a first switch tube Q1A second switch tube Q2A first diode D1A second diode D2A third diode D3、A first inductor L1, a second inductor L2, a first switchClosing tube Q1A second diode D2And a first inductor L1And a second switching tube Q2A third diode D3And a second inductor L2Forming a first-stage two-phase interleaved BOOST converter, wherein the two-phase interleaved BOOST converter drives the control signal to stagger 180 degrees in phase, the input end of the two-phase interleaved BOOST converter is connected with a direct current tested device with a wide voltage input range in parallel, and the output end of the two-phase interleaved BOOST converter is connected with a bus capacitor C in parallelbus1And then connected to a second stage LLC-DCX converter, a first diode D1The anode of the two-phase interleaved BOOST converter is connected with the positive input end, the cathode of the two-phase interleaved BOOST converter is connected with the positive output end of the two-phase interleaved BOOST converter to form a pre-charging branch circuit for a bus capacitor Cbus1Pre-charging; the second-stage LLC-DCX converter comprises a third switching tube Q3And a fourth switching tube Q4The fifth switch tube Q5And a sixth switching tube Q6A fourth diode D4A fifth diode D5A sixth diode D6The seventh diode D7Resonant inductor LrResonant capacitor CrTransformer exciting inductance LmAnd a high-frequency isolation transformer, a third switching tube Q3、Fourth switch tube Q4The fifth switch tube Q5And a sixth switching tube Q6Form a primary full-bridge conversion circuit, a resonant inductor LrResonant capacitor CrAnd transformer excitation inductance LmForming a resonant circuit, a third switching tube Q3And a fifth switching tube Q5Node of (L) series resonance inductorrAnd then with the transformer excitation inductance LmIs connected with one end of the primary side of the high-frequency isolation transformer, and a fourth switching tube Q4And a sixth switching tube Q6Node series resonance capacitor CrAnd then with the transformer excitation inductance LmIs connected with the other end of the primary side of the high-frequency isolation transformer, and a fourth diode D4A fifth diode D5A sixth diode D6And a seventh diode D7Forming a secondary side full-bridge rectifier circuit, a fourth diode D4And a sixth diode D6A node connected with one end of the secondary side of the high-frequency isolation transformer, and a fifth diode D5And a seventh diode D7Node and high frequencyThe other end of the secondary side of the isolation transformer is connected; the first output end and the second output end of the two-stage isolated DC/DC converter are respectively connected with a bus capacitor Cbus2Positive and negative electrodes of (2), bus capacitor Cbus2Respectively connected to the first and second terminals of the DC/AC converter.
Further, a switch tube Q1-Q6Are SiC MOS tubes, diode D1-D7Are all SiC diodes.
Further, the T-type inverter comprises a first switch tube S1A second switch tube S2A third switch tube S3And a fourth switching tube S4A first voltage-dividing capacitor C1A second voltage dividing capacitor C2A third filter inductor L3And a fourth filter inductor L4And a filter capacitor CfA first switch tube S1And a second switching tube S2Connected in series to form a half-bridge structure, a third switching tube S3And a fourth switching tube S4Reverse series connection, one end of which is connected to the first switch tube S1And a second switching tube S2Another end of the node is connected to a first voltage-dividing capacitor C1And a second voltage dividing capacitor C2Is connected in parallel to the network ground, a third filter inductance L3And a fourth filter inductor L4And a filter capacitor CfForming an LCL filter, a third filter inductor L3And a fourth filter inductor L4In series, with nodes passing through filter capacitors CfTo the network ground, a fourth filter inductor L4And the other end of the second switch is connected to the power grid.
Further, a switch tube S1-S4Are all IGBT.
Further, the control unit includes a DC/DC control section and a T-type inverter control section;
the control method of the DC/DC control part comprises the following steps:
(1) the two-phase interleaved BOOST converter is used as a load simulation unit, and the control objects are different according to different electronic load working modes; in the constant current mode, the current I is inputinInput into DSP (TMS32028377) via sampling circuit, and input current reference Iin_refAfter the error signal is calculated by a proportional-integral-derivative (PID) controller in the DSP, the error signal is compared with a triangular carrier to obtain a Pulse Width Modulation (PWM) signal and the PWM signal is input into an isolation driving circuit to respectively control a first switching tube Q in a two-phase interleaved BOOST converter1And a second switching tube Q2Control the input current IinIs equal to the input current reference Iin_ref(ii) a The LLC-DCX converter adopts a fixed frequency uncontrolled method, and the output voltage directly follows the bus voltage Vbus1；
(2) Under the working state of constant power and constant resistance modes, the constant power value and the constant resistance value are respectively converted into corresponding constant current values through the following formulas (1) and (2), so that the control block diagrams of the constant power and the constant resistance can be converted into constant current control block diagrams, and the corresponding control method is the same as the constant current control method;
wherein, PsetAt a constant power setting, RsetIs a constant resistance set value;
(3) in the constant voltage mode, the input voltage VinInput into DSP (TMS32028377) via sampling circuit, and input voltage reference Vin_refAfter the error signal is calculated by a proportional-integral-derivative controller (PID) in the DSP, the error signal is compared with a triangular carrier to obtain a Pulse Width Modulation (PWM) signal, the PWM signal is input into a two-phase interleaved BOOST converter, and the two-phase interleaved BOOST converter respectively controls a first switch tube Q1And a second switching tube Q2Controlling the input voltage VinEqual to the input voltage reference Vin_ref(ii) a The LLC-DCX converter works in a DCX state, and the output voltage directly follows the bus voltage Vbus1；
(4) The transformation ratio of a high-frequency isolation transformer in the LLC-DCX converter is set to be 1, the switching frequency is equal to the resonant frequency, and the gain is 1; excitation of magnetic fieldInductor LmThe energy required for realizing the LLC primary full-bridge switching tube ZVS is designed according to the following formula (3):
wherein, TsIs LLC switching period, tdeadAs dead time, CossIs a LLC primary side switch tube junction capacitor;
the control method of the T-type inverter part adopts a double-loop control method of a bus voltage outer loop and a grid-connected current inner loop, and specifically comprises the following steps:
(1) sampling bus voltage Vbus2The signal is sent to a DSP and filtered by a secondary power frequency trap to be compared with a bus voltage reference value Vbus2_refMaking a difference, and obtaining a given A of the current inner loop by an error signal through a PI controller;
(2) sampling grid current igAnd the network voltage vacSending the signals into a DSP, calculating the grid voltage sampling signals through a phase-locked loop in the DSP to obtain grid voltage phase information sin (omega)0t) to obtain a current reference signal a sin (ω)0t), where A is the output of the voltage outer loop, the grid current igAnd A sin (omega)0T) comparing, calculating error signals by a PI controller in the DSP, comparing with a triangular carrier to obtain PWM signals, obtaining driving signals by the PWM signals through an optical coupling isolation driving circuit, and controlling a first switching tube S in the T-type inverter1A second switch tube S2A third switch tube S3And a fourth switching tube S4The unit power factor is connected in parallel by switching on and off.
Furthermore, the whole circuit is a system module which supports expansion, a plurality of module inputs are connected in parallel, the maximum power input can be improved, and a plurality of module inputs are connected in series, so that the maximum input voltage can be improved. Expanding system modules, namely adding corresponding voltage-sharing and current-sharing control according to different module connection modes;
when the module inputs are connected in parallel, the direct current input ends are connected in parallel, the alternating current output ends are respectively connected to the A/B/C phases of a three-phase power grid, the maximum input current of the whole machine is the sum of the maximum input currents of the three power modules in a parallel mode, the maximum input voltage is the same as that of a single module, and the direct current input side of the module adopts current sharing control;
when the module inputs are connected in series, the direct current input ends are connected in series, the alternating current output ends are respectively connected to the A/B/C phases of a three-phase power grid, the maximum input current of the whole machine is the same as the maximum input current of a single power module in the series connection mode, the maximum input voltage is equal to the sum of the input voltages of the three power modules, and the direct current input side of the module adopts voltage-sharing control.
Has the advantages that:
1. the invention has wide input voltage range and high maximum input voltage, can meet the discharge requirements of most battery packs and energy storage equipment, tests of virtual loads of natural energy (solar cell arrays and wind power generation), tests of aging life of AC/DC and DC/DC converters and the like, feeds energy back to a power grid, saves electricity consumption and heat dissipation cost, supports module expansion, improves maximum power input by connecting a plurality of modules in parallel or connecting a plurality of modules in series, improves maximum input voltage, and has the advantages of high efficiency, high reliability, strong compatibility and the like.
2. The LLC-DCX converter works in a DCX state, the gain is always 1, the control is simple, the efficiency is high, high-frequency isolation is realized, and the safety of client equipment is effectively protected.
3. The LLC-DCX converter can enable the primary side switch tube to be switched on at zero voltage and the secondary side diode to be switched off at zero current in a full-load and wide input voltage range, greatly reduces the switching loss, improves the efficiency and reduces the electromagnetic interference.
4. The BOOST converter adopts a staggered parallel technology, and reduces capacitance volume and ripple current.
5. The T-type inverter is suitable for high-voltage input, the leakage current is small, and the grid-connected harmonic wave of the three-level structure is small.
Drawings
FIG. 1 is a circuit schematic of the present invention;
FIG. 2 is a waveform diagram of the LLC converter operation of the invention;
FIG. 3 is a constant current control block diagram of the present invention;
FIG. 4 is a constant voltage control block diagram of the present invention;
FIG. 5 is a startup flow diagram of the present invention;
FIG. 6 is an input parallel module expansion diagram of the present invention;
FIG. 7 is an input tandem module expansion of the present invention;
FIG. 8 is a diagram of an input voltage sharing and current sharing control scheme of the present invention;
in the figure: 1-two-phase interleaved BOOST converters in parallel; 2-LLC-DCX converter; a 3-T-type inverter;
the symbols of the components in the drawings illustrate that:
Vininput voltage LrResonance inductor
D1-D7Diode CrResonance capacitor
L1First inductance LmExciting inductance
L2Second inductor C1-C2 voltage dividing capacitor
Q1-Q6 MOSFET S1-S4 IGBT
Cbus1Bus capacitor L3Third filter inductor
Cbus2Bus capacitor L4Fourth filter inductor
Vbus1Bus voltage CfFilter capacitor
Vbus2Grid voltage of bus voltage Grid
Detailed Description
The invention is further illustrated with reference to the following figures and examples.
As shown in fig. 1, the present invention provides a high-voltage wide-voltage input range feedback type DC electronic load circuit, which includes an isolated DC/DC converter, a DC/AC converter and a control unit; the direct current tested equipment with wide voltage input range realizes grid connection feedback energy through an isolated DC/DC converter and a DC/AC converter; the isolated DC/DC converter adopts a two-stage structure and comprises a two-phase interleaved BOOST converter 1 and an LLC-DCX converter 2, the DC/AC converter adopts a T-type inverter 3, and the control unit comprises a sampling circuit and DSP digital control.
The first stage of the two-stage isolated DC/DC converter comprises a first switching tube Q1A second switch tube Q2A first diode D1A second diode D2A third diode D3、A first inductor L1, a second inductor L2, and a first switch tube Q1A second diode D2And a first inductor L1And a second switching tube Q2A third diode D3And a second inductor L2Forming a first-stage two-phase interleaved BOOST converter 1, wherein the two-phase interleaved BOOST converter 1 drives the control signal to stagger the phase by 180 degrees, the input end of the two-phase interleaved BOOST converter is connected with the direct current tested equipment with wide voltage input range in parallel, and the output end of the two-phase interleaved BOOST converter is connected with a bus capacitor C in parallelbus1And is connected to a second stage LLC-DCX converter 2, a first diode D1The anode of the two-phase interleaved BOOST converter is connected with the positive input end, the cathode of the two-phase interleaved BOOST converter is connected with the positive output end of the two-phase interleaved BOOST converter 1 to form a pre-charging branch circuit for a bus capacitor Cbus1Pre-charging; the second-stage LLC-DCX converter 2 comprises a third switching tube Q3And a fourth switching tube Q4The fifth switch tube Q5And a sixth switching tube Q6A fourth diode D4A fifth diode D5A sixth diode D6The seventh diode D7Resonant inductor LrResonant capacitor CrTransformer exciting inductance LmAnd a high-frequency isolation transformer, a third switching tube Q3、Fourth switch tube Q4The fifth switch tube Q5And a sixth switching tube Q6Form a primary full-bridge conversion circuit, a resonant inductor LrResonant capacitor CrAnd transformer excitation inductance LmForming a resonant circuit, a third switching tube Q3And a fifth switching tube Q5Node of (L) series resonance inductorrAnd then with the transformer excitation inductance LmAnd high frequencyOne end of the primary side of the isolation transformer is connected with a fourth switching tube Q4And a sixth switching tube Q6Node series resonance capacitor CrAnd then with the transformer excitation inductance LmIs connected with the other end of the primary side of the high-frequency isolation transformer, and a fourth diode D4A fifth diode D5A sixth diode D6And a seventh diode D7Forming a secondary side full-bridge rectifier circuit, a fourth diode D4And a sixth diode D6A node connected with one end of the secondary side of the high-frequency isolation transformer, and a fifth diode D5And a seventh diode D7The node of the transformer is connected with the other end of the secondary side of the high-frequency isolation transformer; the first output end and the second output end of the two-stage isolated DC/DC converter are respectively connected with a bus capacitor Cbus2Positive and negative electrodes of (2), bus capacitor Cbus2Respectively connected to the first and second terminals of the DC/AC converter. Wherein the switching tube Q1-Q6Are SiC MOS tubes, diode D1-D7Are all SiC diodes.
The T-type inverter 3 comprises a first switching tube S1A second switch tube S2A third switch tube S3And a fourth switching tube S4A first voltage-dividing capacitor C1A second voltage dividing capacitor C2A third filter inductor L3And a fourth filter inductor L4And a filter capacitor CfA first switch tube S1And a second switching tube S2Connected in series to form a half-bridge structure, a third switching tube S3And a fourth switching tube S4Reverse series connection, one end of which is connected to the first switch tube S1And a second switching tube S2Another end of the node is connected to a first voltage-dividing capacitor C1And a second voltage dividing capacitor C2Is connected in parallel to the network ground, a third filter inductance L3And a fourth filter inductor L4And a filter capacitor CfForming an LCL filter, a third filter inductor L3And a fourth filter inductor L4In series, with nodes passing through filter capacitors CfTo the network ground, a fourth filter inductor L4And the other end of the second switch is connected to the power grid. Wherein the switch tube S1-S4Are all IGBT.
The DC/AC inverter is not limited to the T-type inverter 3, but may be other inverters depending on the bus voltage Cbus2Other inverters may be selected as appropriate. Bus voltage C of the inventionbus2The inverter is high, belongs to a high-voltage occasion, and has more obvious advantages when the T-type inverter 3 is selected.
The transformation ratio of a high-frequency isolation transformer in the LLC-DCX converter 2 is designed to be 1, the switching frequency is equal to the resonant frequency, and the gain is 1. Excitation inductance LmThe energy required for realizing the LLC primary full-bridge switching tube ZVS is designed according to the following formula (3):
wherein, TsIs LLC switching period, tdeadAs dead time, CossIs a primary side switch tube junction capacitor.
Because the LLC-DCX converter 2 operates in an open-loop fixed-frequency state, and the switching frequency is approximately equal to the resonant frequency in actual operation. To reduce the problem of high LLC output voltage gain under light load, Lm/LrShould be large enough to make the gain curve sufficiently flat near the resonance point so that the LLC does not suffer from the high output voltage swing during constant frequency light load operation. Actual Lm/LrWith a value of 16/1, the gain curve is sufficiently flat near the resonance point.
Specific parameters of the high-voltage and wide-voltage input range feedback type direct current electronic load circuit are shown in the following table 1.
TABLE 1 Circuit parameters
As shown in fig. 2, a switching tube Q5Drain-source voltage V ofds_Q5、Vgs_Q5And a drive voltage signal, a resonant current iLrExcitation current iLmAnd through the secondary side rectifier diode D4Current i ofD4Waveform of (2)Figure (a). According to the graph, the LLC fixed-frequency open loop works near the resonance point to realize ZVS (zero voltage switching) switching-on and secondary ZCS (zero current switching) switching-off of the LLC converter, and the switching-on and switching-off losses of a switching tube are greatly reduced.
The control method of the feedback type direct current electronic load circuit with high voltage and wide voltage input range provided by the invention mainly comprises two parts: the control method of the DC/DC part and the control method of the DC/AC part (T-type inverter 3) are decoupled, and the two parts are mutually independent.
The DC/DC part control method is as follows:
fig. 3 shows a control block diagram of the DC/DC section in the constant current mode control, and the constant current control method includes the following steps:
the two-phase interleaved BOOST converter 1 is used as a load simulation unit, and the control objects of the two-phase interleaved BOOST converter are different according to different electronic load working modes.
Under the working state of the constant current mode, the two-phase interleaved BOOST converter 1 inputs current IinInput into DSP (TMS32028377) via sampling circuit, and input current reference Iin_refAfter the error signal is calculated by a proportional-integral-derivative (PID) controller in the DSP, the error signal is compared with a triangular carrier to obtain a Pulse Width Modulation (PWM) signal and the PWM signal is input into an isolation driving circuit to respectively control a first switching tube Q of the two-phase interleaved BOOST converter 11And a second switching tube Q2Control the input current IinIs equal to the input current reference Iin_ref. The LLC-DCX converter 2 works in a DCX state, and the output voltage directly follows the bus voltage Vbus1。
Under the constant power and constant resistance working modes, the constant power and constant resistance working modes can be converted into corresponding constant current values through the following formulas (1) and (2), so that the control block diagrams of the constant power and the constant resistance can be converted into constant current control block diagrams, and the corresponding control method is the same as that of the constant current control method.
Wherein, PsetAt a constant power setting, RsetIs a constant resistance set value.
Fig. 4 is a control block diagram of a DC/DC section in the constant voltage mode control, the constant voltage control method including the steps of:
the two-phase interleaved BOOST converter 1 is used as a load simulation unit, and the control objects of the two-phase interleaved BOOST converter are different according to different electronic load working modes.
Under the working state of the constant voltage mode, the input voltage V of the two-phase interleaved BOOST converter 1inInput into DSP (TMS32028377) via sampling circuit, and input voltage reference Vin_refAfter the error signal is calculated by a proportional-integral-derivative (PID) controller in the DSP, the error signal is compared with a triangular carrier to obtain a Pulse Width Modulation (PWM) signal and the PWM signal is input into an isolation driving circuit to respectively control a first switching tube Q of the two-phase interleaved BOOST converter 11And a second switching tube Q2Controlling the input voltage VinEqual to the input voltage reference Vin_ref. The LLC-DCX converter 2 works in a DCX state, and the output voltage directly follows the bus voltage Vbus1。
The DC/AC section (T-type inverter 3) control method is as follows:
fig. 3 and 4 each show a control block diagram of the T-type inverter 3, and the control method of the T-type inverter 3 includes the following steps:
the T-type inverter 3 adopts a double-loop control strategy of a bus voltage outer loop and a grid-connected current inner loop.
Firstly, a bus voltage signal is sampled and sent to a DSP, after being filtered by a secondary power frequency trap, the bus voltage signal is differed from a bus voltage reference value, and an error signal is subjected to a given A of a current inner loop through a PI controller.
Second, the grid current i is sampledgAnd the network voltage vacSending the signals into a DSP, calculating the grid voltage sampling signals through a phase-locked loop in the DSP to obtain grid voltage phase information sin (omega)0t). Thereby obtaining a current reference signal A sin (omega)0t) (a is the output of the voltage outer loop). Electric networkStream igAnd A sin (omega)0t) comparing, and comparing the error signals with the triangular carrier after the error signals are calculated by the PI controller in the DSP to obtain PWM signals. The PWM signal is subjected to optical coupling isolation driving circuit to obtain a driving signal to control a first switch tube S of the T-type inverter 31A second switch tube S2A third switch tube S3And a fourth switching tube S4The unit power factor is connected in parallel by switching on and off.
3. Fig. 5 shows a constant current startup flow chart of the whole high-voltage and wide-voltage input range feedback type dc electronic load circuit according to the present invention.
The DC/AC converter firstly supplies C in the reverse direction through the power gridbus2Precharge, when Vbus2After the voltage of 780V is built up, the DC/DC converter starts soft start. At constant current soft start, Iin_refSlowly increasing to a given value, and simultaneously, the LLC phase-shifting is soft, in the process Cbus1The voltage slowly increases when Vbus1After the voltage is increased to 780V, the DC/AC converter is automatically switched to a forward running state, energy is fed back by grid connection, then the converter enters a steady-state working state, and control is switched from starting control to steady-state control.
The high-voltage and wide-voltage input range feedback type direct current electronic load circuit integrally forms a system module. The module supports expansion, and the input of a plurality of modules is connected in parallel, so that the maximum power input can be improved; the input of a plurality of modules is connected in series, so that the maximum input voltage can be improved. According to different module connection modes, corresponding voltage-sharing and current-sharing control needs to be added.
As shown in fig. 6, when the module inputs are connected in parallel, the dc input terminals are connected in parallel, the ac output terminals are respectively connected to the a/B/C phases of the three-phase power grid, the maximum input current of the whole power module is the sum of the maximum input currents of the three power modules in the parallel connection mode, the maximum input voltage is the same as that of a single module, and the dc input side of the module adopts current sharing control.
As shown in fig. 7, when the module inputs are connected in series, the dc input terminals are connected in series, the ac output terminals are respectively connected to the a/B/C phases of the three-phase power grid, the maximum input current of the whole power module is the same as the maximum input current of 3 single power modules in the series connection, the maximum input voltage is equal to the sum of the input voltages of three power modules, for example, the series input voltages of two modules can reach 1500V, and the input side of the module adopts voltage-sharing control.
Fig. 8 shows a current-sharing and voltage-sharing control diagram between power modules, and a CAN communication bus is currently used for current-sharing or voltage-sharing control. The current-equalizing and voltage-equalizing operation among the power modules is placed in the DSP, the transmission of various voltage and current information is realized through CAN communication among the modules, and each module polls and sends respective current and voltage values on a bus to achieve the purpose of current equalizing and voltage equalizing.
In summary, the high-voltage and wide-voltage input range feedback type dc electronic load circuit provided by the invention is suitable for discharge tests of various battery combinations, tests of virtual loads of natural energy (solar battery arrays, wind power generation) and the like, has the advantages of wide input voltage range, high maximum input voltage, high frequency isolation, high efficiency, energy conservation, environmental protection and the like, and has the advantages that the existing circuit does not have.
For example, the two-phase interleaved parallel BOOST converter in the embodiment may also be a single BOOST converter or a multiphase interleaved parallel BOOST converter, the inputs of a plurality of modules are connected in parallel to increase the maximum power input, or the inputs of a plurality of modules are connected in series to increase the maximum input voltage, which are within the protection scope of the present invention.
Claims (6)
1. A high-voltage and wide-voltage input range feedback type direct current electronic load circuit is characterized in that: the device comprises an isolated DC/DC converter, a DC/AC converter and a control unit; the direct current tested equipment with wide voltage input range realizes grid connection feedback energy through an isolated DC/DC converter and a DC/AC converter; the isolated DC/DC converter adopts a two-stage structure and comprises a two-phase interleaved BOOST converter (1) and an LLC-DCX converter (2); the DC/AC converter adopts a T-type inverter (3); the control unit comprises a sampling circuit and a DSP digital control platform;
the control unit includes a DC/DC control part and a T-type inverter control part;
the control method of the DC/DC control part comprises the following steps:
(1) the two-phase interleaved BOOST converter (1) is used as a load simulation unit and inputs current I in a constant current mode working stateinInput into DSP via sampling circuit, and input current reference Iin_refComparing, after the error signal is calculated by a PID controller in the DSP, comparing with a triangular carrier to obtain a PWM signal, inputting the PWM signal into an isolation driving circuit, and respectively controlling a first switching tube Q in the two-phase interleaved BOOST converter (1)1And a second switching tube Q2Control the input current IinIs equal to the input current reference Iin_ref(ii) a The LLC-DCX converter (2) adopts a fixed frequency uncontrolled method, and the output voltage directly follows the bus voltage Vbus1；
(2) Under the working state of constant power and constant resistance modes, the constant power value and the constant resistance value are respectively converted into corresponding constant current values through the following formulas (1) and (2), and then the corresponding control is the same as the constant current control method;
wherein, PsetAt a constant power setting, RsetIs a constant resistance set value;
(3) in the constant voltage mode, the input voltage VinInput into DSP via sampling circuit, and output with reference voltage Vin_refComparing, after error signal is calculated by PID controller in DSP, comparing with triangular carrier to obtain PWM signal, inputting into two-phase interleaving parallel BOOST converter (1), respectively controlling first switch tube Q1And a second switching tube Q2Control input power by controlling the duty cycle ofPressure VinEqual to the input voltage reference Vin_ref(ii) a The LLC-DCX converter (2) works in a DCX state, and the output voltage directly follows the bus voltage Vbus1；
(4) The transformation ratio of a high-frequency isolation transformer in the LLC-DCX converter (2) is set to be 1, the switching frequency is equal to the resonance frequency, and the gain is 1; excitation inductance LmThe energy required for realizing the LLC primary full-bridge switching tube ZVS is designed according to the following formula (3):
wherein, TsIs LLC switching period, tdeadAs dead time, CossIs a LLC primary side switch tube junction capacitor;
the control method of the T-type inverter part adopts a double-loop control method of a bus voltage outer loop and a grid-connected current inner loop, and specifically comprises the following steps:
(1) sampling bus voltage Vbus2The signal is sent to a DSP and filtered by a secondary power frequency trap to be compared with a bus voltage reference value Vbus2_refMaking a difference, and obtaining a given A of the current inner loop by an error signal through a PI controller;
(2) sampling grid current igAnd the network voltage vacSending the signals into a DSP, calculating the grid voltage sampling signals through a phase-locked loop in the DSP to obtain grid voltage phase information sin (omega)0t) to obtain a current reference signal a sin (ω)0t), where A is the output of the voltage outer loop, the grid current igAnd A sin (omega)0T) comparing, calculating error signals by a PI controller in the DSP, comparing with a triangular carrier to obtain PWM signals, obtaining driving signals by the PWM signals through an optical coupling isolation driving circuit, and controlling a first switching tube S in the T-type inverter (3)1A second switch tube S2A third switch tube S3And a fourth switching tube S4The unit power factor is connected in parallel by switching on and off.
2. The high voltage, wide voltage input range feedback of claim 1Direct current electronic load circuit, its characterized in that: the first stage of the two-stage isolated DC/DC converter comprises a first switching tube Q1A second switch tube Q2A first diode D1A second diode D2A third diode D3、A first inductor L1, a second inductor L2, and a first switch tube Q1A second diode D2And a first inductor L1And a second switching tube Q2A third diode D3And a second inductor L2A first-stage two-phase interleaved BOOST converter (1) is formed, the two-phase interleaved BOOST converter (1) drives the control signal to stagger 180 degrees in phase, the input end of the two-phase interleaved BOOST converter is connected with a direct current tested device with a wide voltage input range in parallel, and the output end of the two-phase interleaved BOOST converter is connected with a bus capacitor C in parallelbus1And is connected to a second stage LLC-DCX converter (2), a first diode D1The anode of the two-phase interleaved BOOST converter is connected with the positive input end, the cathode of the two-phase interleaved BOOST converter is connected with the positive output end of the two-phase interleaved BOOST converter (1), and a pre-charging branch circuit for a bus capacitor C is formedbus1Pre-charging; the second-stage LLC-DCX converter (2) comprises a third switching tube Q3And a fourth switching tube Q4The fifth switch tube Q5And a sixth switching tube Q6A fourth diode D4A fifth diode D5A sixth diode D6The seventh diode D7Resonant inductor LrResonant capacitor CrTransformer exciting inductance LmAnd a high-frequency isolation transformer, a third switching tube Q3、Fourth switch tube Q4The fifth switch tube Q5And a sixth switching tube Q6Form a primary full-bridge conversion circuit, a resonant inductor LrResonant capacitor CrAnd transformer excitation inductance LmForming a resonant circuit, a third switching tube Q3And a fifth switching tube Q5Node of (L) series resonance inductorrAnd then with the transformer excitation inductance LmIs connected with one end of the primary side of the high-frequency isolation transformer, and a fourth switching tube Q4And a sixth switching tube Q6Node series resonance capacitor CrAnd then with the transformer excitation inductance LmIs connected with the other end of the primary side of the high-frequency isolation transformer, and a fourth diode D4A fifth diode D5A sixth diode D6And a seventh diode D7Forming a secondary side full-bridge rectifier circuit, a fourth diode D4And a sixth diode D6A node connected with one end of the secondary side of the high-frequency isolation transformer, and a fifth diode D5And a seventh diode D7The node of the transformer is connected with the other end of the secondary side of the high-frequency isolation transformer; the first output end and the second output end of the two-stage isolated DC/DC converter are respectively connected with a bus capacitor Cbus2Positive and negative electrodes of (2), bus capacitor Cbus2Respectively connected to the first and second terminals of the DC/AC converter.
3. The high voltage, wide voltage input range feedback dc electronic load circuit of claim 2, wherein: the switch tube Q1-Q6Are both MOSFETs.
4. The high voltage, wide voltage input range, feedback type dc electronic load circuit of claim 1, wherein: the T-type inverter (3) comprises a first switching tube S1A second switch tube S2A third switch tube S3And a fourth switching tube S4A first voltage-dividing capacitor C1A second voltage dividing capacitor C2A third filter inductor L3And a fourth filter inductor L4And a filter capacitor CfA first switch tube S1And a second switching tube S2Connected in series to form a half-bridge structure, a third switching tube S3And a fourth switching tube S4Reverse series connection, one end of which is connected to the first switch tube S1And a second switching tube S2Another end of the node is connected to a first voltage-dividing capacitor C1And a second voltage dividing capacitor C2Is connected in parallel to the network ground, a third filter inductance L3And a fourth filter inductor L4And a filter capacitor CfForming an LCL filter, a third filter inductor L3And a fourth filter inductor L4In series, with nodes passing through filter capacitors CfTo the network ground, a fourth filter inductor L4And the other end of the second switch is connected to the power grid.
5. The high-voltage, wide-voltage-input-range feedback-type dc electronic load circuit according to claim 4, wherein: the switch tube S1-S4Are all IGBT.
6. The high-voltage, wide-voltage-input-range feedback-type direct current electronic load circuit according to any one of claims 1 to 5, wherein: the whole circuit is a system module, and the module expansion comprises module input parallel connection and module input series connection;
when the module inputs are connected in parallel, the direct current input ends are connected in parallel, the alternating current output ends are respectively connected to the A/B/C phases of a three-phase power grid, the maximum input current of the whole machine is the sum of the maximum input currents of the three power modules in a parallel mode, the maximum input voltage is the same as that of a single module, and the direct current input side of the module adopts current sharing control;
when the module inputs are connected in series, the direct current input ends are connected in series, the alternating current output ends are respectively connected to the A/B/C phases of a three-phase power grid, the maximum input current of the whole machine is the same as the maximum input current of a single power module in the series connection mode, the maximum input voltage is equal to the sum of the input voltages of the three power modules, and the direct current input side of the module adopts voltage-sharing control.
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