CN114123786B - Internal phase shift control method of CLLC converter and sensorless synchronous rectification control method - Google Patents
Internal phase shift control method of CLLC converter and sensorless synchronous rectification control method Download PDFInfo
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/083—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the ignition at the zero crossing of the voltage or the current
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The application provides an internal phase shift control method of a CLLC converter and a sensorless synchronous rectification control method, which relate to the technical field of power electronic converter control and design, wherein the internal phase shift control method of the CLLC converter comprises the steps of selecting and fixing the switching frequency of the CLLC converter; the phase controller is used for determining the phase angle between the first bridge arm and the second bridge arm, namely the primary side shifting phase angle, and determining driving signals of four switching tubes of the primary side H bridge through the primary side shifting phase angle; and the driving signals of the four switching tubes of the primary side H bridge are used for controlling the on-off sequence of the four switching tubes of the primary side H bridge so as to control the output voltage of the CLLC converter. The application adopting the scheme controls the output voltage of the CLLC converter by adopting the internal phase shift control method instead of the frequency modulation control method, thereby not only meeting the requirement of wide-range output voltage, but also simplifying the parameter design process, reducing the calculated amount and improving the control stability of the CLLC converter.
Description
Technical Field
The application relates to the technical field of control and design of power electronic converters, in particular to an internal phase shift control method and a sensorless synchronous rectification control method of a CLLC converter.
Background
Along with the gradual increase of the holding quantity of the electric automobile, the importance of the interaction of the electric automobile network is highlighted, the electric automobile is used as a distributed energy storage unit to participate in the regulation of the power network, the large-scale renewable energy source absorption and the reduction of carbon emission can be supported strongly, the realization of a power-assisted double-carbon target is realized, and in the interaction application of the electric automobile network, the bidirectional isolation direct current-direct current converter is a core component; the resonant DC/DC converter is a high-efficiency and high-power-density DC/DC converter with electrical isolation characteristics, has good application prospect, and the capacitor-inductor-capacitor resonant DC/DC converter is a topology with the most application prospect; in applications such as vehicle network interaction, energy storage, electric vehicle charging and the like, the output voltage variation range is very wide, the DC/DC converter is required to have ultra-wide voltage output capability (200V-1000V), and usually the CLLC converter controls the output voltage by adopting a frequency modulation control method, however, in the case of wide-range output, the frequency modulation control method can cause an excessively wide switching frequency variation range, and challenges are brought to parameter design and control stability.
In order to reduce the conduction loss of the secondary side of the CLLC converter, synchronous rectification control needs to be performed on the switching device of the secondary side of the CLLC converter, and the conduction voltage drop when current flows through the channel of the switching device is much lower than that when current flows through the body diode of the switching device, so that the synchronous rectification control needs to realize that the current flows through the channel of the switching device as much as possible, thereby improving the efficiency; the conventional synchronous rectification control method relies on detecting the voltage or current of the switching device, and one or more sensors and corresponding signal processing circuits are needed, which increases the complexity and cost of the CLLC converter system.
Disclosure of Invention
The present application aims to solve at least one of the technical problems in the related art to some extent.
Therefore, a first objective of the present application is to provide an internal phase shift control method of a CLLC converter, so as to solve the technical problems of unfavorable parameter design and control stability caused by an excessively wide switching frequency variation range due to a frequency modulation control method of the CLLC converter in a wide voltage output occasion.
The second objective of the present application is to provide a sensorless synchronous rectification control method, so as to solve the technical problems that one or more sensors and corresponding signal processing circuits are needed in the conventional synchronous rectification control method, so that the complexity and cost of the system are increased, and the sensors have limitation of working voltage and limitation of working bandwidth, and cannot meet the application situations of high voltage and high switching frequency.
A third object of the application is to propose a computer device.
In order to achieve the above objective, an embodiment of the first aspect of the present application provides an internal phase shift control method of a CLLC converter, where the CLLC converter includes a primary side H-bridge, a resonant cavity, and a secondary side H-bridge, the primary side H-bridge includes a first bridge arm and a second bridge arm, the first bridge arm includes a first upper bridge arm switching tube and a first lower bridge arm switching tube, and the second bridge arm includes a second upper bridge arm switching tube and a second lower bridge arm switching tube; the CLLC converter further comprises a phase controller, the method comprising the steps of:
Step 110: selecting and fixing the switching frequency of the CLLC converter;
step 120: determining phase angles between the first bridge arm and the second bridge arm through a phase controller, namely primary side internal phase angles, and determining driving signals of four switching tubes of the primary side H bridge through the primary side internal phase angles;
step 130: and the driving signals of the four switching tubes of the primary side H bridge are used for controlling the on-off sequence of the four switching tubes of the primary side H bridge so as to control the output voltage of the CLLC converter.
Optionally, in an embodiment of the present application, the step 130 further includes: determining primary side current and exciting current according to the on-off sequence of the four switching tubes of the primary side H bridge, further determining secondary side current, and determining output voltage of the CLLC converter according to the secondary side current, wherein the primary side internal phase angle and the output voltage of the CLLC converter are in monotone negative correlation.
Optionally, in an embodiment of the present application, the secondary side H-bridge includes a third bridge arm and a fourth bridge arm, the third bridge arm includes a third upper bridge arm switching tube and a third lower bridge arm switching tube, and the fourth bridge arm includes a fourth upper bridge arm switching tube and a fourth lower bridge arm switching tube; the step 130 further includes:
And the resonant cavity controls zero voltage switching on of the primary side H-bridge switching tube and zero current switching off of the secondary side H-bridge switching tube according to the switching-on sequence of the four switching tubes of the primary side H-bridge.
Optionally, in one embodiment of the present application, in the step 120, dead time is added to the driving signals of the four switching tubes of the primary side H-bridge to prevent the bridge arm from being directly connected.
Optionally, in an embodiment of the present application, the resonant cavity controls zero voltage on of the primary side H-bridge switching tube and zero current off of the secondary side H-bridge according to the on-off sequence of the four switching tubes of the primary side H-bridge, including: in each period in which the CLLC converter operates, the positive half period and the negative half period of the operating state are symmetrical to each other; in the positive half cycle of operation of each CLLC converter, the following five operation phases are specifically included:
The first stage: the input voltage is positive between the first time point and the second time point, the primary side current is larger than the exciting current, so that the secondary side current is positive, at the moment, the first upper bridge arm switching tube and the second lower bridge arm switching tube are turned on, and the first lower bridge arm switching tube and the second upper bridge arm switching tube are turned off;
And a second stage: at the moment of the second time point, driving signals of the second upper bridge arm switching tube and the second lower bridge arm switching tube are changed to enable the second upper bridge arm switching tube to be turned on and the second lower bridge arm switching tube to be turned off, and an output capacitor of the second upper bridge arm switching tube is charged in dead time due to primary side current to enable zero voltage of the second upper bridge arm switching tube to be turned on;
And a third stage: the input voltage is zero between the second time point and the third time point, the primary side current, the exciting current and the secondary side current gradually decline until the moment of the third time point, the primary side current is equal to the exciting current so that the secondary side current is zero, and the third upper bridge arm switching tube and the fourth lower bridge arm switching tube are turned off at zero current;
Fourth stage: between the third time point and the fourth time point, the input voltage is zero, the primary side current is equal to the exciting current, the secondary side current is kept to be zero, and the secondary side of the resonant cavity does not participate in resonance;
fifth stage: at the fourth time point, the driving signals of the first upper bridge arm switching tube and the first lower bridge arm switching tube are changed to enable the first lower bridge arm switching tube to be turned on and the first upper bridge arm switching tube to be turned off, and the output capacitor of the first lower bridge arm switching tube is charged in dead time due to the fact that the primary side current is the primary side current, so that the first lower bridge arm switching tube is turned on at zero voltage.
Optionally, in an embodiment of the present application, in step 110, the switching frequency is a fixed frequency.
In summary, the method for controlling the internal phase shift of the CLLC converter according to the embodiment of the first aspect of the present application selects and fixes the switching frequency of the CLLC converter; the phase controller is used for determining the phase angle between the first bridge arm and the second bridge arm, namely the primary side shifting phase angle, and determining driving signals of four switching tubes of the primary side H bridge through the primary side shifting phase angle; and the driving signals of the four switching tubes of the primary side H bridge are used for controlling the on-off sequence of the four switching tubes of the primary side H bridge so as to control the output voltage of the CLLC converter. The application adopts the internal phase shift control method to replace the frequency modulation control method to control the output voltage of the CLLC converter, thereby not only meeting the requirement of wide-range output voltage, but also simplifying the parameter design process, reducing the calculated amount and improving the control stability of the CLLC converter.
To achieve the above object, a second aspect of the present application provides a sensorless synchronous rectification control method for internal phase-shifting control in the internal phase-shifting control method for CLLC converter according to the first aspect of the present application, the CLLC converter further comprising a sampling circuit and a secondary side switching tube driving circuit, the method comprising the steps of, during each cycle in which the CLLC converter operates:
step 210: acquiring sampling data by a sampling circuit, and acquiring a value of an intra-primary-side intra-phase angle by the phase control module, wherein the sampling data are output voltage and output current;
step 220: determining the duty ratio of a secondary side switching tube driving signal according to the sampled data and the value of the primary side internal shift phase angle;
Step 230: the secondary side switching tube driving circuit determines a synchronous rectification driving signal of the secondary side switching tube according to the duty ratio of the secondary side switching tube driving signal; and controlling the on-off of four switching tubes of the secondary side H bridge according to the synchronous rectification driving signal.
Optionally, in an embodiment of the present application, the determining the duty cycle of the secondary side switching tube driving signal according to the sampled data and the value of the primary side internal phase angle includes:
the current base value is determined by the output voltage and the output current, wherein the current unitary value is determined by:
Wherein, I o,unit is the current unitary value, I o is the output current, and I base is the current base value;
wherein the current base value is determined by:
Wherein u base is a voltage base value, the magnitude of the voltage base value is equal to the output voltage, and z base is an impedance base value;
wherein the impedance base value is determined by:
Wherein L r1 is a primary side inductance value, L r2 is a secondary side inductance value, C r1 is a primary side capacitance value, and C r2 is a secondary side capacitance value;
The duty cycle value of the secondary side switching tube driving signal is determined by the current base value and the primary side internal phase angle value, wherein the duty cycle value of the secondary side switching tube driving signal is determined by the following formula:
Wherein Ds is the duty ratio of the driving signal of the secondary side switching tube, phip is the primary side inward shift angle value, C is a first intermediate variable, D is a second intermediate variable, and I o,unit is the current unitary value;
wherein the first intermediate variable is determined by:
Wherein, C is a first intermediate variable, k is the ratio of excitation inductance to primary side inductance, w r is the angular frequency value corresponding to the resonant frequency, L r1 is the primary side inductance value, C r1 is the primary side capacitance value, I o,unit is the current unitary value, and alpha is an adjustable parameter determined by parameter setting;
wherein, the angular frequency value corresponding to the resonant frequency is determined by:
ωr＝2πfr
Wherein w r is an angular frequency value corresponding to the resonant frequency, f r is the resonant frequency, L r1 is a primary side inductance value, L r2 is a secondary side inductance value, C r1 is a primary side capacitance value, and C r2 is a secondary side capacitance value;
the second intermediate variable is determined by:
Wherein C is a first intermediate variable, D is a second intermediate variable, and phip is a primary side shift angle value.
Optionally, in an embodiment of the present application, the secondary side switching tube driving circuit is a PWM generating circuit, and the phase control module is a closed loop controller.
In summary, according to the sensorless synchronous rectification control method provided by the embodiment of the second aspect of the present application, sampling data is obtained through a sampling circuit, and the value of the primary side internal phase angle is obtained through the phase control module, wherein the sampling data is output voltage and output current; determining the duty ratio of a secondary side switching tube driving signal according to the sampled data and the value of the primary side internal shift phase angle; the secondary side switching tube driving circuit determines a synchronous rectification driving signal of the secondary side switching tube according to the duty ratio of the secondary side switching tube driving signal; and controlling the on-off of four switching tubes of the secondary side H bridge according to the synchronous rectification driving signal. The application can generate the synchronous rectification driving signal of the secondary side switching tube by simple calculation without adopting a sensor and a corresponding signal processing circuit, thereby realizing the low cost of the CLLC converter, adapting to the high-precision synchronous rectification control of various working voltages and switching frequency occasions and improving the power transmission efficiency.
To achieve the above object, an embodiment of a third aspect of the present application provides a computer device, including a memory, a processor, and a computer program stored in the memory and executable on the processor, where the processor executes the computer program to implement a method as in the embodiment of the first aspect or the embodiment of the second aspect of the present application.
Additional aspects and advantages of the application will be set forth in part in the description which follows and, in part, will be obvious from the description, or may be learned by practice of the application.
Drawings
The foregoing and/or additional aspects and advantages of the application will become apparent and readily appreciated from the following description of the embodiments, taken in conjunction with the accompanying drawings, in which:
Fig. 1 is a circuit topology diagram of a CLLC converter according to an embodiment of the present application;
Fig. 2 is a flowchart of a method for controlling an internal phase shift of a CLLC converter according to an embodiment of the present application;
FIG. 3 is a waveform diagram illustrating the operation of the internal phase shift control of the CLLC converter according to an embodiment of the present application;
FIG. 4 is an equivalent circuit diagram of a CLLC converter according to an embodiment of the present application during a positive half-cycle operation;
FIG. 5 is a flowchart of a sensorless synchronous rectification control method according to an embodiment of the present application;
fig. 6 is a waveform diagram of a synchronous rectification driving signal according to an embodiment of the present application.
Detailed Description
Embodiments of the present application are described in detail below, examples of which are illustrated in the accompanying drawings, wherein like or similar reference numerals refer to like or similar elements or elements having like or similar functions throughout. The embodiments described below by referring to the drawings are illustrative only and are not to be construed as limiting the application. On the contrary, the embodiments of the application include all alternatives, modifications and equivalents as may be included within the spirit and scope of the appended claims.
The circuit topology structure of the CLLC converter provided by the embodiment of the present application is shown in fig. 1, and includes: the primary side H bridge comprises a first bridge arm and a second bridge arm, wherein the first bridge arm comprises a first upper bridge arm switching tube S1 and a first lower bridge arm switching tube S2, and the second bridge arm comprises a second upper bridge arm switching tube S3 and a second lower bridge arm switching tube S4; the secondary side H bridge comprises a third bridge arm and a fourth bridge arm, the third bridge arm comprises a third upper bridge arm switch tube S5 and a third lower bridge arm switch tube S6, and the fourth bridge arm comprises a fourth upper bridge arm switch tube S7 and a fourth lower bridge arm switch tube S8; the resonant cavity is a two-port network, a primary side port is connected with a first bridge arm midpoint A and a second bridge arm midpoint B of the primary side H bridge, and a secondary side port is connected with a third bridge arm midpoint C and a fourth bridge arm midpoint D of the secondary side H bridge; the middle of the resonant cavity is a transformer, the primary side of the transformer is connected in series with a primary side inductor L r1 and a primary side capacitor C r1, and finally connected in series with a primary side port, and the secondary side of the transformer is connected in series with a secondary side inductor L r2 and a secondary side capacitor C r2, and finally connected in series with a secondary side port; the transformation ratio of the transformer is n, and the corresponding parameter relationship is n 2＝Lr1/Lr2＝Cr2/Cr1.
The following describes an internal phase shift control method and a sensorless synchronous rectification control method of a CLLC converter according to an embodiment of the present application with reference to the accompanying drawings.
Fig. 2 is a flowchart of an internal phase shift control method of a CLLC converter according to an embodiment of the present application.
As shown in fig. 2, the internal phase shift control method of the CLLC converter includes the following steps:
Step 110: selecting and fixing the switching frequency of the CLLC converter;
step 120: the phase controller is used for determining the phase angle between the first bridge arm and the second bridge arm, namely the primary side shifting phase angle, and determining driving signals of four switching tubes of the primary side H bridge through the primary side shifting phase angle;
step 130: and the driving signals of the four switching tubes of the primary side H bridge are used for controlling the on-off sequence of the four switching tubes of the primary side H bridge so as to control the output voltage of the CLLC converter.
In the embodiment of the present application, step 130 further includes: the primary side current and the exciting current are determined according to the on-off sequence of the four switching tubes of the primary side H bridge, so that the secondary side current is determined, and the output voltage of the CLLC converter is determined according to the secondary side current, wherein the primary side internal phase angle and the output voltage of the CLLC converter are in monotonic negative correlation.
Specifically, the operational waveforms of the internal phase shift control of the CLLC converter are shown in fig. 3, where i p is the primary side current, i Lm is the exciting current, u AB is the voltage between the first bridge arm midpoint a and the second bridge arm midpoint B of the primary side H bridge, V gs,S1-Vgs,S4 is the driving signal of S1-S4, respectively, where V gs,S1 is complementary to V gs,S2, V gs,S3 is complementary to V gs,S4, i s is the secondary side current, D p is the duty cycle of V gs,S1-Vgs,S4, and Φ p is the primary side internal phase shift angle;
in the embodiment of the present application, step 130 further includes: and the resonant cavity controls zero voltage switching on of the primary side H-bridge switching tube and zero current switching off of the secondary side H-bridge switching tube according to the switching-on sequence of the four switching tubes of the primary side H-bridge.
In the embodiment of the present application, in step 120, dead time is added to the driving signals of the four switching tubes of the primary side H-bridge to prevent the bridge arm from being directly connected.
In the embodiment of the application, the resonant cavity controls zero voltage on of the primary side H-bridge switching tube and zero current off of the secondary side H-bridge switching tube according to the on-off sequence of the four switching tubes of the primary side H-bridge, and the resonant cavity comprises the following components: in each period in which the CLLC converter operates, the positive half period and the negative half period of the operating state are symmetrical to each other; in the positive half cycle of operation of each CLLC converter, the following five operation phases are specifically included:
The first stage: the input voltage is positive between the first time point and the second time point, the primary side current is larger than the exciting current, so that the secondary side current is positive, at the moment, the first upper bridge arm switching tube and the second lower bridge arm switching tube are turned on, and the first lower bridge arm switching tube and the second upper bridge arm switching tube are turned off;
And a second stage: at the moment of the second time point, driving signals of the second upper bridge arm switching tube and the second lower bridge arm switching tube are changed to enable the second upper bridge arm switching tube to be turned on and the second lower bridge arm switching tube to be turned off, and an output capacitor of the second upper bridge arm switching tube is charged in dead time due to primary side current to enable zero voltage of the second upper bridge arm switching tube to be turned on;
And a third stage: the input voltage is zero between the second time point and the third time point, the primary side current, the exciting current and the secondary side current gradually decline until the moment of the third time point, the primary side current is equal to the exciting current so that the secondary side current is zero, and the third upper bridge arm switching tube and the fourth lower bridge arm switching tube are turned off at zero current;
Fourth stage: between the third time point and the fourth time point, the input voltage is zero, the primary side current is equal to the exciting current, the secondary side current is kept to be zero, and the secondary side of the resonant cavity does not participate in resonance;
fifth stage: at the fourth time point, the driving signals of the first upper bridge arm switching tube and the first lower bridge arm switching tube are changed to enable the first lower bridge arm switching tube to be turned on and the first upper bridge arm switching tube to be turned off, and the output capacitor of the first lower bridge arm switching tube is charged in dead time due to the fact that the primary side current is the primary side current, so that the first lower bridge arm switching tube is turned on at zero voltage.
Specifically, as shown in fig. 4, an equivalent circuit of the CLLC converter during the positive half-cycle operation corresponds to a first phase in fig. 4 (a), a second phase and a third phase in fig. 4 (b), and a fourth phase in fig. 4 (c);
Specifically, since the positive half cycle and the negative half cycle of the operation state are symmetrical to each other in the period in which each CLLC converter operates, it is similarly possible that S1 and S4 can realize zero-voltage on and S6 and S7 can realize zero-current off in the negative half cycle in which each CLLC converter operates. Therefore, for the internal phase shift control of the CLLC converter, the CLLC converter can realize zero voltage on of the primary side H-bridge switching tube and zero current off of the secondary side H-bridge switching tube, thereby ensuring excellent soft switching characteristics and high-efficiency power transmission.
In the embodiment of the present application, in step 110, the switching frequency is a fixed frequency, including but not limited to a resonant frequency.
In summary, the scheme provided by the embodiment of the application selects and fixes the switching frequency of the CLLC converter; the phase controller is used for determining the phase angle between the first bridge arm and the second bridge arm, namely the primary side shifting phase angle, and determining driving signals of four switching tubes of the primary side H bridge through the primary side shifting phase angle; the driving signals of the four switching tubes of the primary side H bridge are used for controlling the on-off sequence of the four switching tubes of the primary side H bridge so as to control the output voltage of the CLLC converter, namely the embodiment of the application adopts the internal phase shift control method to replace the frequency modulation control method to control the output voltage of the CLLC converter, thereby not only meeting the requirement of wide-range output voltage, but also simplifying the parameter design process, reducing the calculated amount and improving the control stability of the CLLC converter.
In order to realize the above embodiment, the present application further provides a sensorless synchronous rectification control method for internal phase-shifting control in the internal phase-shifting control method of the CLLC converter according to the first embodiment of the present application.
Fig. 5 is a flowchart of a sensorless synchronous rectification control method according to an embodiment of the present application.
As shown in fig. 5, the sensorless synchronous rectification control method includes the steps of:
step 210: acquiring sampling data by a sampling circuit, and acquiring a value of an intra-primary phase shift angle by a phase control module, wherein the sampling data is output voltage and output current;
step 220: determining the duty ratio of a secondary side switching tube driving signal according to the sampled data and the value of the primary side internal shift phase angle;
step 230: the secondary side switching tube driving circuit determines a synchronous rectification driving signal of the secondary side switching tube according to the duty ratio of the secondary side switching tube driving signal; and controlling the on-off of the four switching tubes of the secondary side H bridge according to the synchronous rectification driving signal.
Specifically, the sensorless synchronous rectification control method of the internal phase shift control in the CLLC converter needs to accurately generate a synchronous rectification driving signal, and the waveform of the synchronous rectification driving signal is shown in fig. 6, where V gs,S5-Vgs,S8 is the synchronous rectification driving signal of S5-S8, V gs,S5 is complementary to V gs,S6, and V gs,S7 is complementary to V gs,S8.
Further, in the positive half cycle in which each of the CLLC converters operates, the method further includes:
Between the first time point and the third time point, the secondary side current is positive, and at the moment, the S5 and the S8 are required to be conducted, and the S6 and the S7 are required to be turned off, namely the synchronous rectification driving signals V gs,S5 and V gs,S8 are required to be set to be at a high level, and the synchronous rectification driving signals V gs,S6 and V gs,S7 are required to be set to be at a low level;
Between the third time point and the fourth time point, the secondary side current is zero, and at this time, the S5 and S8 needs to be turned off, that is, the synchronous rectification driving signals V gs,S5 and V gs,S8 need to be set to low level.
It should be noted that, since the secondary side current has a zero current phase, the duty ratio Ds of the waveform of the synchronous rectification driving signal is less than 50%, and the specific value thereof is determined by the length of the secondary side current zero current phase, and is related to the specific load condition, so that the Ds value needs to be accurately calculated for generating the synchronous rectification driving signal.
In an embodiment of the present application, determining a duty cycle of a secondary side switching tube driving signal according to sampled data and a value of a primary side shift angle includes:
the current base value is determined by the output voltage and the output current, wherein the current unitary value is determined by:
Wherein, I o,unit is the current unitary value, I o is the output current, and I base is the current base value;
wherein the current base value is determined by:
wherein u base is a voltage base value, the magnitude of the voltage base value is equal to the output voltage, and z base is an impedance base value;
wherein the impedance base value is determined by:
Wherein L r1 is a primary side inductance value, L r2 is a secondary side inductance value, C r1 is a primary side capacitance value, and C r2 is a secondary side capacitance value;
The duty cycle value of the secondary side switching tube driving signal is determined by the current base value and the primary side internal phase angle value, wherein the duty cycle value of the secondary side switching tube driving signal is determined by the following formula:
wherein Ds is the duty ratio of the driving signal of the secondary side switching tube, phip is the primary side inward shift angle value, C is a first intermediate variable, D is a second intermediate variable, and I o,unit is the current unitary value;
wherein the first intermediate variable is determined by:
Wherein, C is a first intermediate variable, k is the ratio of excitation inductance to primary side inductance, w r is the angular frequency value corresponding to the resonant frequency, L r1 is the primary side inductance value, C r1 is the primary side capacitance value, I o,unit is the current unitary value, and alpha is an adjustable parameter determined by parameter setting;
wherein, the angular frequency value corresponding to the resonant frequency is determined by:
ωr＝2πfr
Wherein w r is an angular frequency value corresponding to the resonant frequency, f r is the resonant frequency, L r1 is a primary side inductance value, L r2 is a secondary side inductance value, C r1 is a primary side capacitance value, and C r2 is a secondary side capacitance value;
the second intermediate variable is determined by:
Wherein C is a first intermediate variable, D is a second intermediate variable, and phip is a primary side shift angle value.
In the embodiment of the application, the secondary side switching tube driving circuit is a PWM generating circuit, and the phase control module is a closed-loop controller, including but not limited to a PI controller.
In summary, according to the scheme provided by the embodiment of the application, sampling data is obtained through a sampling circuit, the value of the intra-primary phase shift angle is obtained through a phase control module, and the sampling data is output voltage and output current; determining the duty ratio of a secondary side switching tube driving signal according to the sampled data and the value of the primary side internal shift phase angle; the secondary side switching tube driving circuit determines a synchronous rectification driving signal of the secondary side switching tube according to the duty ratio of the secondary side switching tube driving signal; according to the synchronous rectification driving signal, the on-off of the four switching tubes of the secondary side H bridge is controlled, namely, the embodiment of the application does not need to adopt a sensor and a corresponding signal processing circuit, only needs to collect output voltage and output current, and can generate the synchronous rectification driving signal of the secondary side switching tube through simple calculation, thereby realizing the low cost of the CLLC converter, adapting to high-precision synchronous rectification control of various working voltages and switching frequency occasions and improving the power transmission efficiency.
In order to implement the above embodiments, the embodiments of the present application also provide a computer device, including a memory, a processor, and a computer program stored in the memory and executable on the processor, where the processor implements the method described in embodiment 1 or embodiment 2 of the present application when executing the computer program.
It should be noted that in the description of the present application, the terms "first," "second," and the like are used for descriptive purposes only and are not to be construed as indicating or implying relative importance. Furthermore, in the description of the present application, unless otherwise indicated, the meaning of "a plurality" is two or more.
Any process or method descriptions in flow charts or otherwise described herein may be understood as representing modules, segments, or portions of code which include one or more executable instructions for implementing specific logical functions or steps of the process, and further implementations are included within the scope of the preferred embodiment of the present application in which functions may be executed out of order from that shown or discussed, including substantially concurrently or in reverse order, depending on the functionality involved, as would be understood by those reasonably skilled in the art of the present application.
It is to be understood that portions of the present application may be implemented in hardware, software, firmware, or a combination thereof. In the above-described embodiments, the various steps or methods may be implemented in software or firmware stored in a memory and executed by a suitable instruction execution system. For example, if implemented in hardware, as in another embodiment, may be implemented using any one or combination of the following techniques, as is well known in the art: discrete logic circuits having logic gates for implementing logic functions on data signals, application specific integrated circuits having suitable combinational logic gates, programmable Gate Arrays (PGAs), field Programmable Gate Arrays (FPGAs), and the like.
Those of ordinary skill in the art will appreciate that all or part of the steps carried out in the method of the above-described embodiments may be implemented by a program to instruct related hardware, and the program may be stored in a computer readable storage medium, where the program when executed includes one or a combination of the steps of the method embodiments.
In addition, each functional unit in the embodiments of the present application may be integrated in one processing module, or each unit may exist alone physically, or two or more units may be integrated in one module. The integrated modules may be implemented in hardware or in software functional modules. The integrated modules may also be stored in a computer readable storage medium if implemented as software functional modules and sold or used as a stand-alone product.
The above-mentioned storage medium may be a read-only memory, a magnetic disk or an optical disk, or the like.
In the description of the present specification, a description referring to terms "one embodiment," "some embodiments," "examples," "specific examples," or "some examples," etc., means that a particular feature, structure, material, or characteristic described in connection with the embodiment or example is included in at least one embodiment or example of the present application. In this specification, schematic representations of the above terms do not necessarily refer to the same embodiments or examples. Furthermore, the particular features, structures, materials, or characteristics described may be combined in any suitable manner in any one or more embodiments or examples.
While embodiments of the present application have been shown and described above, it will be understood that the above embodiments are illustrative and not to be construed as limiting the application, and that variations, modifications, alternatives and variations may be made to the above embodiments by one of ordinary skill in the art within the scope of the application.
Claims (9)
1. An internal phase shift control method of a CLLC converter, the CLLC converter including a primary side H-bridge, a resonant cavity, and a secondary side H-bridge, the primary side H-bridge including a first leg and a second leg, the first leg including a first upper leg switching tube and a first lower leg switching tube, the second leg including a second upper leg switching tube and a second lower leg switching tube, the CLLC converter further including a phase controller, the method comprising:
Step 110: selecting and fixing the switching frequency of the CLLC converter;
step 120: determining phase angles between the first bridge arm and the second bridge arm through a phase controller, namely primary side internal phase angles, and determining driving signals of four switching tubes of the primary side H bridge through the primary side internal phase angles;
Step 130: the method comprises the steps of determining primary side current and exciting current according to the on-off sequence of the four switching tubes of the primary side H bridge so as to determine secondary side current, and determining the output voltage of the CLLC converter according to the secondary side current, wherein the primary side internal phase angle and the output voltage of the CLLC converter are in monotonic negative correlation.
2. The method for controlling internal phase shift according to claim 1, wherein: the secondary side H bridge comprises a third bridge arm and a fourth bridge arm, the third bridge arm comprises a third upper bridge arm switch tube and a third lower bridge arm switch tube, and the fourth bridge arm comprises a fourth upper bridge arm switch tube and a fourth lower bridge arm switch tube; the step 130 further includes:
And the resonant cavity controls zero voltage switching on of the primary side H-bridge switching tube and zero current switching off of the secondary side H-bridge switching tube according to the switching-on sequence of the four switching tubes of the primary side H-bridge.
3. The method for controlling internal phase shift according to claim 2, wherein: in step 120, dead time is added to the driving signals of the four switching tubes of the primary side H-bridge to prevent the bridge arm from being directly connected.
4. The method for controlling internal phase shift according to claim 3, wherein: the resonant cavity controls zero voltage on of a primary side H-bridge switching tube and zero current off of a secondary side H-bridge according to the on-off sequence of the four switching tubes of the primary side H-bridge, and the resonant cavity comprises the following components: in each period in which the CLLC converter operates, the positive half period and the negative half period of the operating state are symmetrical to each other; in the positive half cycle of operation of each CLLC converter, the following five operation phases are specifically included:
The first stage: the input voltage is positive between the first time point and the second time point, the primary side current is larger than the exciting current, so that the secondary side current is positive, at the moment, the first upper bridge arm switching tube and the second lower bridge arm switching tube are turned on, and the first lower bridge arm switching tube and the second upper bridge arm switching tube are turned off;
And a second stage: at the moment of the second time point, driving signals of the second upper bridge arm switching tube and the second lower bridge arm switching tube are changed to enable the second upper bridge arm switching tube to be turned on and the second lower bridge arm switching tube to be turned off, and an output capacitor of the second upper bridge arm switching tube is charged in dead time due to primary side current to enable zero voltage of the second upper bridge arm switching tube to be turned on;
And a third stage: the input voltage is zero between the second time point and the third time point, the primary side current, the exciting current and the secondary side current gradually decline until the moment of the third time point, the primary side current is equal to the exciting current so that the secondary side current is zero, and the third upper bridge arm switching tube and the fourth lower bridge arm switching tube are turned off at zero current;
Fourth stage: between the third time point and the fourth time point, the input voltage is zero, the primary side current is equal to the exciting current, the secondary side current is kept to be zero, and the secondary side of the resonant cavity does not participate in resonance;
fifth stage: at the fourth time point, the driving signals of the first upper bridge arm switching tube and the first lower bridge arm switching tube are changed to enable the first lower bridge arm switching tube to be turned on and the first upper bridge arm switching tube to be turned off, and the output capacitor of the first lower bridge arm switching tube is charged in dead time due to the fact that the primary side current is the primary side current, so that the first lower bridge arm switching tube is turned on at zero voltage.
5. The method for controlling internal phase shift according to claim 1, wherein: in the step 110, the switching frequency is a fixed frequency.
6. A sensorless synchronous rectification control method for use in a method of controlling internal phase shift in a CLLC converter according to any one of claims 1-5, wherein the CLLC converter further comprises a sampling circuit and a secondary side switching tube driving circuit, the method comprising the steps of, during each cycle in which the CLLC converter operates:
step 210: acquiring sampling data by a sampling circuit, and acquiring a value of an intra-primary phase shift angle by a phase control module, wherein the sampling data is output voltage and output current;
step 220: determining the duty ratio of a secondary side switching tube driving signal according to the sampled data and the value of the primary side internal shift phase angle;
Step 230: the secondary side switching tube driving circuit determines a synchronous rectification driving signal of the secondary side switching tube according to the duty ratio of the secondary side switching tube driving signal; and controlling the on-off of four switching tubes of the secondary side H bridge according to the synchronous rectification driving signal.
7. The sensorless synchronous rectification control method of claim 6, wherein: the determining the duty ratio of the secondary side switching tube driving signal according to the sampled data and the value of the primary side internal shift angle comprises the following steps:
the current base value is determined by the output voltage and the output current, wherein the current unitary value is determined by:
Wherein, I o,unit is the current unitary value, I o is the output current, and I base is the current base value;
wherein the current base value is determined by:
Wherein u base is a voltage base value, the magnitude of the voltage base value is equal to the output voltage, and z base is an impedance base value;
wherein the impedance base value is determined by:
Wherein L r1 is a primary side inductance value, L r2 is a secondary side inductance value, C r1 is a primary side capacitance value, and C r2 is a secondary side capacitance value;
The duty cycle value of the secondary side switching tube driving signal is determined by the current base value and the primary side internal phase angle value, wherein the duty cycle value of the secondary side switching tube driving signal is determined by the following formula:
Wherein Ds is the duty ratio of the driving signal of the secondary side switching tube, phip is the primary side inward shift angle value, C is a first intermediate variable, D is a second intermediate variable, and I o,unit is the current unitary value;
wherein the first intermediate variable is determined by:
Wherein, C is a first intermediate variable, k is the ratio of excitation inductance to primary side inductance, w r is the angular frequency value corresponding to the resonant frequency, L r1 is the primary side inductance value, C r1 is the primary side capacitance value, I o,unit is the current unitary value, and alpha is an adjustable parameter determined by parameter setting;
wherein, the angular frequency value corresponding to the resonant frequency is determined by:
Wherein w r is an angular frequency value corresponding to the resonant frequency, f r is the resonant frequency, L r1 is a primary side inductance value, L r2 is a secondary side inductance value, C r1 is a primary side capacitance value, and C r2 is a secondary side capacitance value;
the second intermediate variable is determined by:
Wherein C is a first intermediate variable, D is a second intermediate variable, and phip is a primary side shift angle value.
8. The sensorless synchronous rectification control method of claim 6, wherein:
The secondary side switching tube driving circuit is a PWM generating circuit, and the phase control module is a closed-loop controller.
9. A computer device comprising a memory, a processor and a computer program stored on the memory and executable on the processor, the processor implementing the CLLC converter internal phase shift control method according to any one of claims 1-5 or the sensorless synchronous rectification control method according to any one of claims 6-8 when executing the computer program.
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