CN116827136A - Zero-return power prediction control method and system for double-active-bridge series resonant converter - Google Patents
Zero-return power prediction control method and system for double-active-bridge series resonant converter Download PDFInfo
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Abstract
The application belongs to the technical field of converter optimization control, and particularly relates to a zero-return power prediction control method and system for a double-active-bridge series resonant converter, wherein the method comprises the following steps: acquiring state parameters of the double-active-bridge series resonant converter; constructing a multi-phase shift model predictive control model according to the acquired state parameters and based on a fundamental wave analysis method to obtain a primary and secondary bridge port voltage fundamental wave component phase difference of the double-active bridge series resonant converter; zero return power control under multiple phase shifting is carried out on the obtained voltage fundamental component phase difference, so that an optimized phase shifting angle is obtained; and performing phase shift modulation of the double-active-bridge series resonant converter according to the obtained optimized phase shift angle, and realizing zero reflux power predictive control of the double-active-bridge series resonant converter.
Description
Technical Field
The application belongs to the technical field of converter optimal control, and particularly relates to a zero-return power prediction control method and system for a double-active-bridge series resonant converter.
Background
The statements in this section merely provide background information related to the present disclosure and may not necessarily constitute prior art.
The double-active-bridge series resonant converter (Dual Bridge Series Resonant Converter, DBSRC) has the advantages of higher sine degree of inductive current and smaller turn-off current of a switching tube, and is widely applied to various energy storage device interfaces. Under the traditional single phase shift (Singe Phase Shift, SPS) modulation, the DBSRC inevitably generates reflux power on the primary side and the secondary side, and larger input voltage or input current is required when the same power is transmitted, so that the resonant cavity needs to bear larger voltage and current stress, the switching loss of the system is increased, and the efficiency of the converter is reduced.
When the conventional PI control is applied to DBSRC, the system adjustment time is long due to the existence of an integration link, and for a multi-input multi-output system, the coupling between control loops makes PI parameters difficult to adjust. The model predictive control has the advantages of multi-target control, quick dynamic response and strong robustness, is widely applied to the field of converter control, and is already applied to DBSRC.
The inventor knows that in the aspect of reflux power inhibition, an expansion phase shift control (Extended Phase Shift, EPS) strategy can be adopted and frequency conversion modulation is combined, and zero reflux power control under any transmission power is realized by adjusting the relation between the zero crossing point of resonance current and the voltage phase of the primary and secondary side H bridge port. The method only comprises two control degrees of freedom, and the control of the transmission power adopts variable frequency modulation; in terms of model predictive control, the predictive model of DBSRC under single phase shift control may be derived, but it does not involve the solution of multiple phase shift control predictive models under efficiency optimization.
Disclosure of Invention
In order to solve the problems, the application provides a zero return power prediction control method and a zero return power prediction control system for a double-active-bridge series resonant converter, which introduce model prediction control (Model Predictive Control, MPC) to accelerate the dynamic response speed of a DBSRC, solve the problem that the return power of the DBSRC is higher under the non-unity voltage gain, and realize the quick dynamic response of the system.
According to some embodiments, the first scheme of the application provides a zero-return power prediction control method for a dual-active bridge series resonant converter, which adopts the following technical scheme:
a zero-return power prediction control method for a double-active-bridge series resonant converter comprises the following steps:
acquiring state parameters of the double-active-bridge series resonant converter;
constructing a multi-phase shift model predictive control model according to the acquired state parameters and based on a fundamental wave analysis method to obtain a primary and secondary bridge port voltage fundamental wave component phase difference of the double-active bridge series resonant converter;
zero return power control under multiple phase shifting is carried out on the obtained voltage fundamental component phase difference, so that an optimized phase shifting angle is obtained;
and performing phase shift modulation of the double-active-bridge series resonant converter according to the obtained optimized phase shift angle, and realizing zero reflux power predictive control of the double-active-bridge series resonant converter.
As a further technical definition, the detected state variables include at least the input voltage, the output voltage and the output current of the double active bridge series resonant converter.
As a further technical limitation, in the process of constructing the multi-phase shift model predictive control model, discretizing the acquired state variable through a forward euler method to obtain a predicted value of the state variable at the next moment, constructing a cost function according to the obtained predicted value, and calculating the fundamental component phase difference of the primary and secondary bridge mouth voltage.
Further, in the process of calculating the fundamental component phase difference of the primary and secondary bridge voltage, derivative processing is carried out on the constructed cost function, and when the derivative of the cost function is zero, an outward phase shift angle is obtained; and converting the obtained external phase shift angle to obtain the fundamental wave component phase difference of the primary and secondary bridge port voltage.
Further, in the process of controlling zero return power under multiple phase shifting, when the voltage gain is smaller than a preset value, the external phase shifting angle controls the output voltage, so that the total transmission power reaches a given value; and adjusting the internal phase angle of the primary side so that the voltage of the primary side bridge port and the secondary side bridge port rises along the same phase.
Further, the intra-secondary phase angle is adjusted, so that the same phase of the resonance current zero-crossing point and the bridge voltage edge is realized; and replacing the fundamental wave phase difference with the external phase shift angle according to the relation between the resonant current expression and the internal phase shift angle and the external phase shift angle to obtain the optimized phase shift angle.
Further, in the process of zero return power control under multiple phase shifting, when the voltage gain is larger than a preset value, the secondary side internal shift angle is negative, and the optimized shift angle is obtained according to the relation between fundamental wave phase differences.
According to some embodiments, a second aspect of the present application provides a dual active bridge series resonant converter zero-return power prediction control system, which adopts the following technical scheme:
a dual active bridge series resonant converter zero return power predictive control system comprising:
an acquisition module configured to acquire a state parameter of the dual active bridge series resonant converter;
the control module is configured to construct a multi-phase shift model prediction control model according to the acquired state parameters and based on a fundamental wave analysis method, so as to obtain a primary and secondary side bridge port voltage fundamental wave component phase difference of the double-active bridge series resonant converter; zero return power control under multiple phase shifting is carried out on the obtained voltage fundamental component phase difference, so that an optimized phase shifting angle is obtained; and performing phase shift modulation of the double-active-bridge series resonant converter according to the obtained optimized phase shift angle, and realizing zero reflux power predictive control of the double-active-bridge series resonant converter.
According to some embodiments, a third aspect of the present application provides a computer-readable storage medium, which adopts the following technical solutions:
a computer-readable storage medium having stored thereon a program which, when executed by a processor, implements the steps in a dual active bridge series resonant converter zero return power predictive control method according to the first aspect of the application.
According to some embodiments, a fourth aspect of the present application provides an electronic device, which adopts the following technical solutions:
an electronic device comprising a memory, a processor and a program stored on the memory and executable on the processor, the processor implementing the steps in the dual active bridge series resonant converter zero return power predictive control method according to the first aspect of the application when the program is executed.
Compared with the prior art, the application has the beneficial effects that:
the application provides a zero-return power control strategy based on model predictive control, which aims at solving the problems of difficult design and slower dynamic response speed of a magnetic element caused by variable frequency modulation in the existing control strategy, and aims at solving the problems that the zero-return power of the primary side and the secondary side are zero by adjusting the primary side internal phase angle to enable the rising edge of the primary side bridge port voltage to be in the same phase and adjusting the secondary side internal phase angle to achieve the same phase of the resonance current zero-crossing point and the bridge port voltage edge, reducing the voltage and current stress required to bear by a resonant cavity when the same power is transmitted, reducing the switching loss of a system and improving the efficiency of a converter. Meanwhile, the application introduces model predictive control, establishes an output voltage cost function and realizes the quick dynamic response of the system.
Drawings
The accompanying drawings, which are included to provide a further understanding of the embodiments and are incorporated in and constitute a part of this specification, illustrate and explain the embodiments and together with the description serve to explain the embodiments.
Fig. 1 is a schematic diagram of a topology of a dual active bridge series resonant converter according to a first embodiment of the present application;
FIG. 2 is a diagram showing waveforms of operation of a dual active bridge series resonant converter under triple phase shift control in accordance with a first embodiment of the present application;
FIG. 3 is a waveform diagram illustrating the operation of a dual active bridge series resonant converter under zero return power control in accordance with a first embodiment of the present application;
fig. 4 is a control flow chart of a control method for predicting zero return power of a dual active bridge series resonant converter according to a first embodiment of the present application.
Detailed Description
The application will be further described with reference to the drawings and examples.
It should be noted that the following detailed description is exemplary and is intended to provide further explanation of the application. Unless defined otherwise, all technical and scientific terms used herein have the same meaning as commonly understood by one of ordinary skill in the art to which this application belongs.
It is noted that the terminology used herein is for the purpose of describing particular embodiments only and is not intended to be limiting of exemplary embodiments according to the present application. As used herein, the singular is also intended to include the plural unless the context clearly indicates otherwise, and furthermore, it is to be understood that the terms "comprises" and/or "comprising" when used in this specification are taken to specify the presence of stated features, steps, operations, devices, components, and/or combinations thereof.
Embodiments of the application and features of the embodiments may be combined with each other without conflict.
Example 1
The embodiment of the application introduces a zero-return power prediction control method for a double-active-bridge series resonant converter.
In terms of the back-flow power suppression, the following disadvantages exist in the prior art:
(1) Zero reflux power control in the full load range is realized through variable frequency modulation, so that magnetic elements in the converter such as resonant inductance, high-frequency transformers and the like are difficult to design;
(2) The output voltage is stable through the PI regulator, and the dynamic response speed is slower.
Therefore, the present embodiment proposes a zero-return power control strategy based on predictive control, which specifically includes: modeling DBSRC triple phase shift control (Triple Phase Shift, TPS) based on fundamental wave analysis (Fundamental Harmonic Analysis, FHA), and ignoring higher harmonic components in the resonant current to reduce the calculated amount; the triple phase shift control replaces the original scheme of expanding phase shift and variable frequency modulation, so that the design difficulty of magnetic elements in a circuit is reduced; the dynamic performance of the system is improved by introducing model predictive control, and the problem of long system adjustment time under traditional PI control is solved.
A zero-return power prediction control method for a double-active-bridge series resonant converter comprises the following steps:
acquiring state parameters of the double-active-bridge series resonant converter;
constructing a multi-phase shift model predictive control model according to the acquired state parameters and based on a fundamental wave analysis method to obtain a primary and secondary bridge port voltage fundamental wave component phase difference of the double-active bridge series resonant converter;
zero return power control under multiple phase shifting is carried out on the obtained voltage fundamental component phase difference, so that an optimized phase shifting angle is obtained;
and performing phase shift modulation of the double-active-bridge series resonant converter according to the obtained optimized phase shift angle, and realizing zero reflux power predictive control of the double-active-bridge series resonant converter.
As shown in fig. 1, the main circuit includes an input side supporting capacitor C 1 Output side supporting capacitor C 2 Resonant capacitor L r Resonant inductance C r High-frequency transformer T and switch tube S 1 ～S 8 And anti-parallel diodes thereof. The double-active-bridge series resonant converter comprises four bridge arms, wherein the upper and lower switching tubes of each bridge arm are complementarily conducted, and the driving signals of the complemental switching tubes are square wave signals with the duty ratio of 50%, namely, each switching tube is conducted for half of a switching period.
The DBSRC working waveform under TPS is shown in figure 2, and the primary side phase shift angle is recorded as alpha 1 The secondary side phase shift angle is alpha 2 The outward phase angle isWith leading primary bridge arm midpoint voltage rising edge alpha 1 The angle/2 is the timing zero point, the fundamental component phase of the midpoint voltage of the primary bridge arm is zero, and the fundamental component phase of the midpoint potential difference of the secondary bridge arm
Carrying out Fourier decomposition on the midpoint voltage of the bridge arm of the primary side and the secondary side and taking the fundamental component of the voltage:
in formula (1), ω s For switching angular frequency, v AB Representing the fundamental component of the midpoint voltage of the primary bridge arm, v' CD.1 Representing the fundamental component of the secondary leg midpoint voltage, the resonant current can be represented as:
wherein M represents a voltage gain, and the value of the gain is nV 2 /V 1 . Neglecting losses generated by wire impedance, on-resistance of a switching tube, parasitic resistance of a supporting capacitor and the like in the power transmission process, taking the voltage of a secondary side bridge port as an example, the transmission power of the converter is as follows:
when M <1, the DBSRC operation waveform is as shown in FIG. 3 (a). The external phase shift angle controls the output voltage, so that the total transmission power reaches a given value; the rising edges of the bridge openings of the primary side and the secondary side are in the same phase by adjusting the inward movement phase angle of the primary side; and adjusting the intra-secondary-side intra-phase angle to realize that the resonance current zero-crossing point is in phase with the bridge voltage edge. At this time, the voltage of the primary and secondary side bridge port and the resonant current are always in the same direction, frequency conversion control is not adopted, and the circuit design is simple.
The resonant current expression is given in the formula (2), and in order to achieve the above-mentioned internal and external phase shift angle relationship, the formula (2) should satisfy:
wherein the method comprises the steps of
In the solution of the formula (4), the fundamental wave phase difference beta is replaced by the external phase shift angle for the convenience of the controller operationSolving the formula (4) to obtain an optimized phase shift angle expression as follows:
when M>1, the secondary side shift phase angle is negative, and the operational waveform is as shown in fig. 3 (b), and the fundamental wave phase difference equation relationship in equation (4) becomes:the optimized phase shift angle expression is:
as shown in fig. 1, the instantaneous value i of the supporting capacitance current is output according to kirchhoff's current law f (t) can be expressed as:
i f (t)＝i 2 (t)-i o (t) (7)
capacitive current i f (t) can be represented by a derivative term of the capacitance voltage, i 2 (t) may be represented by the system output power, namely:
wherein C is o Supporting a capacitance for the output of the DBSRC; u (u) o (t) is the output voltage; u (u) in (t) is the output voltage; n is the turns ratio of the high-frequency transformer; x is X LC The impedance of the resonant cavity is; alpha 1 2 and alpha 2 And/2 is the magnitude of the internal shift angle of the primary side and the secondary side of the DBSRC respectively; beta is the fundamental wave component phase difference of the primary and secondary bridge voltage; i.e o And (t) is the load current.
In order to obtain a prediction model of the DBSRC, discretizing the output voltage differential term by adopting a forward Euler method:
wherein k represents the working time, T s Is a duty cycle.
Substituting the formula (9) into the formula (8) can obtain a predicted value expression of the output voltage at the k+1 time as follows:
in order to make the output voltage reach the given value as soon as possible and remain stable, a cost function can be established
The smaller the cost function, the smaller the deviation between the output support capacitance voltage and the given voltage at the next sampling instant. The control quantity is thus calculated such that the cost function takes a minimum, i.e. J (t k ) The derivative is zero. Substituting the formula (10) into the formula (11) and deriving the formula to enable the derivative to be zero, and obtaining the external phase angle expression as follows:
as shown in fig. 4, the specific implementation manner of zero return power control of DBSRC is:
step S01: sensor pair kth time DBSRC input voltage u in (t k ) Output voltage u o (t k ) And output current i o (t k ) Sampling and setting the given value of output voltage
Step S02: the shift angle alpha of the k-1 moment calculated in the step S04 in the last working period is calculated 1 And alpha 2 And the input voltage u obtained in step S01 in the working period in (t k ) Output voltage u o (t k ) And output current i o (t k ) Substituting the phase shift angle into a DBSRC model predictive controller (12) to obtain an external phase shift angle
Step S03: phase-shifting the outer angleConverting into a primary and secondary side bridge port voltage fundamental component phase difference beta;
step S04: calculating voltage gain M according to the turn ratio of the transformer, namely the input/output voltage transformation ratio, substituting the voltage gain M and fundamental wave phase difference beta into the formula (5) or the formula (6) to obtain alpha 1 And alpha 2 Temporarily storing the data for the next working cycle step S02;
step S05: the obtained phase shift alpha 1 、α 2 Andand the control signals are input into a phase-shifting modulator to carry out phase-shifting modulation, so as to obtain control signals of each switching tube, and the converter is controlled to realize zero return power control.
And the steps are circulated, so that the zero reflux power prediction control of the double-active full-bridge series resonant converter can be realized. The control strategy effectively improves the dynamic performance of the system, realizes zero system reflux power in one working period, and improves the efficiency of the converter.
The embodiment provides a zero-return power control strategy based on model predictive control aiming at the problems of difficult design and slower dynamic response speed of a magnetic element caused by variable frequency modulation in the existing control strategy, and the zero-return power control strategy realizes the same phase of a resonance current zero-crossing point and a bridge port voltage edge by adjusting the primary side internal phase angle to enable the same phase of the primary side secondary side bridge port voltage rising edge and the secondary side internal phase angle, realizes zero primary side secondary side return power, reduces the voltage and current stress required to bear by a resonant cavity when the same power is transmitted, reduces the switching loss of a system, and improves the efficiency of a converter. Meanwhile, model predictive control is introduced, an output voltage cost function is established, and quick dynamic response of the system is realized.
Example two
The embodiment of the application introduces a zero-return power prediction control system of a double-active-bridge series resonant converter.
A dual active bridge series resonant converter zero return power predictive control system comprising:
an acquisition module configured to acquire a state parameter of the dual active bridge series resonant converter;
the control module is configured to construct a multi-phase shift model prediction control model according to the acquired state parameters and based on a fundamental wave analysis method, so as to obtain a primary and secondary side bridge port voltage fundamental wave component phase difference of the double-active bridge series resonant converter; zero return power control under multiple phase shifting is carried out on the obtained voltage fundamental component phase difference, so that an optimized phase shifting angle is obtained; and performing phase shift modulation of the double-active-bridge series resonant converter according to the obtained optimized phase shift angle, and realizing zero reflux power predictive control of the double-active-bridge series resonant converter.
The detailed steps are the same as those of the method for predicting and controlling zero return power of the dual active bridge series resonant converter provided in the first embodiment, and will not be described herein.
Example III
The third embodiment of the application provides a computer readable storage medium.
A computer readable storage medium having stored thereon a program which when executed by a processor performs the steps in a method for controlling zero return power prediction of a dual active bridge series resonant converter according to the first embodiment of the application.
The detailed steps are the same as those of the method for predicting and controlling zero return power of the dual active bridge series resonant converter provided in the first embodiment, and will not be described herein.
Example IV
The fourth embodiment of the application provides electronic equipment.
An electronic device comprising a memory, a processor and a program stored on the memory and executable on the processor, wherein the processor implements the steps in the dual active bridge series resonant converter zero return power predictive control method according to the first embodiment of the application when executing the program.
The detailed steps are the same as those of the method for predicting and controlling zero return power of the dual active bridge series resonant converter provided in the first embodiment, and will not be described herein.
The above description is only a preferred embodiment of the present embodiment, and is not intended to limit the present embodiment, and various modifications and variations can be made to the present embodiment by those skilled in the art. Any modification, equivalent replacement, improvement, etc. made within the spirit and principle of the present embodiment should be included in the protection scope of the present embodiment.
Claims (10)
1. The zero-return power prediction control method for the double-active-bridge series resonant converter is characterized by comprising the following steps of:
acquiring state parameters of the double-active-bridge series resonant converter;
constructing a multi-phase shift model predictive control model according to the acquired state parameters and based on a fundamental wave analysis method to obtain a primary and secondary bridge port voltage fundamental wave component phase difference of the double-active bridge series resonant converter;
zero return power control under multiple phase shifting is carried out on the obtained voltage fundamental component phase difference, so that an optimized phase shifting angle is obtained;
and performing phase shift modulation of the double-active-bridge series resonant converter according to the obtained optimized phase shift angle, and realizing zero reflux power predictive control of the double-active-bridge series resonant converter.
2. A method of controlling zero-return power prediction of a dual active bridge series resonant converter as recited in claim 1 wherein the obtained state parameters include at least an input voltage, an output voltage, and an output current of the dual active bridge series resonant converter.
3. The method for predicting and controlling zero return power of a double active bridge series resonant converter according to claim 1, wherein in the process of constructing a multi-phase shift model predictive control model, discretizing the obtained state variables by a forward euler method to obtain predicted values of the state variables at the next moment, constructing a cost function according to the obtained predicted values, and calculating the phase difference of the fundamental wave components of the primary and secondary bridge port voltages.
4. A method for predicting and controlling zero return power of a double active bridge series resonant converter as claimed in claim 3, wherein in the process of calculating the phase difference of fundamental wave components of the primary and secondary bridge voltages, the constructed cost function is subjected to derivative processing, and when the derivative of the cost function is zero, the phase angle of the outer shift is obtained; and converting the obtained external phase shift angle to obtain the fundamental wave component phase difference of the primary and secondary bridge port voltage.
5. The method for predicting and controlling zero return power of a double active bridge series resonant converter as recited in claim 4, wherein the external phase shift angle controls the output voltage to achieve the total transmission power reaching the given value when the voltage gain is smaller than a preset value in the process of controlling zero return power under multiple phase shifts; and adjusting the internal phase angle of the primary side so that the voltage of the primary side bridge port and the secondary side bridge port rises along the same phase.
6. The method for predicting and controlling zero return power of a dual active bridge series resonant converter as recited in claim 5 wherein adjusting the secondary side internal phase angle achieves the same phase of the resonant current zero crossing point and the bridge voltage edge; and replacing the fundamental wave phase difference with the external phase shift angle according to the relation between the resonant current expression and the internal phase shift angle and the external phase shift angle to obtain the optimized phase shift angle.
7. The method of claim 4, wherein the secondary side internal phase shift angle is negative when the voltage gain is greater than a predetermined value during the zero-return power control under multiple phase shifts, and the optimized phase shift angle is obtained according to the relationship between the fundamental wave phase differences.
8. A dual active bridge series resonant converter zero return power predictive control system comprising:
an acquisition module configured to acquire a state parameter of the dual active bridge series resonant converter;
the control module is configured to construct a multi-phase shift model prediction control model according to the acquired state parameters and based on a fundamental wave analysis method, so as to obtain a primary and secondary side bridge port voltage fundamental wave component phase difference of the double-active bridge series resonant converter; zero return power control under multiple phase shifting is carried out on the obtained voltage fundamental component phase difference, so that an optimized phase shifting angle is obtained; and performing phase shift modulation of the double-active-bridge series resonant converter according to the obtained optimized phase shift angle, and realizing zero reflux power predictive control of the double-active-bridge series resonant converter.
9. A computer readable storage medium having stored thereon a computer program, which when executed by a processor implements the steps of the dual active bridge series resonant converter zero return power predictive control method of any of claims 1-7.
10. An electronic device comprising a memory, a processor and a computer program stored on the memory and executable on the processor, wherein the processor implements the steps of the dual active bridge series resonant converter zero return power predictive control method of any one of claims 1-7 when the program is executed by the processor.
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| CN118017849A (en) * | 2024-04-09 | 2024-05-10 | 西安图为电气技术有限公司 | Soft start and light load control method for double-active-bridge series resonant converter |
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| CN118017849A (en) * | 2024-04-09 | 2024-05-10 | 西安图为电气技术有限公司 | Soft start and light load control method for double-active-bridge series resonant converter |
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