CN113904560A - DAB converter multi-target unified control method based on triple phase-shift control - Google Patents

DAB converter multi-target unified control method based on triple phase-shift control Download PDF

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CN113904560A
CN113904560A CN202111192878.6A CN202111192878A CN113904560A CN 113904560 A CN113904560 A CN 113904560A CN 202111192878 A CN202111192878 A CN 202111192878A CN 113904560 A CN113904560 A CN 113904560A
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mode
phase shift
power
current stress
switching
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曾进辉
饶尧
兰征
何东
梁博文
黄浪尘
邹彬
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Hunan University of Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/24—Arrangements for preventing or reducing oscillations of power in networks
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/38—Arrangements for parallely feeding a single network by two or more generators, converters or transformers
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention discloses a DAB converter multi-target unified control method based on triple phase shift control, which comprises the steps of establishing an analytic model of a triple phase shift control optimal mode, minimizing current stress under different working modes based on a cost function optimization equation, deducing soft switching power constraint ranges of all switching tubes and ensuring that all switching tubes realize zero-voltage switching. And meanwhile, a virtual power component is constructed in the efficiency optimization phase-shift ratio combination, a phase-shift ratio expression under the multi-target unified control method is obtained based on the relation between the efficiency optimization phase-shift ratio combination and the virtual power component, and the response speed of the output power under the condition of input voltage or load sudden change is improved through power control. The invention can realize the minimum current stress of the DAB converter in the full power range, enables all switching tubes to work in the soft switching range, effectively reduces the conduction loss and the switching loss of the DAB converter, and improves the stability of the output voltage and the output power of the system when the system suddenly changes states.

Description

DAB converter multi-target unified control method based on triple phase-shift control
Technical Field
The invention relates to the technical field of power transmission, in particular to a DAB converter multi-target unified control method based on triple phase-shift control.
Background
With the development of power electronic technology, the high-frequency isolation power conversion technology is applied to the power grid more and more, and becomes an important means for realizing quick and flexible control in the power grid. The double-active full-bridge converter based on the phase-shift control technology has the advantages of high power density, fast dynamic response, easy realization of soft switching, bidirectional power flow and the like, and is popular in occasions such as uninterrupted power supplies, electric automobiles, solid-state transformers and the like.
In order to simultaneously realize the target optimization of current stress and soft switching equivalent ratio of the double-active-bridge converter and improve the dynamic performance of the output power of the converter, the invention provides a multi-target unified optimization control strategy based on triple phase-shift control.
Disclosure of Invention
The invention aims to provide a DAB converter multi-target unified control method based on triple phase-shift control so as to improve the performance and efficiency of the DAB converter in the prior art.
The purpose of the invention can be realized by the following technical scheme:
a DAB converter multi-target unified control method based on triple phase shift control comprises the following steps:
firstly, establishing an analytic model of a triple phase-shift control optimal mode;
secondly, minimizing current stress under different working modes based on a cost function optimization equation, deducing soft switching power constraint ranges of all switching tubes, and ensuring that all switching tubes realize zero-voltage switching;
and thirdly, constructing a virtual power component in the efficiency optimization phase-shifting ratio combination, obtaining a phase-shifting ratio expression under the multi-target unified control method based on the relation between the efficiency optimization phase-shifting ratio combination and the virtual power component, and improving the response speed of the output power under the condition of input voltage or load sudden change through power control.
As a further aspect of the invention, the transmission power and current stress in the TPS control in the first step in three modes are:
Figure BDA0003301935980000021
Figure BDA0003301935980000022
wherein p is transmission power, G is current stress, D1 and D3 are phase shift ratios in an H1 full bridge and an H2 full bridge, respectively, and are referred to as an internal shift ratio;
d2 is the phase shift ratio between the H1 full bridge and the H2 full bridge, which is called the external phase shift ratio;
the value range of the shift ratio in the mode 1 is more than or equal to 0 and less than or equal to D1≤D2≤1,D1≤D3≤1；
The value range of the shift ratio in the mode 2 is more than or equal to 0 and less than or equal to D2≤D1≤1,D1≤D3≤1；
The value range of the shift ratio in the mode 3 is more than or equal to 0 and less than or equal to D2≤D1≤1,0≤D3≤D1。
As a further scheme of the invention, the cost function optimization equation is as follows:
λ(1,j)＝λ(2,j)＝λ(3,j)
where λ is a cost function defined as:
Figure BDA0003301935980000023
wherein: i represents a control variable, i.e. Di represents a different phase shift ratio; j represents the working mode, and Gj and Pj represent the current stress and the transmission power in different modes; i and j each take the values 1, 2 and 3.
As a further aspect of the present invention, the minimum current stress in different operating modes is:
mode 1 has a minimum current stress of
Figure BDA0003301935980000031
mode 2 has a minimum current stress of
Figure BDA0003301935980000032
Since the optimal phase shift ratio combination for mode 2 is at the domain boundary for mode 2 and mode 3, the minimum current stress optimal solution for mode 3 is the same as for mode 2;
as a further scheme of the present invention, the soft switching power constraint ranges of all the switching tubes in the three modes are:
in the mode 1, the switching tube can be realized in the working range of the whole mode 1;
all switching tube thresholds in the working ranges of mode 2 and mode 3 satisfy ZVS.
As a further aspect of the present invention, the virtual power component in the third step is:
Figure BDA0003301935980000033
in the formula: vv is defined as a virtual voltage component, which is an output value of the PI controller; v2 is the desired output voltage; v2 and i2 are the actual sampled output voltage and output current, respectively.
As a further aspect of the present invention, the phase shift ratio in the third step is expressed as:
Figure BDA0003301935980000034
the invention has the beneficial effects that:
(1) compared with SPS and DPS control, the invention can realize the minimum current stress of the DAB converter in the full power range by modulating the phase shift ratio of three dimensions, and effectively reduces the conduction loss of the DAB converter;
(2) according to the invention, by deducing the soft switching power constraint ranges of all the switching tubes and optimizing the combination of the phase shift ratio extremum of the current stress, all the switching tubes of the DAB converter are in a ZVS state, so that the switching loss of the DAB converter is effectively reduced;
(3) the MUOC control method based on TPS not only improves the efficiency of the DAB converter, but also can reduce the dynamic response time of the system and improve the stability of the output voltage and the output power when the system suddenly changes states.
Drawings
The invention will be further described with reference to the accompanying drawings.
FIG. 1 is a schematic diagram of the topology of a DAB converter;
FIG. 2 is a schematic diagram of the switching sequence and steady state operating waveforms of a full bridge of the DAB converter;
FIG. 3 is a schematic diagram of the full bridge AC output voltage waveform in different modes;
FIG. 4 is a schematic diagram of full bridge AC output voltage and inductor current waveforms for each time period of mode 1-3;
FIG. 5 is a schematic diagram of optimized current stress curves for single-phase-shift controlled current stress, dual-phase-shift, and triple-phase-shift controlled current stress;
fig. 6 is a ZVS power constraint boundary diagram for each mode.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
As shown in fig. 1, a topology structure of a Dual Active Bridge (DAB) converter, where T is a transformer with a turn ratio of n, C1 and C2 are capacitors on the full-bridge H1 and the full-bridge H2 sides, respectively, L is the sum of a leakage inductance and an auxiliary inductance of the transformer, and vH1 and vH2 are equivalent ac output voltages on the V1 side H1 and H2, respectively;
the voltage conversion ratio of the DAB converter is defined as k as V1/nV2, and the analysis is carried out by taking k to be more than or equal to 1 as an example;
the switching sequence and the steady state operating waveform of the full bridge of the DAB converter based on triple-phase-shift (TPS) control are shown in fig. 2. Wherein Ths is half of the switching period, and is 1/2 fs; d1 and D3 are phase shift ratios in the H1 full bridge and the H2 full bridge, respectively, called an internal shift ratio; d2 is the phase shift ratio between the H1 full bridge and the H2 full bridge, which is called the external phase shift ratio;
according to kirchhoff voltage law vL-vH 1-vH2, different inductor voltages vL form different inductor currents iL, so that the operating modes of TPS control can be distinguished based on different vL;
D1-D3 are in relation to the ascending and descending order of vH1 and vH2, the waveform of the primary full bridge vH1 is determined only by the phase shift ratio D1, and the waveform of the secondary full bridge vH2 is determined by the phase shift ratios D2 and D3;
considering forward power flow, power is transferred from vH1 to vH 2;
d1 ∈ [0,1] ^ D2 ∈ [0,1] ^ D3 ∈ [0,2], the TPS control can be divided into 6 modes according to the magnitude relation between the shift ratios, the full-bridge AC output voltage waveform under different modes is shown in FIG. 3, and the value range of the shift ratio D1-D3 is as follows:
Figure BDA0003301935980000051
since the relationship of D2 and D3 in mode 4-6 satisfies 1 ≦ D3, in these several modes, S1 has been turned off (i.e., falling edge of vH 1) before Q1 and Q4 are turned on (i.e., rising edge of vH 2), there is no time period satisfying that the polarities of vH1 and vH2 are the same, i.e., power will not be able to transfer directly from H1 to H2, resulting in very large return power in mode 4-6, with a significant increase in iL;
therefore, when selecting efficiency optimization as a target, mode 4-6 is no longer considered, and the current stress optimization for mode 1-3 is analyzed in detail below;
deducing expressions of transmission power and current stress under different modes of TPS control by adopting a sectional analysis method; FIG. 4 shows the specific switching times of the modes 1-3, and the full-bridge AC output voltage and the inductor current waveforms corresponding to the respective time periods;
the expressions of the transmission power and the inductive current stress of the DAB converter are
Figure BDA0003301935980000061
For simplicity of analysis, the transmission power and the current stress are unified into
Figure BDA0003301935980000062
In the formula: pbase is used as reference power; ibase is reference current;
combining equations (1) - (2) and fig. 4, we can obtain the transmission power and current stress in the TPS controlled in three modes:
Figure BDA0003301935980000063
Figure BDA0003301935980000064
solving for the minimum current stress, the Lagrange Multiplier Method (LMM) is commonly used, but there are two problems in constructing a mathematical model of LMM:
1) due to the constraint of the relation of the transmission power and the phase shift ratio, the feasible domain of the method may not be a convex set;
2) it is not meaningful to study the current stress by neglecting the transmission power, however, the power transmission range has overlapped parts under different operation modes, and for a specific power transmission point, different optimal phase shift ratio combinations may be corresponding to the power transmission range, so that the optimal solution is difficult to be solved by using the LMM.
Under specific transmission power, the method for solving the TPS control current stress optimization problem by constructing a cost function is considered, wherein the cost function lambda is defined as
Figure BDA0003301935980000071
In the formula: i represents a control variable, i.e. Di represents a different phase shift ratio; j represents the working mode, and Gj and Pj represent the current stress and the transmission power in different modes; i and j all take on values of 1, 2 and 3, and the cost function lambda represents the variation between the cost and the gain caused by small disturbance in the control variable;
according to the formula (5), a cost function formed by three different phase shift ratios exists in a certain specific mode, and when the three cost functions are different, the influence of the system on adjusting the different phase shift ratios is different; assuming that the cost function of trim D2 is greater in mode 1 than the cost function of trim D1, i.e., λ (2,1) > λ (1,1) >0, one can obtain
Figure BDA0003301935980000072
Since the disturbance of D1 and D2 is small, the disturbance in the transmission power is negligible, and assuming that D1 is increased, D2 is decreased, and D3 is unchanged, the transmission power with the changed phase shift ratio and the current stress can be obtained as follows
Figure BDA0003301935980000073
Figure BDA0003301935980000074
From equation (7), the following relationship can be derived
Figure BDA0003301935980000075
By substituting formula (9) for formula (8)
Figure BDA0003301935980000076
As can be seen from equation (10), when the transmission power is constant, D1 increases and D2 decreases, and since the cost function of adjusting D2 is greater than the cost function of adjusting D1, the current stress decreases;
if the three cost functions are not equal, adjusting one of the cost functions inevitably enables the current stress to be further reduced, so in order to realize the current stress optimization control, the three cost functions must be equal, as shown in formula (11);
λ(1,j)＝λ(2,j)＝λ(3,j) (11)
equation (11) is defined as a Cost Function Optimization (CFO) equation, and includes equation constraints of two cost functions, and in combination with a specific transmission power constraint condition, a unique current stress optimal phase shift ratio combination at the power level can be solved;
the CFO equation in mode 1 can be tabulated as follows according to equation (11)
Figure BDA0003301935980000081
By solving the formula (12), the
Figure BDA0003301935980000082
Substituting the above equation into the transmission power analysis model of mode 1, the following relation equation of phase shift ratio extreme value combination with respect to k and p can be obtained
Figure BDA0003301935980000083
Substituting the obtained extreme value into the current stress expression to obtain the minimum current stress of
Figure BDA0003301935980000084
Wherein the shift ratio D1 and the transmission power p are in the range
Figure BDA0003301935980000085
Similarly, the combination of the phase shift ratio extremes for mode 2 can be found with respect to the relationship between k and p and the minimum current stress as follows:
Figure BDA0003301935980000091
Figure BDA0003301935980000092
wherein the shift ratio D1 and the transmission power range are
Figure BDA0003301935980000093
For mode 3, because the current stress is uncertain in an analytical expression, it is difficult to directly mathematically find the current stress optimized phase shift ratio combination in the mode; however, after the combination of the transmission power and the phase shift ratio is determined, it is further possible to determine at which switching time the current stress is specifically located; further, as can be seen from equation (17), the current stress optimal solution for mode 2 is at the boundary of the domain of mode 2 and mode 3, so the optimal solution for mode 3 is the same as the optimal solution for mode 2;
according to the analysis, the current stress curve of the TPS controlled in the whole power range along with the change of k and p can be obtained, and the current stress curves of single-phase-shift (SPS) and double-phase-shift (DPS) control are provided at the same time, as shown in FIG. 5;
as can be seen from fig. 5, the TPS control has the least current stress over the entire operating range, except that k is 1, enabling the DAB converter to achieve the highest efficiency over the full power range;
generally, the transformer turn ratio of the DAB converter is fixed, and when the input or output voltage changes, that is, the voltage turn ratio is not matched, it cannot be guaranteed that each switching tube realizes zero-voltage-switching (ZVS); because each switch tube of the DAB converter is reversely connected with a diode in parallel, ZVS of the switch tube is realized in a mode that the voltage of the diode clamping switch tube which is reversely connected in parallel is zero; therefore, the ZVS range of the DAB converter can be derived from the inductor current polarity at different times, as shown in the following table:
Figure BDA0003301935980000101
the soft switching ranges for the three modes obtained from the above analysis are shown below
Figure BDA0003301935980000102
Figure BDA0003301935980000103
Figure BDA0003301935980000104
When D2 is 0.5, combining equations (3), (20) to (22) with the phase shift ratio relationship of each mode, it can be obtained that the ZVS power constraint boundary in each mode is as shown in fig. 6, and all switching tubes of the DAB converter can realize ZVS within the ZVS power constraint range;
substituting the combination of the phase shift ratio extremum obtained by the mode 1 into the ZVS range of the mode 1 to obtain a formula (23), wherein the ZVS power constraint range is just the same as the power range satisfied by the current stress extremum, namely the switching tube can realize ZVS within the whole working range of the mode 1;
Figure BDA0003301935980000105
substituting the equation (20) into the ZVS range can obtain an equation (24), and since the value of one of the inequalities is equal to zero, that is, the inequality threshold is established, all the switch tube thresholds satisfy ZVS in the working ranges of mode 2 and mode 3;
Figure BDA0003301935980000111
in summary, in mode 1, all the switching tubes are in the ZVS state in the working range; all switching tube critical values under mode 2 and mode 3 meet ZVS;
compared with SPS and DPS control, optimization under three modes of TPS control not only realizes minimum current stress in a full power range, but also ensures all switching tubes ZVS, and effectively reduces conduction loss and switching loss of the converter;
the optimized phase-shift ratio combination obtained by the research ensures that the DAB converter realizes the minimum current stress in the full-power range and all the switching tubes ZVS;
however, the non-power control mode downward shift ratio is directly output by proportional-integral (PI) control, and the dynamic performance of the downward shift ratio cannot meet the requirements of actual engineering; in order to improve the output dynamic performance, the invention provides a multi-objective unified optimal control (MUOC) strategy based on TPS control based on the idea of virtual direct power control, and simultaneously optimizes the efficiency and dynamic performance of the DAB converter;
constructing a virtual power component as follows
Figure BDA0003301935980000112
In the formula: vv is defined as a virtual voltage component, which is an output value of the PI controller; v2 is the desired output voltage; v2 and i2 are the actual sampled output voltage and output current, respectively;
by constructing the virtual power component, the power deviation caused by the factors such as the voltage drop of the switch tube, the power loss, the internal parameters of the converter and the like can be compensated; the calculation process does not relate to the internal parameters (inductance L, switching frequency fs, transformer turn ratio n and the like) of the system, the parameter sensitivity of the system is reduced, and the compatibility and the portability of a control strategy are improved; in addition, since the optimal solutions for mode 2 and mode 3 are the same, only mode 2 may be studied; the transmission power p0 of the reduced parameter may be further expressed as
Figure BDA0003301935980000121
Combining equations (14), (17) and (25), (26), we can obtain the phase shift ratio expressions of the MUOC strategy as follows:
Figure BDA0003301935980000122
Figure BDA0003301935980000123
in summary, in the MUOC strategy, the system needs to sample the input voltage V1, the output voltage V2, and the output current i 2; obtaining a virtual voltage component Vv through an output voltage outer ring PI, and compensating power deviation; and judging the working mode of the DAB converter by calculating the values of k and p. Then, based on the relation between the optimized phase shift ratio combination and the virtual power component p, the phase shift ratio expressions of the MUOC strategy are obtained, namely the expressions (27) and (28), and finally the switching tube is driven to be switched on and off by the phase shift ratio.
While one embodiment of the present invention has been described in detail, the description is only a preferred embodiment of the present invention and should not be taken as limiting the scope of the invention. All equivalent changes and modifications made within the scope of the present invention shall fall within the scope of the present invention.

Claims (7)

1. A DAB converter multi-target unified control method based on triple phase shift control is characterized by comprising the following steps:
firstly, establishing an analytic model of a triple phase-shift control optimal mode;
secondly, minimizing current stress under different working modes based on a cost function optimization equation, deducing soft switching power constraint ranges of all switching tubes, and ensuring that all switching tubes realize zero-voltage switching;
and thirdly, constructing a virtual power component in the efficiency optimization phase-shifting ratio combination, obtaining a phase-shifting ratio expression under the multi-target unified control method based on the relation between the efficiency optimization phase-shifting ratio combination and the virtual power component, and improving the response speed of the output power under the condition of input voltage or load sudden change through power control.
2. A DAB converter multi-target unified control method based on triple phase shift control as claimed in claim 1, characterized in that the transmission power and current stress in the TPS control in the first step under three modes are:
Figure FDA0003301935970000011
Figure FDA0003301935970000012
wherein p is transmission power, G is current stress, D1 and D3 are phase shift ratios in an H1 full bridge and an H2 full bridge, respectively, and are referred to as an internal shift ratio;
d2 is the phase shift ratio between the H1 full bridge and the H2 full bridge, which is called the external phase shift ratio;
the value range of the shift ratio in the mode 1 is more than or equal to 0 and less than or equal to D1≤D2≤1,D1≤D3≤1；
The value range of the shift ratio in the mode 2 is more than or equal to 0 and less than or equal to D2≤D1≤1,D1≤D3≤1；
The value range of the shift ratio in the mode 3 is more than or equal to 0 and less than or equal to D2≤D1≤1,0≤D3≤D1。
3. A DAB converter multi-objective unified control method based on triple phase shift control as recited in claim 2, wherein the cost function optimization equation is:
λ(1,j)＝λ(2,j)＝λ(3,j)
where λ is a cost function defined as:
Figure FDA0003301935970000021
wherein: i represents a control variable, i.e. Di represents a different phase shift ratio; j represents the working mode, and Gj and Pj represent the current stress and the transmission power in different modes; i and j each take the values 1, 2 and 3.
4. A DAB converter multi-target unified control method based on triple phase shift control as recited in claim 3, wherein the minimized current stress under different operation modes is:
mode 1 has a minimum current stress of
Figure FDA0003301935970000022
mode 2 has a minimum current stress of
Figure FDA0003301935970000023
The minimum current stress optimal solution for mode 3 is the same as for mode 2.
5. A DAB converter multi-target unified control method based on triple phase shift control as recited in claim 4, wherein the soft switching power constraint ranges of all the switching tubes under the three modes are as follows:
in the mode 1, the switching tube can be realized in the working range of the whole mode 1;
all switching tube thresholds in the working ranges of mode 2 and mode 3 satisfy ZVS.
6. A DAB converter multi-target unified control method based on triple phase shift control as recited in claim 5, wherein the virtual power component in the third step is:
Figure FDA0003301935970000024
in the formula: vv is defined as a virtual voltage component, which is an output value of the PI controller; v2 is the desired output voltage; v2 and i2 are the actual sampled output voltage and output current, respectively.
7. A DAB converter multi-target unified control method based on triple phase shift control as recited in claim 5, wherein the phase shift ratio expression is:
Figure FDA0003301935970000031
CN202111192878.6A 2021-10-13 2021-10-13 DAB converter multi-target unified control method based on triple phase-shift control Withdrawn CN113904560A (en)

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN114430234A (en) * 2022-01-18 2022-05-03 合肥工业大学 Soft switch of DAB converter and current stress optimization method
CN118473227A (en) * 2024-07-10 2024-08-09 湖南大学 Full-power in-range optimization control method for double-active-bridge converter

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
JINHUI ZENG: "Multi-Objective Unified Optimal Control Strategy for DAB Converters with Triple-Phase-Shift Control", ENERGIES, pages 1 - 10 *

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN114430234A (en) * 2022-01-18 2022-05-03 合肥工业大学 Soft switch of DAB converter and current stress optimization method
CN114430234B (en) * 2022-01-18 2024-03-01 合肥工业大学 Soft switch and current stress optimization method of DAB converter
CN118473227A (en) * 2024-07-10 2024-08-09 湖南大学 Full-power in-range optimization control method for double-active-bridge converter

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Application publication date: 20220107