CN112615549B - Novel universal four-phase shift modulation method for improving dynamic performance of double active bridges - Google Patents
Novel universal four-phase shift modulation method for improving dynamic performance of double active bridges Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33584—Bidirectional converters
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- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention provides a novel universal four-phase-shift modulation method for improving the dynamic performance of a double-active bridge, all carrier signals are kept synchronous, and the universal four-phase-shift modulation method adjusts corresponding phase shift angles by changing the parameters of a comparison register in each carrier. The control method provided by the invention is based on the traditional phase-shifting control method, only needs to measure input and output voltages, and does not need to add an auxiliary circuit. Compared with other control methods, the method provided by the invention has the advantages that the dynamic response is instantly finished, the transition process is not needed, the detection of the inductive current is also not needed, and the whole control process is independent of the inductance value. The method provided by the invention reduces the cost and the calculation complexity, realizes the quick dynamic response of the circuit and eliminates the direct current bias of the inductive current in the response process, and meanwhile, the method provided by the invention can be suitable for all application scenes of hard switches, soft switches, unidirectional power transmission, bidirectional power transmission and the like, and is also suitable for all control methods of single phase-shift modulation, three phase-shift modulation and the like.
Description
Technical Field
The invention relates to a novel universal four-phase-shift modulation strategy for improving dynamic performance of a double-active-bridge, relates to a double-active-bridge direct-current converter, and belongs to the technical field of power electronics.
Background
With the continuous development of power electronic technology and the diversification of application scenes, more and more application scenes need to realize the bidirectional transmission of electric energy. Bidirectional isolated DC/DC converters are increasingly used. The dual active bridge circuit is widely used due to its characteristics of simple control, easy realization of soft switching, high efficiency, etc. FIG. 1 is a circuit topology of a conventional dual active bridge, in which primary and secondary sides of the circuit topology are full-bridge structures composed of four MOSFETs, each full-bridge structure can be divided into two bridge arms, and there are four bridge arms L1-L4Each bridge arm is composed of an upper pipe and a lower pipe driven by complementary signals. The topology is widely used in medium and high power application scenarios by using a transformer connection and utilizing an inductor for bidirectional power transmission.
In some application scenarios, the magnitude and direction of the transmission power often change, and the conventional phase shift modulation strategy mainly matches the required load change by adjusting the phase shift angle between different bridge arms. However, this conventional method may cause transient bias current of the inductor due to sudden change of duty ratio, accompanied by sudden change of phase shift angle. This results in slow dynamic response speed, increased current stress, and increased losses. Meanwhile, the bias current may also cause saturation of the inductor, which may result in serious consequences such as loss of converter function or circuit damage.
The chinese patent with application number CN201410678003.0, entitled "transient phase shift control method for dual active full bridge dc converter" proposes a method for eliminating bias current for single phase shift control, but cannot realize transient dc bias suppression capability in multi-phase shift modulation strategy.
The invention provides a method for eliminating bias current for multi-phase-shift control, which is provided by the Chinese patent with the application number of CN202010365209.3 and the term of general phase-shift control method for transient direct current bias of a double-active-bridge direct current converter, but the control process is more complex, and the response speed is influenced by the transient transition process.
In summary, during the process of dynamic change of the dual active bridge load based on the conventional single phase shift modulation strategy, the dc bias of the inductor current is easily generated, which may seriously affect the dynamic response and reliability of the converter. Existing solutions have certain limitations. Therefore, it is of great practical significance to use a simpler and more versatile scheme to improve the dynamic performance of the system.
Disclosure of Invention
The purpose of the invention is: a simpler and more versatile scheme is used to improve the dynamic performance of the dual active bridge system.
In order to achieve the above object, the technical solution of the present invention is to provide a novel universal four-phase shift modulation method for improving dynamic performance of a dual active bridge, wherein a primary side and a secondary side of a circuit topology of the dual active bridge are respectively a full-bridge structure composed of four switching tubes, and the full-bridge structure of the primary side is divided into a bridge arm L1And bridge arm L2The secondary side full bridge structure is divided into bridge arms L3And bridge arm L4Each bridge arm consists of an upper switch tube and a lower switch tube driven by complementary signals, a primary side full-bridge structure and a secondary side full-bridge structure are connected through a transformer, bidirectional power transmission is carried out by using an inductor, and driving signals of eight switch tubes are used for realizing bidirectional power transmission when the bridge arms run in a steady stateThe four-phase-shift modulation method is characterized in that all carrier signals are kept synchronous, and the general four-phase-shift modulation method adjusts corresponding phase shift angles by changing parameters of a comparison register in each carrier, and specifically comprises the following steps:
step 1: according to the required transmission power, input voltage V1An output voltage V2And calculating the phase shift angle D required by the modulation mode1、D2、D3Wherein: the modulation modes comprise single phase shift modulation, double phase shift modulation, expansion phase shift modulation and triple phase shift modulation; d1TsIs the phase shift angle of the primary side, TsFor counting cycles, the phase-shifting angle D of the primary side is adjusted by changing the distance between the comparison register CMP1 and the comparison register CMP31Ts；D3TsFor the phase shift angle of the secondary side, the phase shift angle D of the secondary side is adjusted by changing the distance between the comparison register CMP5 and the comparison register CMP73Ts；D2TsFor the phase shift angle between the primary side and the secondary side, the phase shift angle D between the primary side and the secondary side is adjusted by changing the distance between the comparison register CMP1 and the comparison register CMP52Ts；
Step 2: according to the required phase shift angle and the input voltage V1An output voltage V2Judging the working state of the circuit to further calculate an alpha value corresponding to the zero-crossing moment of the inductive current, wherein alpha is a control variable based on a carrier wave, and alpha TsIs a bridge arm L1The distance between the falling edge of the upper switching tube driving signal and the end moment of the controller carrier cycle counting is the distance between the comparison register CMP2 and the end moment of the controller carrier cycle counting, and is regarded as a bridge arm L1Phase shift angle of the drive signal relative to the carrier;
and step 3: determining the values of a comparison register CMP1 and a comparison register CMP2 of the 1 st carrier according to the calculated alpha value, and updating the comparison register CMP1 and the comparison register CMP 2;
and 4, step 4: according to the calculated phase shift angle D1、D2、D3And the value of the comparison register of the 1 st carrier determines the values of the comparison registers of the other carriers, i.e., the values of the comparison registers CMP3 through CMP8, and updates the comparison registers CMP3 through CMP 8.
Preferably, in step 1, if the modulation mode is single phase shift modulation, then:
D1＝D3＝0，D2controlling the size and direction of the transmission power of the circuit;
in step 2, the α value is calculated by the following formula:
in the above formula: k represents the transmission voltage ratio, k is nV2/V1N represents a transformation ratio of the transformer;
the state I represents that the forward direction of the double active bridges does not realize zero voltage switching-on; the state two represents that the double active bridges realize zero voltage switching-on in the forward direction; the third state shows that the double active bridges reversely do not realize zero voltage switching-on; and the state four represents that the double active bridges reversely realize zero voltage switching-on.
Preferably, whether the double active bridges can realize zero voltage turn-on and phase shift angle D2The method comprises the following steps:
in the above formula, non-ZVS indicates that the dual active bridge does not achieve zero voltage turn-on, and ZVS indicates that the dual active bridge achieves zero voltage turn-on.
Preferably, in step 1, if the modulation method is triple phase shift modulation, then:
phase shift angle D1、D2、D3Controlling the size and direction of the transmission power of the circuit;
in step 2, the α value is calculated by the following formula:
in the above formula: k represents the transmission voltage ratio, k is nV2/V1N represents a transformation ratio of the transformer;
in buck mode forward power transmission, the optimal phase shift angles with different power magnitudes are divided into a mode one and a mode two, wherein the mode one represents a light load state, and the mode two represents a heavy load state.
Compared with the prior art, the invention has the following advantages:
the control method provided by the invention is based on the traditional phase-shifting control method, only needs to measure input and output voltages, and does not need to add an auxiliary circuit. Compared with other control methods, the method provided by the invention has the advantages that the dynamic response is instantly finished, the transition process is not needed, the detection of the inductive current is also not needed, and the whole control process is independent of the inductance value. The method provided by the invention reduces the cost and the calculation complexity, realizes the quick dynamic response of the circuit and eliminates the direct current bias of the inductive current in the response process, and meanwhile, the method provided by the invention can be suitable for all application scenes of hard switches, soft switches, unidirectional power transmission, bidirectional power transmission and the like, and is also suitable for all control methods of single phase-shift modulation, three phase-shift modulation and the like.
Drawings
FIG. 1 is a block diagram of a dual active bridge circuit topology and control implementation;
FIG. 2 is a schematic diagram of the mechanism of generation of square waves;
FIG. 3 shows the key waveforms of the proposed method under the single phase shift modulation strategy;
FIG. 4 shows the key waveforms of the proposed method under triple phase shift modulation strategy;
FIG. 5 is a schematic diagram of the calculation process of the present invention;
FIG. 6 is a switching process from a forward direction not implementing ZVS to a forward direction implementing ZVS and back to the forward direction not implementing ZVS under a single phase shift modulation strategy;
FIG. 7 is a process for bi-directional switching of power transmission directions for a single phase shift modulation down-converter;
FIG. 8 is a process of switching from TPS light load to TPS heavy load to SPS to TPS heavy load to TPS light load.
Detailed Description
The invention will be further illustrated with reference to the following specific examples. It should be understood that these examples are for illustrative purposes only and are not intended to limit the scope of the present invention. Further, it should be understood that various changes or modifications of the present invention may be made by those skilled in the art after reading the teaching of the present invention, and such equivalents may fall within the scope of the present invention as defined in the appended claims.
In the analysis of a dual active bridge, it is generally considered that Single Phase Shift (SPS), Double Phase Shift (DPS), or Extended Phase Shift (EPS), is a special form of Triple Phase Shift (TPS). Therefore, the proposed control method is analyzed only by taking single phase shift and triple phase shift as examples. In addition, due to the symmetrical structure of the double active bridges, the voltage reduction mode is only analyzed, and the voltage increase mode can be analyzed by using a similar method.
The novel universal four-phase shift modulation method for improving the dynamic performance of the double active bridges adopts the following technical means:
in the double-active-bridge converter, driving signals S1-S8 of eight switching tubes on the primary side and the secondary side are square waves with duty ratios of 50% in steady-state operation, and the generation mechanism of the square waves is that sawtooth-shaped carriers with cycle counting are generated in a controller through counting, as shown in FIG. 2, each carrier can generate a pair of complementary square waves required by one bridge arm. The carrier counting range 0-TBPRD determines the counting period TsAnd a switching frequency fs. TBPRD is the value of a timebase period register in the controller. Each carrier corresponds to two comparison registers (CMPA, CMPB) and keeps a distance of half a cycle to realize a 50% duty cycle, and a counter generates a rising or falling action of a driving signal when counting the value of the comparison registers, so as to be convenient for distinguishingThe two comparison registers for the nth carrier are denoted as CMP (2n-1) and CMP (2 n). Conventional approaches typically use a phase register (TBPHS) in each carrier of the controller to adjust the phase shift between the carriers. In the invention, all phase registers are not enabled, all carrier signals are kept synchronous, and the corresponding phase shifting angle is adjusted by changing the parameters of the comparison registers in each carrier. In the period shadow register mode, after the counter counts to the set maximum value, the counting is cleared and a synchronous signal is generated at the same time, so that the values of all registers are updated. The switching frequency is kept unchanged due to the proposed dual active bridge phase shift modulation method. Therefore, only the parameters of all the compare registers need to be updated.
In actual circuit control, the phase shift angle D of the primary side is adjusted by changing the distance between CMP1 and CMP31TsAdjusting the phase shift angle D of the secondary side by changing the distance between CMP5 and CMP73TsChanging the distance between CMP1 and CMP5 adjusts the phase shift angle D between the primary and secondary sides2Ts. In the invention, a control variable alpha, alpha T based on carrier wave is addedsIs a bridge arm L1The distance between the falling edge of the upper tube drive signal (CMP2) and the end of the controller carrier cycle count can be considered as the bridge arm L1The magnitude of alpha is adjusted by calculating the current zero-crossing time to change the value of CMP2, and thus the proposed method can be referred to as a quad-phase-shift (QPS) modulation strategy. As shown in fig. 5, the calculation process may be in the following order:
(1) calculating the phase shift angle according to the required transmission power, input/output voltage and modulation mode1、D2、D3。
(2) And judging the working state of the circuit according to the phase shift angle and the input and output voltage to further calculate the alpha value corresponding to the zero-crossing moment of the inductive current.
(3) The values of the comparison registers CMP1, CMP2 of the PWM1 are determined from the calculated α value, and the comparison registers CMP1, CMP2 are updated.
(4) According to the calculated D1、D2、D3Comparison register CMP of sum PWM11. The value of CMP2 determines the values of the compare registers CMP3-CMP8 for the other carriers and updates the compare registers CMP3-CMP 8.
FIG. 3 shows the key waveform of the proposed method under a single phase shift modulation strategy, D1＝D3＝0。D2The magnitude and direction of the power transmitted by the control circuit. The inductor current is made zero at the end of each carrier cycle by adjusting the variable a. Since whether the circuit can achieve zero voltage turn-on (hereinafter abbreviated as ZVS) condition is related to the moment when the inductor current crosses zero, it can be divided into four modes:
state one, forward direction does not implement ZVS,
state two, forward implementation of ZVS,
state three, reverse direction does not achieve ZVS,
state four, ZVS is achieved in reverse.
The corresponding variable α is calculated as follows:
in the above formula, k represents a transmission voltage ratio, and k is nV2/V1，V2Representing the output voltage, V1Representing the input voltage and n representing the transformer transformation ratio.
Whether the circuit can realize ZVS and phase shift angle D2The method comprises the following steps:
in the above formula, non-ZVS indicates that the dual active bridge does not achieve zero voltage turn-on, and ZVS indicates that the dual active bridge achieves zero voltage turn-on.
Thus only the input and output voltages need to be measured and the phase shift angle D calculated from the required transmission power2The corresponding alpha can be calculated. And alpha is calculated independently of circuit internal parameters such as inductance values and the like. As can be seen from fig. 3, the inductor current is zero at the beginning and at the end of each cycle. Therefore, the next one isAt the beginning of the cycle, after the values of the parameters of the registers are updated, the new inductor current of the cycle will enter a new steady state from zero, which also means that the whole dynamic response process is completed instantaneously. And simultaneously, the direct current bias of the current can be eliminated.
Phase angle D shift under triple phase shift modulation strategy1、D2、D3The magnitude and direction of the power transmitted by the control circuit. Taking buck mode forward power transmission as an example, the optimal phase shift angles of different power magnitudes can be divided into: mode one, light load state; the second mode, the heavy load state and the two modes. Fig. 4 shows the key waveforms of the proposed method under the Triple Phase Shift (TPS) modulation strategy, and the corresponding variable α calculation formula is as follows:
it can be seen that the control method proposed by the present invention is also zero at the end of each carrier period in the TPS modulation mode. If the register parameters are updated at the beginning of a new carrier cycle, the proposed method can achieve a good dynamic response process in both the light load state and the heavy load state.
Example specific circuit structure see fig. 1, wherein the input voltage is set to 300V, the output voltage is 200-280V, and the switching frequency is set to 100 kHz. The inductance value was 86 uH. The control logic is shown in figure 5. The sampling circuit detects the input and output voltage and calculates D according to the transmission power and the modulation mode1-D3And the variable alpha value, and then calculate that the comparison registers CMP1-CMP8 generate corresponding driving signals, so that the inductive current is zero at the end of each carrier cycle. When the required load changes, the circuit updates the required phase shift angle according to the required output power and the input and output voltage, and then calculates a new alpha value according to the new phase shift angle and the current input and output voltage. And each comparison register is updated when the next period starts, so that the circuit works in a new state immediately, and the aims of completing dynamic response instantly and eliminating the direct current bias of the inductive current are fulfilled. FIG. 6 is a diagram of forward non-ZVS implementation, forward ZVS implementation and return to positive under a single phase shift modulation strategyTo a process in which ZVS is not implemented. Fig. 7 shows a process of bidirectional switching of power transmission direction of the single phase shift modulation down converter, and fig. 8 shows a process of switching from TPS light load to TPS heavy load to SPS heavy load to TPS light load. The experimental results all verify the feasibility of the proposed method.
Claims (4)
1. A novel universal four-phase shift modulation method for improving dynamic performance of a double-active bridge circuit topology is characterized in that a primary side and a secondary side of the double-active bridge circuit topology are respectively of a full-bridge structure composed of four switching tubes, and the full-bridge structure of the primary side is divided into a bridge arm L1And bridge arm L2The secondary side full bridge structure is divided into bridge arms L3And bridge arm L4Each bridge arm is composed of an upper switch tube and a lower switch tube driven by complementary signals, a primary side full bridge structure and a secondary side full bridge structure are connected through a transformer, bidirectional power transmission is carried out by utilizing an inductor, the drive signals of the eight switch tubes are square waves with the duty ratio of 50% in steady-state operation, saw-tooth-shaped carriers with the cycle count generated by counting in a controller generate square waves, each carrier generates a pair of complementary square waves required by one bridge arm, each carrier corresponds to two comparison registers and keeps the distance of half cycle to realize the 50% duty ratio, when the counter counts the value of the comparison registers, the rising or falling action of the drive signals is generated, the two comparison registers of the nth carrier are marked as CMP (2n-1) and CMP (2n), the universal four-phase shift modulation method is characterized in that all carrier signals are kept synchronous, the corresponding phase shift angle is adjusted by changing the parameters of the comparison registers in each carrier, the method specifically comprises the following steps:
step 1: according to the required transmission power, input voltage V1An output voltage V2And calculating the phase shift angle D required by the modulation mode1、D2、D3Wherein: the modulation modes comprise single phase shift modulation, double phase shift modulation, expansion phase shift modulation and triple phase shift modulation; d1TsIs the phase shift angle of the primary side, TsFor counting cycles, the phase-shifting angle D of the primary side is adjusted by changing the distance between the comparison register CMP1 and the comparison register CMP31Ts；D3TsFor the phase shift angle of the secondary side, the phase shift angle D of the secondary side is adjusted by changing the distance between the comparison register CMP5 and the comparison register CMP73Ts；D2TsFor the phase shift angle between the primary side and the secondary side, the phase shift angle D between the primary side and the secondary side is adjusted by changing the distance between the comparison register CMP1 and the comparison register CMP52Ts；
Step 2: according to the required phase shift angle and the input voltage V1An output voltage V2Judging the working state of the circuit to further calculate an alpha value corresponding to the zero-crossing moment of the inductive current, wherein alpha is a control variable based on a carrier wave, and alpha TsIs a bridge arm L1The distance between the falling edge of the upper switching tube driving signal and the end moment of the controller carrier cycle counting is the distance between the comparison register CMP2 and the end moment of the controller carrier cycle counting, and is regarded as a bridge arm L1Phase shift angle of the drive signal relative to the carrier;
and step 3: determining the values of a comparison register CMP1 and a comparison register CMP2 of the 1 st carrier according to the calculated alpha value, and updating the comparison register CMP1 and the comparison register CMP 2;
and 4, step 4: according to the calculated phase shift angle D1、D2、D3And the value of the comparison register of the 1 st carrier determines the values of the comparison registers of the other carriers, i.e., the values of the comparison registers CMP3 through CMP8, and updates the comparison registers CMP3 through CMP 8.
2. The novel universal four-phase shift modulation method for improving the dynamic performance of the dual-active bridge as claimed in claim 1, wherein in step 1, if the modulation mode is single-phase shift modulation, then:
D1＝D3＝0，D2controlling the size and direction of the transmission power of the circuit;
in step 2, the α value is calculated by the following formula:
in the above formula: k represents the transmission voltage ratio, k is nV2/V1N represents a transformation ratio of the transformer;
the state I represents that the forward direction of the double active bridges does not realize zero voltage switching-on; the state two represents that the double active bridges realize zero voltage switching-on in the forward direction; the third state shows that the double active bridges reversely do not realize zero voltage switching-on; and the state four represents that the double active bridges reversely realize zero voltage switching-on.
3. The method as claimed in claim 2, wherein the dual active bridge can realize zero voltage turn-on and phase shift angle D2The method comprises the following steps:
in the above formula, non-ZVS indicates that the dual active bridge does not achieve zero voltage turn-on, and ZVS indicates that the dual active bridge achieves zero voltage turn-on.
4. The novel universal four-phase shift modulation method for improving the dynamic performance of the dual active bridge as claimed in claim 1, wherein in step 1, if the modulation mode is triple phase shift modulation, then:
phase shift angle D1、D2、D3Controlling the size and direction of the transmission power of the circuit;
in step 2, the α value is calculated by the following formula:
in the above formula: k represents the transmission voltage ratio, k is nV2/V1N represents a transformation ratio of the transformer;
in buck mode forward power transmission, the optimal phase shift angles with different power magnitudes are divided into a mode one and a mode two, wherein the mode one represents a light load state, and the mode two represents a heavy load state.
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| CN104852601A (en) * | 2015-05-27 | 2015-08-19 | 广西大学 | Cascaded multi-level power electronic transformer based on DSP (Digital Signal Processor)/FPGA (Field Programmable Gate Array) cooperative control |
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| CN110401350A (en) * | 2019-07-01 | 2019-11-01 | 中南大学 | The phase-shifting control method of the full-load range ZVS of double active full-bridge bidirectional DC-DC converters |
| CN111628655A (en) * | 2020-04-30 | 2020-09-04 | 合肥博鳌电气科技有限公司 | Universal phase-shifting control method for transient DC offset of dual-active-bridge DC converter |
| CN111525811A (en) * | 2020-05-07 | 2020-08-11 | 爱士惟新能源技术(江苏)有限公司 | Magnetic balance control method of double-active full-bridge bidirectional DC/DC converter |
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