CN113900071A - Output power detection circuit, adjustment method, detection method and phased array radar - Google Patents
Output power detection circuit, adjustment method, detection method and phased array radar Download PDFInfo
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- CN113900071A CN113900071A CN202111479486.8A CN202111479486A CN113900071A CN 113900071 A CN113900071 A CN 113900071A CN 202111479486 A CN202111479486 A CN 202111479486A CN 113900071 A CN113900071 A CN 113900071A
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
- G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
- G01S7/40—Means for monitoring or calibrating
- G01S7/4004—Means for monitoring or calibrating of parts of a radar system
- G01S7/4021—Means for monitoring or calibrating of parts of a radar system of receivers
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
- G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
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- G—PHYSICS
- G01—MEASURING; TESTING
- G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
- G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
- G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
- G01S2013/0236—Special technical features
- G01S2013/0245—Radar with phased array antenna
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Abstract
The invention discloses an output power detection circuit, which comprises a power output circuit, a power detection circuit and a control circuit, wherein the power output circuit is connected with the power detection circuit; the power output circuit comprises a first intermediate frequency filter, a first amplifier, a first attenuator, a second amplifier, a second attenuator, a first mixer, a first filter, a third amplifier, a first coupler, a third attenuator, a fourth attenuator, a second filter and a second coupler; the power detection circuit comprises a first detection circuit and a second detection circuit; the first detection circuit comprises a fixed attenuator, the input end of the fixed attenuator is connected with the coupling end of the second coupler, and the output end of the fixed attenuator is connected with the first AD detection module; the second detection circuit comprises a fifth attenuator, a fourth amplifier, a fifth amplifier, a second mixer, a third filter, a second intermediate frequency filter, a first single-pole double-throw switch and a second single-pole double-throw switch; the circuit can realize power output in a range of more than 95dB and can carry out detection in real time.
Description
Technical Field
The invention belongs to the technical field of power detection, and particularly relates to a wide-bandwidth output power detection circuit, an adjustment method, a detection method and a phased array radar.
Background
According to the requirement of an X-waveband double-polarization one-dimensional phased array weather radar system functional specification requirement book, the X-waveband phased array radar has the following requirements: 1. the dynamic range reaches more than 95 dB; 2. the working frequency band is 9.3 GHz-9.5 GHz.
In order to meet the above requirements, a dynamic range of more than 95dB needs to be realized within 200MHz, and the dynamic range can be accurately measured, and there are two specific implementation manners for accurate measurement:
one is manual testing, namely off-line testing, which has high requirements on testing sites and instruments and equipment, and is inconvenient to test after the radar is erected. The other is online testing, which is usually implemented by circuit design, and the circuit needs to satisfy three conditions:
firstly, any frequency in the range of 9.3 GHz-9.5 GHz is supported to work: the X-band phased array radar needs to support 200MHz working frequency.
Secondly, the output power can reach a dynamic range above 95 dB: if the phased array radar reception dynamic range is to be tested completely, it is necessary to provide at least 95dB more input signal.
Thirdly, the output power can be accurately detected in real time, and the detection error is as small as possible, such as +/-0.35 dB: if the receiving dynamic range of the phased array radar is to be completely tested, at least more than 95dB of input signals are required to be provided for a receiver, the sizes of the input signals correspond to those of output signals of the receiver one by one, and therefore the size of power provided for the input signals of the receiver must be detected in real time.
However, the following difficulties exist in the implementation of such circuits:
(1) for an active circuit, the gain fluctuates within a bandwidth of 200MHz, resulting in the same input power and the corresponding output power deviations for different frequencies.
(2) The power detection range of the existing intermediate frequency or radio frequency AD detection chip is about 70dB (about-60 dBm to +10 dBm), and the detection range of a linear area is usually only about 40dB, so that the requirement of the detection range of the input signal of the phased array radar is far less than that.
(3) The conventional power detection usually detects only part of the output power, and other output powers which cannot be detected are speculated through control logic, so that detection errors are caused by the self errors of a control system, and accurate detection in a 200MHz frequency band range is difficult to guarantee.
Disclosure of Invention
The invention aims to provide an output power detection circuit, an adjustment method, a detection method and a phased array radar, and aims to solve the problems that the linear detection range of an AD detection chip cannot meet the test requirement of the wide dynamic range of the phased array radar, and the output power cannot be accurately detected in real time within the frequency band range of 200MHz and the detection precision requirement is met.
The invention solves the technical problems through the following technical scheme: an output power detection circuit comprises a power output circuit, a power detection circuit and a control circuit; the power output circuit comprises a first intermediate frequency filter, a first amplifier, a first attenuator, a second amplifier, a second attenuator, a first mixer, a first filter, a third amplifier, a first coupler, a third attenuator, a fourth attenuator, a second filter and a second coupler which are connected in sequence;
the power detection circuit comprises a first detection circuit and a second detection circuit; the first detection circuit comprises a fixed attenuator, the input end of the fixed attenuator is connected with the coupling end of the second coupler, and the output end of the fixed attenuator is connected with the first AD detection module; the second detection circuit comprises a fifth attenuator, a fourth amplifier, a fifth amplifier, a second mixer, a third filter, a second intermediate frequency filter, a first single-pole double-throw switch and a second single-pole double-throw switch; the moving contact of the first single-pole double-throw switch is connected with the coupling end of the first coupler, the two fixed contacts of the first single-pole double-throw switch are respectively connected with the input ends of the fifth attenuator and the fourth amplifier, and the output ends of the fifth attenuator and the fourth amplifier are respectively connected with the two fixed contacts of the second single-pole double-throw switch; the moving contact, the fifth amplifier, the second mixer, the third filter and the second intermediate frequency filter of the second single-pole double-throw switch are sequentially connected, and the output end of the second intermediate frequency filter is connected with the second AD detection module;
the first frequency mixer and the second frequency mixer are also externally connected with local oscillator signals; the first attenuator, the second attenuator, the third attenuator, the fourth attenuator, the first AD detection module and the second AD detection module are all connected with the control circuit.
Further, the first attenuator and the second attenuator are both 30dB adjustable attenuators; and the third attenuator and the fourth attenuator are both 1bit 20dB numerical control attenuators.
Further, the first filter is a band-pass filter; the second filter and the third filter are both low-pass filters.
The invention also provides an output power adjusting method, which is applied to the output power detection circuit and comprises the following steps:
the attenuation values of the first attenuator, the second attenuator, the third attenuator and the fourth attenuator are all adjusted to be 0, so that the output power detection circuit outputs the maximum power;
gradually increasing the attenuation values of the first attenuator and the second attenuator and/or adjusting the attenuation values of the third attenuator and the fourth attenuator to be 0 or the maximum attenuation value according to the set step length, so that the output power of the output power detection circuit is in the range of the maximum power to the minimum power;
and adjusting the attenuation values of the first attenuator, the second attenuator, the third attenuator and the fourth attenuator to be maximum attenuation values, so that the output power detection circuit outputs minimum power.
Further, the calculation formula of the output power is as follows:
Pout＝Pmax－Q1－Q2－Q3－Q4
wherein, Pout is the output power of the output power detection circuit, Pmax is the maximum power, and Q1, Q2, Q3 and Q4 are the attenuation values of the first attenuator, the second attenuator, the third attenuator and the fourth attenuator, respectively.
The invention also provides a detection method of output power, which is applied to the output power detection circuit and comprises the following steps:
step 1: before detection, measuring a power difference value delta between the input end of the first AD detection module and the output end of the output power detection circuit; measuring and calculating an attenuation value G between the first AD detection module and the second AD detection module when the moving contacts of the first single-pole double-throw switch and the second single-pole double-throw switch are at different positions and the third attenuator and the fourth attenuator have different attenuation values;
step 2: during detection, the positions of the movable contacts of the first single-pole double-throw switch and the second single-pole double-throw switch and the attenuation values of the third attenuator and the fourth attenuator are controlled and determined, and the detection value P2 of the second AD detection module is obtained in real time;
and step 3: and calculating the output power of the output power detection circuit according to the power difference value delta, an attenuation value G and a detection value P2, wherein the attenuation value G is an attenuation value corresponding to the positions of the movable contacts of the first single-pole double-throw switch and the second single-pole double-throw switch and the attenuation values of the third attenuator and the fourth attenuator in the step 2.
Further, the specific measurement steps of the power difference δ are as follows:
connecting a signal source with a frequency spectrograph through a sixth attenuator, setting the frequencies of the signal source and the frequency spectrograph as the output frequency of the output power detection circuit, and recording a power value P0 on the frequency spectrograph at the moment;
connecting the output end of the output power detection circuit with the input end of the sixth attenuator, setting the attenuation values of the first attenuator, the second attenuator, the third attenuator and the fourth attenuator to 0, and acquiring a detection value P' 1 of the first AD detection module and a power value P on the frequency spectrograph;
calculating a power difference value delta according to the power value P0, the detection value P' 1 and the power value P, wherein a specific calculation formula is as follows:
δ＝P＋∣P0∣－P’1。
further, when the first attenuator or the second attenuator is subjected to attenuation control and the attenuation value is less than 30dB, the movable contact of the first single-pole double-throw switch, the fifth attenuator and the movable contact of the second single-pole double-throw switch are sequentially connected;
when the attenuation control is carried out on the first attenuator and the second attenuator and the attenuation value is larger than 30dB, the moving contact of the first single-pole double-throw switch, the fourth amplifier and the moving contact of the second single-pole double-throw switch are sequentially connected.
Further, when the moving contact of the first single-pole double-throw switch, the fifth attenuator and the moving contact of the second single-pole double-throw switch are sequentially connected, and the attenuation values of the third attenuator and the fourth attenuator are 0, the detection values P1a and P2a of the first AD detection module and the second AD detection module are obtained, and the attenuation value G is equal to the difference between the detection values P2a and P1 a;
when the moving contact of the first single-pole double-throw switch, the fifth attenuator and the moving contact of the second single-pole double-throw switch are sequentially connected, and the attenuation values of the third attenuator and the fourth attenuator are maximum attenuation values, detection values P1b and P2b of the first AD detection module and the second AD detection module are obtained, and the attenuation value G is equal to the difference between the detection values P2b and P1 b;
when the moving contact of the first single-pole double-throw switch, the fourth amplifier and the moving contact of the second single-pole double-throw switch are sequentially connected and the attenuation values of the third attenuator and the fourth attenuator are 0, the detection values P1c and P2c of the first AD detection module and the second AD detection module are obtained, and the attenuation value G is equal to the difference between the detection values P2c and P1 c;
when the moving contact of the first single-pole double-throw switch, the fourth amplifier and the moving contact of the second single-pole double-throw switch are sequentially connected and the attenuation values of the third attenuator and the fourth attenuator are maximum attenuation values, detection values P1d and P2d of the first AD detection module and the second AD detection module are obtained, and the attenuation value G is equal to the difference between the detection values P2d and P1 d.
The invention also provides a phased array radar, which comprises a signal generating unit, an antenna coupling unit, a receiver and the output power detection circuit; the signal generating unit is connected with a first intermediate frequency filter of the output power detection circuit, and the receiver is connected with a second coupler of the output power detection circuit through the antenna coupling unit.
Advantageous effects
Compared with the prior art, the invention has the advantages that:
the output power detection circuit, the adjusting method, the detection method and the phased array radar can realize power output in a range of more than 95dB, ensure that the output power is just in the test input requirement of a receiver by adjusting the size of an input signal, and can carry out real-time detection; the circuit can be used in the range of 200MHz of the radar, and does not need to fit detection curves under different frequencies in advance, so that the workload is greatly reduced, and the measurement effect is ensured.
Drawings
In order to more clearly illustrate the technical solution of the present invention, the drawings needed to be used in the description of the embodiments are briefly introduced below, and it is obvious that the drawings in the following description are only one embodiment of the present invention, and it is obvious for those skilled in the art to obtain other drawings based on the drawings without creative efforts.
FIG. 1 is a schematic diagram of an output power detection circuit according to an embodiment of the present invention;
FIG. 2 is a simplified diagram of an output power detection circuit according to an embodiment of the present invention;
FIG. 3 is a power difference δ measurement connection diagram in an embodiment of the present invention;
FIG. 4 is a diagram of the output power detection circuit and spectrometer in accordance with an embodiment of the present invention;
figure 5 is a circuit diagram of two single pole double throw switches in different positions in an embodiment of the present invention.
Detailed Description
The technical solutions in the present invention are clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
The technical solution of the present application will be described in detail below with specific examples. The following several specific embodiments may be combined with each other, and details of the same or similar concepts or processes may not be repeated in some embodiments.
As shown in fig. 1, the output power detection circuit provided in this embodiment includes a power output circuit, a power detection circuit, and a control circuit; the power output circuit comprises a first intermediate frequency filter, a first amplifier, a first attenuator, a second amplifier, a second attenuator, a first mixer, a first filter, a third amplifier, a first coupler, a third attenuator, a fourth attenuator, a second filter and a second coupler which are connected in sequence.
The power detection circuit comprises a first detection circuit and a second detection circuit; the first detection circuit comprises a fixed attenuator, the input end of the fixed attenuator is connected with the coupling end of the second coupler, and the output end of the fixed attenuator is connected with the first AD detection module; the second detection circuit comprises a fifth attenuator, a fourth amplifier, a fifth amplifier, a second mixer, a third filter, a second intermediate frequency filter, a first single-pole double-throw switch and a second single-pole double-throw switch; a moving contact of the first single-pole double-throw switch is connected with a coupling end of the first coupler, two fixed contacts of the first single-pole double-throw switch are respectively connected with input ends of a fifth attenuator and a fourth amplifier, and output ends of the fifth attenuator and the fourth amplifier are respectively connected with two fixed contacts of the second single-pole double-throw switch; the moving contact, the fifth amplifier, the second mixer, the third filter and the second intermediate frequency filter of the second single-pole double-throw switch are sequentially connected, and the output end of the second intermediate frequency filter is connected with the second AD detection module.
The first frequency mixer and the second frequency mixer are also externally connected with local oscillator signals L0; the first attenuator, the second attenuator, the third attenuator, the fourth attenuator, the first AD detection module and the second AD detection module are all connected with the control circuit.
In this embodiment, the first attenuator and the second attenuator are both 30dB adjustable attenuators; the third attenuator and the fourth attenuator are both 1bit 20dB numerical control attenuators. The first filter is a band-pass filter; the second filter and the third filter are both low-pass filters. The degree of coupling of the first coupler is 20 dB.
The power output circuit is used for adjusting a 95dB signal range in a 200MHz bandwidth; the first detection circuit and the second detection circuit are used for detecting the power of the output signal.
The signal generating unit generates an intermediate frequency signal f0Obtaining the frequency f through amplification, frequency conversion and filtering1The output power adjusting range of the radio frequency signal is more than 95dB by adjusting 4 attenuators. The adjustment mode is as follows:
as shown in fig. 1, for example, when the input signal of the first if filter is-15 dBm, and the attenuation values of 2 30dB adjustable attenuators (i.e., the first attenuator and the second attenuator) and 2 20dB digitally controlled attenuators (i.e., the third attenuator and the fourth attenuator) are adjusted to 0 (i.e., not attenuated) by the control circuit, the output of the second coupler is about 18dBm, which is the maximum output of the power output circuit. The adjusting step length of the 2 adjustable attenuators with 30dB is 0.5dB, the adjustable step length can be adjusted to 31.5dB from 1.5dB (fixed loss when the attenuations are not performed), and the adjusting range is 30 dB; the 20dB digital control attenuator is a 1bit adjustable attenuator, and has only two states, namely a non-attenuation state (the attenuation value is 0) and a full-attenuation state (the attenuation value is 20 dB), and the first attenuator, the second attenuator, the third attenuator and the fourth attenuator are selected to be matched with a power detection circuit to carry out power detection. When the 2 adjustable attenuators with 30dB are set to be maximum attenuation 31.5dB and the attenuation values of the 2 numerical control attenuators with 20dB are set to be maximum attenuation 20dB (considering the fixed attenuation 1.5dB when the attenuation is not attenuated, the actual adjustable range is 18.5 dB), the output of the second coupler is-79 dBm (18 dBm-30 dB-30 dB-18.5 dB-18.5 dB = -79 dBm), and the minimum output of the power output circuit is obtained at this moment. The maximum output is 18dBm, the minimum output is-79 dBm, the dynamic range is 97dB, and the requirement that the dynamic range of the phased array weather radar reaches more than 95dB is met.
And the first detection circuit and the second detection circuit are adopted to carry out real-time and accurate detection on the power of the output signal of the power output circuit.
The first detection circuit does not perform segmented detection, the power detection range of the AD detection chip is 70dB at most, and the linear detection range is only about 40dB conventionally, so that the first detection circuit is not enough to detect the output power within the 95dB range, and if the purpose of detecting the output power within the 95dB range is achieved through the first detection circuit, two ways are provided:
first, segment detection is performed on a first detection circuit, and at least 3 segments are required, but there are the following problems:
(1) the circuit is complex, three sections of circuits need to be switched, each section of circuit corresponds to different gains, and active devices such as amplifiers need to be used; (2) active devices on the circuit can change along with temperature and frequency, the detection precision is influenced, the problem is avoided, the detection circuit needs to be tested according to different frequencies and temperatures, then data is stored, the later stage of work is convenient to search the table under different working modes, the mode is large in workload, and large test errors can exist.
Secondly, fuzzy detection, only detecting the output power in the linear region of the AD detection chip, and deriving the rest power through control logic, wherein the method has the following disadvantages: the accuracy of the control error of the circuit is strictly dependent, but there is a deviation in the actual control, and this error cannot be measured in real time and is superimposed on the detection error of the final AD detection chip, making it difficult to ensure the accuracy.
In order to accurately detect the output power of the output signal of the power output circuit in real time within the 200MHz frequency band range and meet the detection precision of +/-0.35 dB, the invention adds the second detection circuit, and finishes the detection of the output power of the output signal of the power output circuit through the cooperation of the first detection circuit and the second detection circuit.
The second detection circuit is positioned in front of the third attenuator and the fourth attenuator, and the adjustable power range in front of the first coupler is 60dB, so that the second detection circuit is divided into two paths, wherein one path is connected with the fifth attenuator, and the fifth attenuator ensures that a large signal coupled by the first coupler falls into the linear detection range of the AD detection chip; and the other path is connected with a fourth amplifier, amplifies the small signal coupled by the first coupler and falls into the linear detection range of the AD detection chip. The two paths of signals are switched through the two single-pole double-throw switches, the switching direction of the single-pole double-throw switches is judged according to the states of the 2 30dB adjustable attenuators, and when only 1 30dB adjustable attenuator is subjected to attenuation control and the attenuation value is smaller than 30dB, the single-pole double-throw switch of the second detection circuit is switched to the fifth attenuator; when the 2 adjustable attenuators with 30dB simultaneously carry out attenuation control and the attenuation value is more than 30dB, the single-pole double-throw switch of the second detection circuit is switched to the fourth amplifier.
The radio-frequency signal detected by the second detection circuit is subjected to down-conversion to obtain an intermediate-frequency signal, and the intermediate-frequency signal is sent to the second AD detection module. The reason why the present embodiment uses down-conversion for intermediate frequency detection, rather than directly using rf detection, is as follows:
(1) for the bandwidth of 200MHz, no matter how many radio frequency, the frequency detected after down-conversion is the same frequency, thus avoiding the problem that the detection curves of the intermediate frequency detector are different under different frequencies and improving the detection precision;
(2) the intermediate frequency detector is convenient to select the type, and the detection precision is improved.
The adjustable power range before the first coupler is 60dB, and 40dB needs to be adjusted through 2 numerical control attenuators with 20dB, and the power of the part is detected and confirmed through the first detection circuit and the second detection circuit. The 20dB digitally controlled attenuator has only two states: the attenuation values of the numerical control attenuator, the filter and the coupler are fixed and are not influenced by input signals under the same frequency and the same temperature according to actual measurement, so that under the same frequency and the instantaneity of test time, the attenuation value G between the first AD detection module and the second AD detection module is considered to be fixed under the same control state, the attenuation value G between the first AD detection module and the second AD detection module under different working states is measured before detection, the attenuation condition of 2 numerical control attenuators with 20dB and a single-pole double-throw switch of the second detection circuit are switched during measurement, and the G value is obtained by simultaneously testing the first detection circuit and the second detection circuit. Before detection, the intermediate frequency signal f needs to be reasonably set0The power of the AD detection chip is ensured to be in a linear state.
The present embodiment also providesA detection method of output power is applied to the output power detection circuit. For the sake of convenience in explaining the principle or process of the detection method, fig. 1 is simplified to fig. 2, and in fig. 2, Pin represents the intermediate frequency signal f0P1 represents the power of the first AD detector module input signal (i.e., the detected value of the first AD detector module), P2 represents the power of the second AD detector module input signal (i.e., the detected value of the second AD detector module), and Pout represents the power of the power detector circuit output signal (i.e., the output power of the power detector circuit).
The detection method comprises the following steps:
1. and measuring a power difference value delta between the input end of the first AD detection module and the output end of the output power detection circuit.
The circuit corresponding to the power difference value delta is a passive device and is single, so that the power difference value delta is stable at different temperatures (generally, the temperature is within 15-35 ℃) and 200MHz frequency, and can be obtained by testing through a frequency spectrograph, and the specific testing method comprises the following steps:
step 1.1: the signal source is connected with the spectrometer through the sixth attenuator, as shown in fig. 3, and the loss of cables among the spectrometer, the attenuator and the equipment is measured at normal temperature. The frequency of the signal source and the frequency meter is set as the output frequency of the output power detection circuit, the output power is set as 0dBm, and the power value P0 on the frequency spectrograph at the moment is recorded.
In this embodiment, the sixth attenuator is a 20dB adjustable attenuator.
Step 1.2: the output end of the output power detection circuit is connected with the input end of the sixth attenuator, as shown in fig. 4, the attenuation values of the first attenuator, the second attenuator, the third attenuator and the fourth attenuator are all set to 0, and at this time, the detection value P' 1 of the first AD detection module and the power value P on the spectrometer are obtained.
Step 1.3: calculating a power difference value delta according to the power value P0, the detection value P' 1 and the power value P, wherein the specific calculation formula is as follows:
δ＝P＋∣P0∣－P’1（1）
the power difference value delta is the relative difference value between Pout and the detection value P' 1 of the first AD detection module, under different input powers, the relative difference value cannot be changed, and is only influenced by the gain flatness of the first detection circuit and the coupler, the gain fluctuation of the power output circuit is very small and can be ignored within the range of 200MHz, in addition, the output power detection circuit is arranged in the phased array radar, the working environment is between 15 ℃ and 35 ℃, the detection error of the first AD detection module is very small (less than 0.1 dB), and therefore the power difference value delta is considered to be a fixed value within the range of 200 MHz.
2. And measuring and calculating an attenuation value G between the first AD detection module and the second AD detection module when the moving contacts of the first single-pole double-throw switch and the second single-pole double-throw switch are at different positions and the third attenuator and the fourth attenuator have different attenuation values.
As shown in fig. 5, when the if input is constant at the same frequency and temperature, the power detection circuit has four cases, and obtains the corresponding attenuation value G in different cases:
when the moving contact of the first single-pole double-throw switch, the fifth attenuator and the moving contact of the second single-pole double-throw switch are sequentially connected (namely, the circuit 1 in fig. 5), and the attenuation values of the third attenuator and the fourth attenuator are 0, the detection values P1a and P2a of the first AD detection module and the second AD detection module are obtained, and the attenuation value G is equal to the difference between the detection values P2a and P1a, namely, the difference between the detection values P2a and P1a
G＝P2a－P1a（2）
When the moving contact of the first single-pole double-throw switch, the fifth attenuator and the moving contact of the second single-pole double-throw switch are sequentially connected (namely, the circuit 1 in fig. 5), and the attenuation values of the third attenuator and the fourth attenuator are maximum attenuation values, detection values P1b and P2b of the first AD detection module and the second AD detection module are obtained, wherein the attenuation value G is equal to the difference between the detection values P2b and P1b, namely, the difference between the detection values P2b and P1b
G＝P2b－P1b（3）
When the moving contact of the first single-pole double-throw switch, the fourth amplifier and the moving contact of the second single-pole double-throw switch are sequentially connected (namely, the line 2 in fig. 5), and the attenuation values of the third attenuator and the fourth attenuator are 0, the detection values P1c and P2c of the first AD detection module and the second AD detection module are obtained, and the attenuation value G is equal to the difference between the detection values P2c and P1c, namely, the difference between the detection values P2c and P1c
G＝P2c－P1c（4）
When the moving contact of the first single-pole double-throw switch, the fourth amplifier and the moving contact of the second single-pole double-throw switch are sequentially connected (namely, the circuit 2 in fig. 5), and the attenuation values of the third attenuator and the fourth attenuator are maximum attenuation values, detection values P1d and P2d of the first AD detection module and the second AD detection module are obtained, wherein the attenuation value G is equal to the difference between the detection values P2d and P1d, namely, the difference between the detection values P2d and P1d
G＝P2d－P1d（5）
3. And during detection, the positions of the movable contacts of the first single-pole double-throw switch and the second single-pole double-throw switch and the attenuation values of the third attenuator and the fourth attenuator are controlled and determined, and the detection value P2 of the second AD detection module is obtained in real time.
In this embodiment, when the first attenuator or the second attenuator is subjected to attenuation control and the attenuation value is less than 30dB, the moving contact of the first single-pole double-throw switch, the fifth attenuator, and the moving contact of the second single-pole double-throw switch are sequentially connected (i.e., line 1 of fig. 5);
when the attenuation of the first attenuator and the second attenuator is controlled and the attenuation value is greater than 30dB, the moving contact of the first single-pole double-throw switch, the fourth amplifier and the moving contact of the second single-pole double-throw switch are connected in sequence (i.e. line 2 of fig. 5).
4. Calculating the output power of the output power detection circuit according to the power difference value delta, the attenuation value G and the detection value P2, wherein the specific calculation formula is as follows:
Pout＝P2－G＋δ（6）
in the equation (6), Pout is the output power of the output power detection circuit detected by the first detection circuit and the second detection circuit in real time, and G is a corresponding attenuation value, for example, if the detection value P2 of the second AD detection module is obtained in real time, the positions of the moving contacts of the first single-pole double-throw switch and the second single-pole double-throw switch correspond to the line 1, and the attenuation values of the third attenuator and the fourth attenuator are 0, the attenuation value G is uniquely determined by the equation (2); if the detection value P2 of the second AD detection module is obtained in real time, the positions of the moving contacts of the first single-pole double-throw switch and the second single-pole double-throw switch correspond to the line 2, and the attenuation values of the third attenuator and the fourth attenuator are maximum values, the attenuation value G is uniquely determined by the formula (5).
Under different control conditions, different G values are adopted to obtain corresponding Pout, and after the frequency is switched, only 4G values need to be measured on line before detection, so that the real-time detection of the Pout can be carried out.
The first attenuator, the second attenuator, the third attenuator and the fourth attenuator jointly ensure that the power output circuit is adjustable within a dynamic range of 95 dB; the linear detection range of the second AD detection module reaches 40dB, and the second detection circuit is divided into two paths, so that the 60dB power dynamic range can be ensured to be in the detection range of the second AD detection module, and the power of the adjusting ranges of the first attenuator and the second attenuator in front of the first coupler can be measured; the linear detection range of the first AD detection module is 40dB, and the first AD detection module is used for measuring the power of the third attenuator and the fourth attenuator under the condition of full attenuation and no attenuation under a large signal.
Generally, for a broadband AD detection chip, the detection difference fluctuation in a 200MHz bandwidth range is very small and can be ignored; the input frequency of the second AD detection module is a fixed intermediate frequency and is not influenced by the radio frequency, so that the problem of detection precision difference of different frequencies does not exist, and the problem of detection precision difference of output power under different frequencies is avoided; the output power detection circuit is positioned in the whole radar, the common environmental temperature range of the output power detection circuit is 15-35 ℃ through the whole heat dissipation design, the first AD detection module and the second AD detection module are relatively stable and have very small fluctuation in the temperature range, in addition, the second AD detection module adopts a detection chip with a temperature compensation function, the detection errors under different temperatures can be further reduced, and the detection errors of the first AD detection module and the second AD detection module, which are influenced by the temperature, are added up to about +/-0.1 dB, so the influence of the temperature on the detection precision of the output power is avoided; the output power detection circuit can meet the requirement of output power detection accuracy of +/-0.35 dB.
The input frequency of the second AD detection module is a fixed intermediate frequency and is not influenced by the radio frequency, so that the requirement of 200MHz is met; the first AD detection module meets the requirement of working in the range of 9.3GHz to 9.5GHz, and the fluctuation in 200MHz is small and can be ignored; the G value can be tested in real time, and after the frequency is adjusted, the G value can be tested in real time on line, so that the requirement of detecting any frequency of 200MHz can be met; in summary, the output power detection circuit can meet the power detection of any frequency of 200MHZ, and can realize a dynamic detection range of > 95dB, and the detection precision meets the requirement of ± 0.35 dB.
The invention mainly solves the problem that the single AD detection chip cannot be used for detecting the input signal of the phased array radar in the wide dynamic range because the linear detection range is too low, and cannot ensure the detection precision and meet the test requirement of the phased array radar in the dynamic range. The output power detection circuit provided by the invention can realize power output in a range of more than 95dB, and can ensure that the output power is just in the test input requirement of a receiver by adjusting the size of an input signal and can carry out real-time detection; the circuit can be used in the range of 200MHz of the radar, and does not need to fit detection curves under different frequencies in advance, so that the workload is greatly reduced, and the measurement effect is ensured.
The above disclosure is only for the specific embodiments of the present invention, but the scope of the present invention is not limited thereto, and any person skilled in the art can easily conceive of changes or modifications within the technical scope of the present invention, and shall be covered by the scope of the present invention.
Claims (10)
1. An output power detection circuit, characterized by: the power detection circuit comprises a power output circuit, a power detection circuit and a control circuit; the power output circuit comprises a first intermediate frequency filter, a first amplifier, a first attenuator, a second amplifier, a second attenuator, a first mixer, a first filter, a third amplifier, a first coupler, a third attenuator, a fourth attenuator, a second filter and a second coupler which are connected in sequence; the power output circuit is used for adjusting a signal range larger than 95dB in a 200MHz bandwidth;
the power detection circuit comprises a first detection circuit and a second detection circuit; the first detection circuit comprises a fixed attenuator, the input end of the fixed attenuator is connected with the coupling end of the second coupler, and the output end of the fixed attenuator is connected with the first AD detection module; the second detection circuit comprises a fifth attenuator, a fourth amplifier, a fifth amplifier, a second mixer, a third filter, a second intermediate frequency filter, a first single-pole double-throw switch and a second single-pole double-throw switch; the moving contact of the first single-pole double-throw switch is connected with the coupling end of the first coupler, the two fixed contacts of the first single-pole double-throw switch are respectively connected with the input ends of the fifth attenuator and the fourth amplifier, and the output ends of the fifth attenuator and the fourth amplifier are respectively connected with the two fixed contacts of the second single-pole double-throw switch; the moving contact, the fifth amplifier, the second mixer, the third filter and the second intermediate frequency filter of the second single-pole double-throw switch are sequentially connected, and the output end of the second intermediate frequency filter is connected with the second AD detection module;
the first frequency mixer and the second frequency mixer are also externally connected with local oscillator signals; the first attenuator, the second attenuator, the third attenuator, the fourth attenuator, the first AD detection module and the second AD detection module are all connected with the control circuit.
2. The output power detection circuit of claim 1, wherein: the first attenuator and the second attenuator are both 30dB adjustable attenuators; and the third attenuator and the fourth attenuator are both 1bit 20dB numerical control attenuators.
3. The output power detection circuit according to claim 1 or 2, wherein: the first filter is a band-pass filter; the second filter and the third filter are both low-pass filters.
4. An output power adjusting method applied to the output power detection circuit according to any one of claims 1 to 3, comprising:
the attenuation values of the first attenuator, the second attenuator, the third attenuator and the fourth attenuator are all adjusted to be 0, so that the output power detection circuit outputs the maximum power;
gradually increasing the attenuation values of the first attenuator and the second attenuator and/or adjusting the attenuation values of the third attenuator and the fourth attenuator to be 0 or the maximum attenuation value according to the set step length, so that the output power of the output power detection circuit is in the range of the maximum power to the minimum power;
and adjusting the attenuation values of the first attenuator, the second attenuator, the third attenuator and the fourth attenuator to be maximum attenuation values, so that the output power detection circuit outputs minimum power.
5. The method for adjusting output power according to claim 4, wherein the output power is calculated by the formula:
Pout＝Pmax－Q1－Q2－Q3－Q4
wherein, Pout is the output power of the output power detection circuit, Pmax is the maximum power, and Q1, Q2, Q3 and Q4 are the attenuation values of the first attenuator, the second attenuator, the third attenuator and the fourth attenuator, respectively.
6. An output power detection method applied to the output power detection circuit according to any one of claims 1 to 3, comprising:
step 1: before detection, measuring a power difference value delta between the input end of the first AD detection module and the output end of the output power detection circuit; measuring and calculating an attenuation value G between the first AD detection module and the second AD detection module when the moving contacts of the first single-pole double-throw switch and the second single-pole double-throw switch are at different positions and the third attenuator and the fourth attenuator have different attenuation values;
step 2: during detection, the positions of the movable contacts of the first single-pole double-throw switch and the second single-pole double-throw switch and the attenuation values of the third attenuator and the fourth attenuator are controlled and determined, and the detection value P2 of the second AD detection module is obtained in real time;
and step 3: and calculating the output power of the output power detection circuit according to the power difference value delta, an attenuation value G and a detection value P2, wherein the attenuation value G is an attenuation value corresponding to the positions of the movable contacts of the first single-pole double-throw switch and the second single-pole double-throw switch and the attenuation values of the third attenuator and the fourth attenuator in the step 2.
7. The method for detecting output power according to claim 6, wherein the specific steps of measuring the power difference δ are as follows:
connecting a signal source with a frequency spectrograph through a sixth attenuator, setting the frequencies of the signal source and the frequency spectrograph as the output frequency of the output power detection circuit, and recording a power value P0 on the frequency spectrograph at the moment;
connecting the output end of the output power detection circuit with the input end of the sixth attenuator, setting the attenuation values of the first attenuator, the second attenuator, the third attenuator and the fourth attenuator to 0, and acquiring a detection value P' 1 of the first AD detection module and a power value P on the frequency spectrograph;
calculating a power difference value delta according to the power value P0, the detection value P' 1 and the power value P, wherein a specific calculation formula is as follows:
δ＝P＋∣P0∣－P’1。
8. the method for detecting output power according to claim 6, wherein when the first attenuator or the second attenuator is controlled to be attenuated and the attenuation value is less than 30dB, the moving contact of the first single-pole double-throw switch, the fifth attenuator and the moving contact of the second single-pole double-throw switch are connected in sequence;
when the attenuation control is carried out on the first attenuator and the second attenuator and the attenuation value is larger than 30dB, the moving contact of the first single-pole double-throw switch, the fourth amplifier and the moving contact of the second single-pole double-throw switch are sequentially connected.
9. The method according to any one of claims 6 to 8, wherein when the moving contact of the first single-pole double-throw switch, the fifth attenuator, and the moving contact of the second single-pole double-throw switch are connected in sequence, and the attenuation values of the third attenuator and the fourth attenuator are 0, the detection values P1a, P2a of the first AD detection module and the second AD detection module are obtained, and the attenuation value G is equal to the difference between the detection values P2a and P1 a;
when the moving contact of the first single-pole double-throw switch, the fifth attenuator and the moving contact of the second single-pole double-throw switch are sequentially connected, and the attenuation values of the third attenuator and the fourth attenuator are maximum attenuation values, detection values P1b and P2b of the first AD detection module and the second AD detection module are obtained, and the attenuation value G is equal to the difference between the detection values P2b and P1 b;
when the moving contact of the first single-pole double-throw switch, the fourth amplifier and the moving contact of the second single-pole double-throw switch are sequentially connected and the attenuation values of the third attenuator and the fourth attenuator are 0, the detection values P1c and P2c of the first AD detection module and the second AD detection module are obtained, and the attenuation value G is equal to the difference between the detection values P2c and P1 c;
when the moving contact of the first single-pole double-throw switch, the fourth amplifier and the moving contact of the second single-pole double-throw switch are sequentially connected and the attenuation values of the third attenuator and the fourth attenuator are maximum attenuation values, detection values P1d and P2d of the first AD detection module and the second AD detection module are obtained, and the attenuation value G is equal to the difference between the detection values P2d and P1 d.
10. A phased array radar, characterized by: comprising a signal generating unit, an antenna coupling unit, a receiver and an output power detecting circuit according to any one of claims 1 to 3; the signal generating unit is connected with a first intermediate frequency filter of the output power detection circuit, and the receiver is connected with a second coupler of the output power detection circuit through the antenna coupling unit.
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN115372690A (en) * | 2022-08-19 | 2022-11-22 | 北京唯捷创芯精测科技有限责任公司 | Antenna tuner peak voltage measurement system |
| CN115913417A (en) * | 2023-01-07 | 2023-04-04 | 成都川美新技术股份有限公司 | Device and method for improving detection range and precision of radio frequency power detector |
| CN116256707A (en) * | 2023-05-15 | 2023-06-13 | 浙江宜通华盛科技有限公司 | Dual-polarization array radar and PIN tube SPDT switching device and method thereof |
Citations (24)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS56109054A (en) * | 1980-02-01 | 1981-08-29 | Matsushita Electric Ind Co Ltd | Standard signal generator |
| JP2001285211A (en) * | 2000-03-31 | 2001-10-12 | Matsushita Electric Ind Co Ltd | Amplifier measurement instrument |
| US20050270219A1 (en) * | 2004-06-08 | 2005-12-08 | Dwelly Wesley H | Short pulse/stepped frequency radar system |
| WO2008076424A1 (en) * | 2006-12-18 | 2008-06-26 | Aai Corporation | Method for implementing continuous radio frequency (rf) alignment in advanced electronic warfare (ew) signal stimulation systems |
| US20090322451A1 (en) * | 2008-06-30 | 2009-12-31 | Advantest Corporation | Signal Output Device, Signal Output Control Method, Program and Recording Medium |
| CN202204928U (en) * | 2011-08-12 | 2012-04-25 | 西安天伟电子系统工程有限公司 | Medium frequency and radio frequency universal target simulator of pulse compression radar |
| US20130113650A1 (en) * | 2011-05-04 | 2013-05-09 | Sabertek Inc. | Methods and apparatus for suppression of low-frequency noise and drift in wireless sensors or receivers |
| CN104270148A (en) * | 2014-08-21 | 2015-01-07 | 安徽白鹭电子科技有限公司 | Broadband digital fixed-amplitude multi-system radio frequency signal source module |
| CN204145470U (en) * | 2014-07-31 | 2015-02-04 | 南京恒电电子有限公司 | Receiver high frequency front-end module |
| CN104393857A (en) * | 2014-10-10 | 2015-03-04 | 中国电子科技集团公司第四十一研究所 | Large-dynamic-range automatic level control (ALC) system for microwave signal generator |
| CN104734656A (en) * | 2013-12-24 | 2015-06-24 | 苏州普源精电科技有限公司 | Radio frequency signal source with amplitude modulation and automatic level control functions |
| CN204855795U (en) * | 2015-07-14 | 2015-12-09 | 安徽四创电子股份有限公司 | Embedded air traffic control radar feeder standing wave real -time supervision device |
| CN105548975A (en) * | 2015-12-11 | 2016-05-04 | 中国科学院电子学研究所 | High-stability radio-frequency channel gain calibration apparatus and method |
| CN205880198U (en) * | 2016-06-28 | 2017-01-11 | 安徽四创电子股份有限公司 | S mode secondary radar transmitting system |
| CN107085204A (en) * | 2017-03-31 | 2017-08-22 | 西安电子工程研究所 | A kind of phased-array radar receives multichannel sensitivity test method |
| CN208432723U (en) * | 2018-07-28 | 2019-01-25 | 信阳市航信测控技术有限公司 | Radar power test device |
| US20190242973A1 (en) * | 2018-02-08 | 2019-08-08 | Nxp B.V. | Built-in self-test for a radar unit receiver and method therefor |
| CN210297644U (en) * | 2019-11-08 | 2020-04-10 | 成都菲斯洛克电子技术有限公司 | Receiving frequency converter |
| CN111337889A (en) * | 2020-02-07 | 2020-06-26 | 北京环境特性研究所 | Receiver power calibration device and calibration method thereof |
| CN211627811U (en) * | 2019-12-06 | 2020-10-02 | 湖南宜通华盛科技有限公司 | Test device for phased array radar full link directional diagram |
| CN112653459A (en) * | 2020-12-28 | 2021-04-13 | 成都美数科技有限公司 | Radio frequency signal source capable of being calibrated in real time |
| US20210181326A1 (en) * | 2019-12-12 | 2021-06-17 | Infineon Technologies Ag | Phase, phase noise, and slave mode measurement for millimeter wave integrated circuits on automatic test equipment |
| CN113281730A (en) * | 2020-12-05 | 2021-08-20 | 扬州宇安电子科技有限公司 | Ku wave band sea clutter measuring radar |
| CN113655456A (en) * | 2021-10-20 | 2021-11-16 | 南京雷电信息技术有限公司 | Radar active signal source |
-
2021
- 2021-12-07 CN CN202111479486.8A patent/CN113900071B/en active Active
Patent Citations (24)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS56109054A (en) * | 1980-02-01 | 1981-08-29 | Matsushita Electric Ind Co Ltd | Standard signal generator |
| JP2001285211A (en) * | 2000-03-31 | 2001-10-12 | Matsushita Electric Ind Co Ltd | Amplifier measurement instrument |
| US20050270219A1 (en) * | 2004-06-08 | 2005-12-08 | Dwelly Wesley H | Short pulse/stepped frequency radar system |
| WO2008076424A1 (en) * | 2006-12-18 | 2008-06-26 | Aai Corporation | Method for implementing continuous radio frequency (rf) alignment in advanced electronic warfare (ew) signal stimulation systems |
| US20090322451A1 (en) * | 2008-06-30 | 2009-12-31 | Advantest Corporation | Signal Output Device, Signal Output Control Method, Program and Recording Medium |
| US20130113650A1 (en) * | 2011-05-04 | 2013-05-09 | Sabertek Inc. | Methods and apparatus for suppression of low-frequency noise and drift in wireless sensors or receivers |
| CN202204928U (en) * | 2011-08-12 | 2012-04-25 | 西安天伟电子系统工程有限公司 | Medium frequency and radio frequency universal target simulator of pulse compression radar |
| CN104734656A (en) * | 2013-12-24 | 2015-06-24 | 苏州普源精电科技有限公司 | Radio frequency signal source with amplitude modulation and automatic level control functions |
| CN204145470U (en) * | 2014-07-31 | 2015-02-04 | 南京恒电电子有限公司 | Receiver high frequency front-end module |
| CN104270148A (en) * | 2014-08-21 | 2015-01-07 | 安徽白鹭电子科技有限公司 | Broadband digital fixed-amplitude multi-system radio frequency signal source module |
| CN104393857A (en) * | 2014-10-10 | 2015-03-04 | 中国电子科技集团公司第四十一研究所 | Large-dynamic-range automatic level control (ALC) system for microwave signal generator |
| CN204855795U (en) * | 2015-07-14 | 2015-12-09 | 安徽四创电子股份有限公司 | Embedded air traffic control radar feeder standing wave real -time supervision device |
| CN105548975A (en) * | 2015-12-11 | 2016-05-04 | 中国科学院电子学研究所 | High-stability radio-frequency channel gain calibration apparatus and method |
| CN205880198U (en) * | 2016-06-28 | 2017-01-11 | 安徽四创电子股份有限公司 | S mode secondary radar transmitting system |
| CN107085204A (en) * | 2017-03-31 | 2017-08-22 | 西安电子工程研究所 | A kind of phased-array radar receives multichannel sensitivity test method |
| US20190242973A1 (en) * | 2018-02-08 | 2019-08-08 | Nxp B.V. | Built-in self-test for a radar unit receiver and method therefor |
| CN208432723U (en) * | 2018-07-28 | 2019-01-25 | 信阳市航信测控技术有限公司 | Radar power test device |
| CN210297644U (en) * | 2019-11-08 | 2020-04-10 | 成都菲斯洛克电子技术有限公司 | Receiving frequency converter |
| CN211627811U (en) * | 2019-12-06 | 2020-10-02 | 湖南宜通华盛科技有限公司 | Test device for phased array radar full link directional diagram |
| US20210181326A1 (en) * | 2019-12-12 | 2021-06-17 | Infineon Technologies Ag | Phase, phase noise, and slave mode measurement for millimeter wave integrated circuits on automatic test equipment |
| CN111337889A (en) * | 2020-02-07 | 2020-06-26 | 北京环境特性研究所 | Receiver power calibration device and calibration method thereof |
| CN113281730A (en) * | 2020-12-05 | 2021-08-20 | 扬州宇安电子科技有限公司 | Ku wave band sea clutter measuring radar |
| CN112653459A (en) * | 2020-12-28 | 2021-04-13 | 成都美数科技有限公司 | Radio frequency signal source capable of being calibrated in real time |
| CN113655456A (en) * | 2021-10-20 | 2021-11-16 | 南京雷电信息技术有限公司 | Radar active signal source |
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN115372690A (en) * | 2022-08-19 | 2022-11-22 | 北京唯捷创芯精测科技有限责任公司 | Antenna tuner peak voltage measurement system |
| CN115372690B (en) * | 2022-08-19 | 2023-06-02 | 北京唯捷创芯精测科技有限责任公司 | Antenna tuner peak voltage measurement system |
| CN115913417A (en) * | 2023-01-07 | 2023-04-04 | 成都川美新技术股份有限公司 | Device and method for improving detection range and precision of radio frequency power detector |
| CN116256707A (en) * | 2023-05-15 | 2023-06-13 | 浙江宜通华盛科技有限公司 | Dual-polarization array radar and PIN tube SPDT switching device and method thereof |
| CN116256707B (en) * | 2023-05-15 | 2023-08-08 | 浙江宜通华盛科技有限公司 | Dual-polarization array radar and PIN tube SPDT switching device and method thereof |
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