CN113872437B - Pulse load power supply and voltage hysteresis control method thereof - Google Patents
Pulse load power supply and voltage hysteresis control method thereof Download PDFInfo
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- CN113872437B CN113872437B CN202110944732.6A CN202110944732A CN113872437B CN 113872437 B CN113872437 B CN 113872437B CN 202110944732 A CN202110944732 A CN 202110944732A CN 113872437 B CN113872437 B CN 113872437B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1582—Buck-boost converters
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The invention discloses a pulse load power supply and a voltage hysteresis control method thereof, wherein the voltage hysteresis control method comprises the following steps: collecting the load end voltage of the staggered parallel bidirectional buck/boost converter connected between the power supply and the load by using a sampling circuit; comparing the load end voltage of the staggered parallel bidirectional buck/boost converter with a preset boost low-voltage given value, a preset boost high-voltage given value, a preset buck low-voltage given value and a preset buck high-voltage given value, and generating corresponding square wave pulse control voltage according to a comparison result; and amplifying the square wave pulse control voltage and transmitting the square wave pulse control voltage to a switching tube in the staggered parallel type bidirectional buck/boost converter so as to control the on-off of the switching tube by using a voltage hysteresis control algorithm. The invention adopts a voltage hysteresis double-position control mode, and in the control mode, the action times of a switching tube in the system are obviously reduced, thereby reducing the switching loss of the system and improving the working efficiency of the system.
Description
Technical Field
The invention belongs to the technical field of power electronic converters and control, and particularly relates to a pulse load power supply and a voltage hysteresis control method thereof.
Background
The bidirectional buck/boost converter has the advantages of high efficiency, high power density, simple structure and the like, has the function of bidirectional energy transmission, and is suitable for various power supply systems, such as a radar base station power supply system, a vehicle-mounted battery, a photovoltaic grid-connected system, a wind power generation system and the like. The bidirectional buck/boost converter can be expanded and doubled by combining the staggered parallel technology, so that the switching frequency of the system is improved, the output ripple is reduced, the size of a magnetic element is reduced, and the power density of the system is improved.
The operating efficiency and switching losses are an extremely important indicator in switching power supplies. In the bidirectional buck/boost converter, the switching loss, namely reactive power loss when the switching tube is switched on and off, can be enabled to work in a CRM (critical conduction) mode through parameter design of a system, so that the effect of zero current conduction of the switching tube is achieved, the switching loss is minimized, but the switching loss of the switching tube can only be reduced by adding an auxiliary circuit, and various auxiliary circuits are often overlarge in size, so that the high power density and integration of the system are not facilitated. When the integration level requirement of the switching power supply system is high, the working efficiency of the system is difficult to break through the bottleneck. In particular, in applications such as pulsed loads, continuous switching is often not required.
The pulse type load is a common nonlinear load, has the characteristic of short-time high load and has certain periodicity. Such as radar, ground navigation, broadcasting systems, and various communication devices, etc., all belong to pulse-type loads, and are mainly characterized by large peak value and low average value of instantaneous power. The common switching power supply is difficult to meet the power consumption requirement or has the characteristic of low working efficiency. The staggered parallel bidirectional buck/boost converter has large working capacity and smaller total system ripple, and meets the power consumption requirement of a pulse type load.
Although interleaved bi-directional buck/boost converters have been widely used in various power systems, due to the lack of a targeted control method, conventional bi-directional buck/boost converters often employ PI (proportional, integral) closed-loop control modes. When applied to a pulsed load, such a load has an intermittent operation characteristic, and is light and heavy when loaded, and a conventional control mode often cannot satisfy the operation efficiency when the load is changed. The traditional control mode always enables the bidirectional buck/boost converter to continuously work, the switching tube continuously switches, unnecessary continuous actions can enable the system to continuously generate larger switching loss, the reactive power of the system is unchanged, the total power is reduced, and therefore the efficiency of the system is gradually reduced.
Disclosure of Invention
In order to solve the problems in the prior art, the invention introduces a voltage hysteresis control algorithm, provides a pulse load power supply and a voltage hysteresis control method thereof, reduces the action times of a switching tube on the basis of not increasing any auxiliary hardware structure, better meets the power consumption requirement of a pulse load, and can keep the characteristics of high efficiency and high power density. The technical problems to be solved by the invention are realized by the following technical scheme:
one aspect of the present invention provides a voltage hysteresis control method of a pulse load power supply, including:
s1: collecting the load end voltage of the staggered parallel bidirectional buck/boost converter connected between the power supply and the load by using a sampling circuit;
s2: comparing the load end voltage of the staggered parallel bidirectional buck/boost converter with a preset boost low-voltage given value, a preset boost high-voltage given value, a preset buck low-voltage given value and a preset buck high-voltage given value, and generating corresponding square wave pulse control voltage according to a comparison result;
s3: and amplifying the square wave pulse control voltage and transmitting the square wave pulse control voltage to a switching tube in the staggered parallel type bidirectional buck/boost converter so as to control the on-off of the switching tube by using a voltage hysteresis control algorithm.
In one embodiment of the present invention, before the step S1, the method further includes:
and presetting and adjusting a boost low-voltage given value, a boost high-voltage given value, a buck low-voltage given value and a buck high-voltage given value of the staggered parallel bidirectional buck/boost converter so as to adjust the loop width of voltage hysteresis control.
In one embodiment of the present invention, the controlling the on-off of the switching tube by using a voltage hysteresis control algorithm includes:
when the collected voltage value of the load end is smaller than the given value of the boost low voltage, the staggered parallel bidirectional buck/boost converter works in a boost mode, so that a power supply supplies power to the load;
when the voltage value of the load terminal is larger than the given value of the boost high voltage, the boost mode is terminated, so that the power supply stops supplying power to the load;
when the voltage value of the load end is larger than the buck high-voltage given value, the staggered parallel bidirectional buck/boost converter enters a buck mode, so that the load is discharged;
when the voltage value of the load terminal is smaller than the buck low-voltage given value, the buck mode is terminated, so that the load stops discharging;
and when the voltage value of the load terminal is between the boost low-voltage given value and the buck high-voltage given value, the switching tube keeps the current state.
In one embodiment of the invention, the load is a pulsed load.
In one embodiment of the invention, when the voltage value of the load terminal is lower than the low voltage given value of the boost, the boost mode is started, and the power supply supplies energy to the pulse load through the staggered parallel type bidirectional buck/boost converter; until the voltage of the load end reaches a boost high-voltage given value, ending the boost mode; and switching tubes of the staggered parallel bidirectional buck/boost converter are closed at the rest moments.
Another aspect of the invention provides a pulsed load power supply comprising an interleaved bi-directional buck/boost converter, a drive circuit, a sampling circuit and a control circuit, wherein,
the staggered parallel bidirectional buck/boost converter is connected between a power supply and a load and is used for realizing voltage conversion and bidirectional energy transmission between the power supply and the load;
the sampling circuit is connected with one end, close to the load, of the staggered parallel bidirectional buck/boost converter and is used for collecting the voltage of the load end of the staggered parallel bidirectional buck/boost converter;
the control circuit is connected with the sampling circuit and is used for comparing the load end voltage of the staggered parallel bidirectional buck/boost converter with a preset threshold value and generating square wave pulse control voltage according to a comparison result;
the driving circuit is connected between the control circuit and the staggered parallel type bidirectional buck/boost converter and is used for amplifying square wave pulse control voltage generated by the control circuit and transmitting the square wave pulse control voltage to a switching tube in the staggered parallel type bidirectional buck/boost converter;
the switching tube in the staggered parallel type bidirectional buck/boost converter is switched on and off based on a voltage hysteresis control algorithm.
In one embodiment of the present invention, the preset threshold includes a set boost low voltage set point, a boost high voltage set point, a buck low voltage set point, and a buck high voltage set point.
In one embodiment of the present invention, the voltage hysteresis control algorithm specifically includes:
when the voltage value of the load end acquired by the sampling circuit is smaller than the given value of the boost low voltage, controlling the staggered parallel bidirectional buck/boost converter to work in a boost mode, so that the power supply supplies power to the load;
when the voltage value of the load terminal is larger than the high-voltage given value of the boost, controlling the boost mode to terminate so that the power supply stops supplying power to the load;
when the voltage value of the load end is larger than the given value of the buck high voltage, controlling the staggered parallel bidirectional buck/boost converter to enter a buck mode, so that the load discharges;
when the voltage value of the load terminal is smaller than the buck low-voltage given value, controlling the buck mode to terminate, so that the load stops discharging;
and when the voltage value of the load terminal is between the given value of the boost low voltage and the given value of the buck high voltage, the staggered parallel type bidirectional buck/boost converter keeps the current state.
In one embodiment of the present invention, the driving circuit includes a first output terminal, a second output terminal, a third output terminal and a fourth output terminal respectively connected to different switching tubes of the interleaved bi-directional buck/boost converter, where the first output terminal and the second output terminal output two complementary pulse voltage signals, the third output terminal outputs a pulse voltage signal shifted to 180 ° from the first output terminal, and the fourth output terminal outputs a pulse voltage signal shifted to 180 ° from the second output terminal.
Compared with the prior art, the invention has the beneficial effects that:
1. the invention provides a pulse load power supply and a voltage hysteresis control method thereof. Firstly, enabling an interleaved parallel bi-directional buck/boost converter to work in a CRM (critical conduction) working mode; on the basis of reducing the turn-on loss of the system, the voltage of the load end is collected, a voltage hysteresis control algorithm is introduced, the voltage of the load end is compared with a preset threshold value, the purpose of maximally reducing the turn-off loss is achieved in a mode of minimizing the action times of a switching tube, the working efficiency of the staggered parallel bidirectional buck/boost converter is improved, and the effect is remarkable in the field of pulse load; and secondly, based on a voltage hysteresis control method, the energy bidirectional flow of the staggered parallel bidirectional buck/boost converter is realized, and the overvoltage of a load end caused by counter electromotive force or faults and the like is effectively restrained. It should be noted that, by adjusting the magnitude of the preset threshold, the loop width of the voltage hysteresis control can be adjusted, so as to regulate the voltage ripple at the load end and the sensitivity of the system. The control method provided by the invention has strong applicability and is suitable for various switching power supply systems under various pulse loads.
2. By utilizing the voltage hysteresis control method, under the application scenes of intermittent load, new energy charging and the like, when the new energy battery is charged, if the battery is in insufficient power, the staggered parallel bidirectional buck/boost converter works to provide energy for the battery; otherwise, the staggered parallel type bidirectional buck/boost converter is in a non-working state, so that the switching loss of the staggered parallel type bidirectional buck/boost converter is obviously reduced. And by reducing the action times of the switching tube, the failure time and the service life of the element are improved. And the storage battery is protected by means of reverse energy release.
The present invention will be described in further detail with reference to the accompanying drawings and examples.
Drawings
FIG. 1 is a flowchart of a voltage hysteresis control method of a pulse load power supply according to an embodiment of the present invention;
FIG. 2 is a schematic diagram of a voltage hysteresis control process of a voltage hysteresis control method of a pulse load power supply according to an embodiment of the present invention;
FIG. 3 is a schematic diagram of a voltage hysteresis control process in which the load is a pulsed load according to an embodiment of the present invention;
FIG. 4 is a block diagram of a pulsed load power supply according to an embodiment of the present invention;
FIG. 5 is a circuit diagram of a pulsed load power supply according to an embodiment of the present invention;
FIG. 6 is a schematic diagram of connection between a driving circuit and a control circuit according to an embodiment of the present invention;
fig. 7 shows a switching tube (S) 1 And S is 3 ) A comparison schematic diagram of drain-source voltage and inductance current waveform;
FIG. 8 shows a driving voltage and a switching tube (S) under voltage hysteresis control according to an embodiment of the present invention 1 And S is 3 ) Drain-source voltage and load terminal voltage V of (a) 0 Is a comparative schematic of (1);
fig. 9 is a graph comparing efficiency of voltage hysteresis control provided by an embodiment of the present invention with that of conventional PI control.
Detailed Description
In order to further explain the technical means and effects adopted by the invention to achieve the preset aim, the invention provides an intermittent new energy power supply system and method based on voltage hysteresis control, which are described in detail below with reference to the accompanying drawings and the detailed description.
The foregoing and other features, aspects, and advantages of the present invention will become more apparent from the following detailed description of the preferred embodiments when taken in conjunction with the accompanying drawings. The technical means and effects adopted by the present invention to achieve the intended purpose can be more deeply and specifically understood through the description of the specific embodiments, however, the attached drawings are provided for reference and description only, and are not intended to limit the technical scheme of the present invention.
It should be noted that in this document relational terms such as first and second, and the like are used solely to distinguish one entity or action from another entity or action without necessarily requiring or implying any actual such relationship or order between such entities or actions. Moreover, the terms "comprises," "comprising," or any other variation thereof, are intended to cover a non-exclusive inclusion, such that an article or apparatus that comprises a list of elements does not include only those elements but may include other elements not expressly listed. Without further limitation, an element defined by the phrase "comprising one … …" does not exclude the presence of other like elements in an article or apparatus that comprises the element.
Example 1
Referring to fig. 1, fig. 1 is a flowchart of a voltage hysteresis control method of a pulse load power supply according to an embodiment of the invention. The voltage hysteresis control method comprises the following steps:
s1: collecting the load end voltage of the staggered parallel bidirectional buck/boost converter connected between the power supply and the load by using a sampling circuit;
s2: comparing the load end voltage of the staggered parallel bidirectional buck/boost converter with a preset boost low-voltage given value, a preset boost high-voltage given value, a preset buck low-voltage given value and a preset buck high-voltage given value, and generating corresponding square wave pulse control voltage according to a comparison result;
s3: and amplifying the square wave pulse control voltage and transmitting the square wave pulse control voltage to a switching tube in the staggered parallel type bidirectional buck/boost converter so as to control the on-off of the switching tube by using a voltage hysteresis control algorithm.
Further, before S1, the method further includes:
and presetting and adjusting a boost low-voltage given value, a boost high-voltage given value, a buck low-voltage given value and a buck high-voltage given value of the staggered parallel bidirectional buck/boost converter so as to adjust the loop width of voltage hysteresis control.
The loop width of hysteresis control can be adjusted by adjusting a preset boost low-voltage given value, a preset boost high-voltage given value, a preset buck low-voltage given value and a preset buck high-voltage given value, so that voltage ripple of a load terminal and sensitivity of a system are adjusted.
The staggered parallel type bidirectional Buck/Boost converter of the embodiment is a two-phase staggered parallel type bidirectional Buck/Boost converter, and the power born by each phase by the parallel connection of 2 identical Buck/Boost circuits is reduced to one half of that of the traditional Buck/Boost circuit, so that a larger space is brought for the type selection of devices, and meanwhile, the inductance value and the inductance volume can be reduced; when in operation, the two-phase circuit is conducted in a staggered way with a phase difference of 180 degrees.
According to the characteristics of the staggered parallel bidirectional buck/boost converter, zero current switching on of a switching tube can be realized through reasonable circuit parameters, so that the size of a magnetic element is reduced, and the power density and efficiency of a system are improved; the total inductance current ripple of the system is reduced to the maximum extent in a two-phase 180-degree staggered parallel mode; and the complementary pulse voltage is applied to the two switching tubes of the same phase in a synchronous rectification mode, so that zero voltage switching on of an upper tube is realized, the reverse recovery time of a body diode of the upper tube is reduced, and the on-state loss of the system is reduced; the novel SiC device is adopted, so that the system is high-frequency, the volume of a magnetic original is reduced, and the power density of the system is improved.
Further, referring to fig. 2, fig. 2 is a schematic diagram of a voltage hysteresis control process of a voltage hysteresis control method of a pulse load power supply according to an embodiment of the present invention. The on-off of the switching tube is controlled by a voltage hysteresis control algorithm, which comprises the following steps:
when the collected voltage value of the load end is smaller than the given value of the boost low voltage, the staggered parallel bidirectional buck/boost converter works in a boost mode, so that a power supply supplies power to the load;
when the voltage value of the load terminal is larger than the given value of the boost high voltage, the boost mode is terminated, so that the power supply stops supplying power to the load;
when the voltage value of the load end is larger than the buck high-voltage given value, the staggered parallel bidirectional buck/boost converter enters a buck mode, so that the load is discharged;
when the voltage value of the load terminal is smaller than the buck low-voltage given value, the buck mode is terminated, so that the load stops discharging;
and when the voltage value of the load terminal is between the boost low-voltage given value and the buck high-voltage given value, the switching tube keeps the current state.
The load of this embodiment is a pulsed load. Referring to fig. 3, when the load is a pulse load, the boost mode is turned on once the voltage value at the load end is lower than the boost low-voltage given value, and the power supply supplies energy to the pulse load through the staggered parallel bidirectional buck/boost converter; until the voltage of the load end reaches a boost high-voltage given value, ending the boost mode; and the square wave pulse voltage between the grid and the source of the switching tube at the rest moment is zero, namely the switching tube is closed. The frequency of the switching tube operation depends on the frequency of the pulse load, and the lower the pulse load frequency is, the fewer the switching tube operation times are, namely the smaller the switching loss is, and the higher the working efficiency of the staggered parallel bidirectional buck/boost converter is.
The embodiment provides a voltage hysteresis control method of a pulse load power supply, and a system for executing the method comprises a staggered parallel type bidirectional buck/boost converter hardware system architecture and a voltage hysteresis software control algorithm based on a DSP. Firstly, enabling an interleaved parallel bi-directional buck/boost converter to work in a CRM (critical conduction) working mode; on the basis of reducing the turn-on loss of the system, the voltage of the load end is collected, a voltage hysteresis control algorithm is introduced, the voltage of the load end is compared with a preset threshold value, the purpose of maximally reducing the turn-off loss is achieved in a mode of minimizing the action times of a switching tube, the working efficiency of the staggered parallel bidirectional buck/boost converter is improved, and the effect is remarkable in the field of pulse load; and secondly, based on a voltage hysteresis control method, the energy bidirectional flow of the staggered parallel bidirectional buck/boost converter is realized, and the overvoltage of a load end caused by counter electromotive force or faults and the like is effectively restrained. It should be noted that, by adjusting the magnitude of the preset threshold, the loop width of the voltage hysteresis control can be adjusted, so as to regulate the voltage ripple at the load end and the sensitivity of the system. The control method provided by the invention has strong applicability and is suitable for various switching power supply systems under various pulse loads.
Example two
On the basis of the above embodiments, the present embodiment provides a pulse load power supply. Referring to fig. 4, fig. 4 is a block diagram of a pulse load power supply according to an embodiment of the invention. The intermittent new energy power supply system comprises an interleaved parallel type bidirectional buck/boost converter 1, a driving circuit 2, a sampling circuit 3 and a control circuit 4, wherein the interleaved parallel type bidirectional buck/boost converter 1 is connected between a power supply 5 and a load 6 and is used for realizing voltage conversion and bidirectional energy transmission between the power supply 5 and the load 6; the sampling circuit 3 is connected with one end of the staggered parallel bidirectional buck/boost converter 1, which is close to the load 6, and is used for collecting the voltage of the load end of the staggered parallel bidirectional buck/boost converter 1; the control circuit 4 is connected with the sampling circuit 3 and is used for comparing the load end voltage of the staggered parallel bidirectional buck/boost converter 1 with a preset threshold value and generating square wave pulse control voltage according to a comparison result; the driving circuit 2 is connected between the control circuit 4 and the staggered parallel type bidirectional buck/boost converter 1, and is used for amplifying and transmitting square wave pulse control voltage generated by the control circuit 4 to a switching tube in the staggered parallel type bidirectional buck/boost converter 1 so as to control the on-off of the switching tube by using a voltage hysteresis control algorithm.
In this embodiment, the preset threshold includes a set boost low voltage given value, a boost high voltage given value, a buck low voltage given value, and a buck high voltage given value.
The voltage hysteresis control algorithm of this embodiment specifically includes:
when the voltage value of the load end acquired by the sampling circuit 3 is smaller than the given value of the boost low voltage, the staggered parallel bidirectional buck/boost converter 1 is controlled to work in a boost mode, so that the power supply 5 supplies power to the load 6; when the voltage value of the load terminal is larger than the high-voltage given value of the boost, the boost mode is terminated, so that the power supply 5 stops supplying power to the load 6; when the voltage value of the load end is larger than the given value of the buck high voltage, controlling the staggered parallel bidirectional buck/boost converter 1 to enter a buck mode, so that the load 6 discharges; when the voltage value of the load terminal is smaller than the buck low-voltage given value, terminating the buck mode, so that the load 6 stops discharging; when the voltage value of the load terminal is between the given value of the boost low voltage and the given value of the buck high voltage, the staggered parallel type bidirectional buck/boost converter 1 keeps the current state.
Further, referring to fig. 5, fig. 5 is a circuit diagram of a pulse load power supply according to an embodiment of the invention. The interleaved bi-directional buck/boost converter 1 of the present embodiment includes a first capacitor C 1 A second capacitor C 2 First inductor L 1 Second inductance L 2 First MOS transistor S 1 Second MOS transistor S 2 Third MOS transistor S 3 Fourth MOS transistor S 4 First parasitic diode D 1 Second parasitic diode D 2 Third parasitic diode D 3 And a fourth parasitic diode D 4 Wherein, the method comprises the steps of, wherein,
first capacitor C 1 A second capacitor C connected between the output end of the power supply 5 and the ground GND 2 Connected between the load 6 and ground GND;
first MOS transistor S 1 A first MOS tube S connected to the first output end of the driving circuit 2 1 The source electrode of (1) is connected with the grounding end, the first MOS tube S 1 The drain electrode of the transistor is connected with the second MOS tube S 2 Source electrode of the third MOS transistor S 3 The gate of the transistor is connected to the third output end of the driving circuit 2, and a third MOS transistor S 3 The source electrode of the third MOS tube S is connected with the grounding end 3 The drain electrode of the transistor is connected with a fourth MOS tube S 4 A source of (a);
second MOS transistor S 2 The grid electrode of the second MOS tube S is connected to the second output end of the driving circuit 2 2 The drain electrode of the transistor is connected with a load 6, a fourth MOS tube S 4 The grid electrode of the transistor is connected to the fourth output end of the driving module 2, and a fourth MOS tube S 4 Is connected to the load 6;
first parasitic diode D 1 The anode of the first MOS tube S is connected with 1 Source of first parasitic diodeTube D 2 The negative electrode of (a) is connected with the first MOS tube S 1 Drain electrode of the second parasitic diode D 2 The anode of the second MOS tube S is connected with 2 Source of second parasitic diode D 2 Is connected with a second MOS tube S 2 Drain electrode of third parasitic diode D 3 The anode of the third MOS tube S is connected with 3 Source of third parasitic diode D 3 Is connected with a third MOS tube S 3 Drain electrode of fourth parasitic diode D 4 The anode of the transistor is connected with a fourth MOS tube S 4 Source of fourth parasitic diode D 4 Is connected with a fourth MOS tube S 4 A drain electrode of (2);
first inductance L 1 One end of the transistor is connected to the power supply 5, and the other end is connected to the second MOS tube S 2 Source electrode of the second inductance L 2 One end of the transistor is connected to the power supply 5, and the other end is connected to the fourth MOS transistor S 4 Is a source of (c).
Further, the first output end and the second output end of the driving circuit 2 are used for outputting two paths of complementary pulse voltage signals, so as to respectively drive the first MOS tube S 1 And a second MOS transistor S 2 The method comprises the steps of carrying out a first treatment on the surface of the Meanwhile, the third output end is used for outputting the pulse voltage which is phase-shifted by 180 degrees from the first output end, and the fourth output end is used for outputting the pulse voltage which is phase-shifted by 180 degrees from the second output end, so as to respectively drive the third MOS tube S 3 And a fourth MOS transistor S 4 。
It should be noted that, the interleaved bi-directional Buck/Boost converter 1 of the present embodiment is a two-phase interleaved bi-directional Buck/Boost converter, and is formed by connecting 2 identical Buck/Boost circuits in parallel, wherein the first MOS transistor S 1 Second MOS transistor S 2 And a first inductance L 1 Form a phase, a third MOS tube S 3 Fourth MOS transistor S 4 And a second inductance L 2 The second phase is formed, so that the power born by each phase is reduced to one half of that of a traditional Buck/Boost circuit, a larger space is brought for the type selection of the device, and meanwhile, the inductance value and the inductance volume can be reduced; when in operation, the two-phase circuit is conducted in a staggered way with a phase difference of 180 degrees.
According to the characteristics of the staggered parallel bidirectional buck/boost converter, zero current switching on of a switching tube can be realized through reasonable circuit parameters, so that the size of a magnetic element is reduced, and the power density and efficiency of a system are improved; the total inductance current ripple of the system is reduced to the maximum extent in a two-phase 180-degree staggered parallel mode; and the complementary pulse voltage is applied to the two switching tubes of the same phase in a synchronous rectification mode, so that zero voltage switching on of an upper tube is realized, the reverse recovery time of a body diode of the upper tube is reduced, and the on-state loss of the system is reduced; the novel SiC device is adopted, so that the system is high-frequency, the volume of a magnetic original is reduced, and the power density of the system is improved.
In the present embodiment, the control circuit 4 specifically includes a DSP F28335 control chip, and a peripheral power supply circuit, an ePWM peripheral module, an ADC peripheral module, and the like. The DSP F28335 is used for controlling the staggered parallel type bidirectional buck/boost converter, and the voltage hysteresis control process is realized through the C language code. In addition, the boost low voltage given value, the boost high voltage given value, the buck low voltage given value and the buck high voltage given value can be preset and stored.
The driving circuit 2 of the embodiment specifically comprises a Si8275 driving chip, an isolation power supply module and peripheral circuits thereof, wherein the Si8275 driving chip is mainly responsible for modulating and amplifying square wave pulse control signals output by a DSP F28335 control chip to generate pulses required by a switching tube, and the isolation power supply module is mainly responsible for supplying power to each output of the driving chip and providing isolation function so that the driving chip can be used for driving a high-end MOSFET; the peripheral circuit mainly comprises a driving resistor, a bypass capacitor and the like. In other embodiments, the driving circuit 2 and the control circuit 4 may be other suitable circuits or modules capable of implementing the respective functions.
Referring to fig. 6, fig. 6 is a schematic diagram illustrating connection between a driving circuit and a control circuit according to an embodiment of the invention. Because the switching tube is selected as the MOS tube, the control mode is selected as the voltage type control, and in order to improve the output stability, a closed loop feedback loop is selected and built to control the switching tube. The DSP F28335 has complete internal functions, can complete a series of functions of closed-loop PI control, PWM pulse width modulation and the like of the system through programming, saves a large amount of volume, and has the advantages of convenient operation, low cost and the likeThe voltage value output from DSP F28335 is insufficient to drive the MOS transistor: the output voltage of the DSP F28335 is 3.3V at most, and the MOS transistor generally needs gate driving of 10V to 15V, so the voltage of the PWM wave must be raised to drive the MOS transistor, and finally, the Si8275 programmable MOS driving chip is selected. By examining the data manual, the VDD voltage range at the input side is required to be 2.5-5.5V, the VDDA and VDDB supply voltages at the output side are required to be between 4.2-30V, and the bypass capacitors at the input side and the output side of the Si8275 driver chip are helpful for reducing high-frequency noise and improving performance. The two drive outputs are independent of each other so that the polarity of the relative voltages of the VOA and VOB may be reversed, i.e. the voltage of the VOA may be higher or lower than the voltage of the VOB. In the invention, four switching tubes are required to be driven, and each driving chip only has two paths of output, namely, each driving chip only can drive two switching tubes, so that two Si8275 driving chips are required to be provided for driving the four switching tubes. In this embodiment, as shown in fig. 6, the VOA end of the Si8275 driving chip is connected to the second MOS transistor S 2 The VOB end is connected with the first MOS tube S through a NOT gate 1 To drive the first MOS tube S respectively 1 And a second MOS transistor S 2 And the VOA terminal and the VOB terminal output two complementary pulse voltage signals. Similarly, in another driving chip, the VOA end is connected with a fourth MOS tube S 4 The VOB end is connected with the third MOS tube S through a NOT gate 3 To control the third MOS tube S respectively 3 And a fourth MOS transistor S 4 Is provided for the opening and closing of (a). It should be noted that one DSP F28335 control chip is connected to two Si8275 driving chips at the same time.
The sampling circuit 3 of the present embodiment may be any suitable sampling circuit or module, and is not limited herein.
Preferably, the power source 5 is a dc power source and the load 6 is a battery or a pulsed load. When the load is a storage battery, if the storage battery needs to be charged, the staggered parallel bidirectional buck/boost converter works normally, provides energy for the storage battery and stops when the storage battery is full; when the storage battery is deficient, the converter is started again to supplement energy for the storage battery; at other moments, the converter does not work, so that the switching loss caused by continuous work is greatly reduced, and the average power of the system is improved. In addition, the staggered parallel type bidirectional buck/boost converter in the intermittent new energy power supply system has a reverse energy transmission function, and when the terminal voltage of the storage battery is too high due to other reasons such as back electromotive force or short circuit and the like, the storage battery can reversely discharge energy through the converter to play a role in protecting the storage battery.
It should be noted that, according to the parameter design of the system, the system works in CRM (critical on) operation mode. The number of the interleaved parallel phases of the interleaved parallel bi-directional buck/boost converter 1 of the embodiment is two, and when the duty ratio is 50%, the peak values of the inductor current ripple of the system can be offset, and the theoretical value of the total ripple is 0. Preferably, when the first inductance L 1 And a second inductance L 2 When the inductance value of (1) is 68uH, the staggered parallel type bidirectional buck/boost converter 1 works in a CRM mode, namely a switching tube S 1 And S is 3 Zero current turn-on is realized, and turn-on loss is reduced. By calculation, capacitance C 1 And C 2 The capacity value is 10uF, the volume is extremely small, and the method has obvious effect on increasing the power density of the system.
Further, referring to fig. 7, fig. 7 is a schematic diagram of a switching tube (S) 1 And S is 3 ) A comparison diagram of drain-source voltage and inductance current waveform, wherein the abscissa represents time, and the drain-source voltage is the first MOS tube S 1 Drain-source voltage of (2), inductor current is L 1 Is set in the above-described range). In this embodiment, in the first MOS transistor S 1 Before the MOS transistor is turned on, the current of the MOS transistor is reduced to 0, namely the MOS transistor realizes zero-current turn-on; similarly, a third MOS transistor S 3 Zero current turn on is also achieved. Thereby reducing the first MOS transistor S 1 And a third MOS transistor S 3 The opening loss of the system is improved. It can be seen that the system has a very small volume of the magnetic element by reasonable design, thereby improving the power density of the system.
Referring to fig. 8, fig. 8 is a schematic diagram showing a driving voltage and a load voltage V under voltage hysteresis control according to an embodiment of the present invention 0 Wherein the abscissa represents time, the driving voltage is the output voltage of the driving circuit, and the drain-source voltage is the first MOS tube S 1 And a third MOS transistor S 3 The output voltage is the output voltage of the staggered parallel bidirectional buck/boost converter 1, namely the load terminal voltage. It is not difficult to find that compared with the traditional PI closed-loop control mode, the control mode obviously reduces the action times of the switching tube, so that the switching loss of the system is reduced. As can be seen from fig. 8, in this control mode, there are two phases of circuit operation and non-operation within one cycle. Taking Boost working mode as an example, the circuit is started in the working stage, the voltage hysteresis control works, PWM modulation is carried out on the control signals, and the complementation of the two paths of control signals is kept, so that the circuit is boosted. When the voltage rises to the upper limit of Boost mode, the system will stop the output of PWM pulse voltage so that the power supply supplies power to the load, wait until it falls to the lower limit of Boost mode, and the control circuit will restart, repeating the above process.
Further, referring to fig. 9, fig. 9 is a graph showing the comparison between the efficiency of the voltage hysteresis control provided by the embodiment of the present invention and the efficiency of the existing PI (proportional integral) control. It is apparent that when the load is gradually reduced from the heavy load, the efficiency of the conventional PI control mode has a significant tendency to decrease, and thus is not suitable for the fields of intermittent load and the like. The voltage hysteresis control mode of the intermittent new energy power supply system provided by the embodiment is relatively stable in efficiency, and particularly the efficiency is gradually improved when the load is lightened, so that the intermittent new energy power supply system has important research significance in the fields of intermittent loads such as radar antennas, base station navigation and the like and new energy scenes such as vehicle-mounted chargers and wind power generation and the like.
In the intermittent new energy power supply system of the embodiment, a voltage hysteresis double-position control mode is adopted, and in the control mode, the action times of a switching tube in the system are obviously reduced, so that the switching loss of the system is reduced, and the working efficiency of the system is greatly improved. Under the application scenes of intermittent load, new energy charging and the like, when the new energy battery is charged, if the battery is in insufficient power, the system works to provide energy for the storage battery; otherwise, the system is in a non-working state, which obviously reduces the switching loss of the system. And by reducing the action times of the switching tube, the failure time and the service life of the element are improved. And the storage battery is protected by means of reverse energy release.
The foregoing is a further detailed description of the invention in connection with the preferred embodiments, and it is not intended that the invention be limited to the specific embodiments described. It will be apparent to those skilled in the art that several simple deductions or substitutions may be made without departing from the spirit of the invention, and these should be considered to be within the scope of the invention.
Claims (6)
1. The voltage hysteresis control method of the pulse load power supply is characterized by comprising the following steps of:
s1: collecting the load end voltage of the staggered parallel bidirectional buck/boost converter connected between the power supply and the load by using a sampling circuit;
s2: comparing the load end voltage of the staggered parallel bidirectional buck/boost converter with a preset boost low-voltage given value, a preset boost high-voltage given value, a preset buck low-voltage given value and a preset buck high-voltage given value, and generating corresponding square wave pulse control voltage according to a comparison result;
s3: amplifying the square wave pulse control voltage and transmitting the square wave pulse control voltage to a switching tube in the staggered parallel type bidirectional buck/boost converter so as to control the on-off of the switching tube by using a voltage hysteresis control algorithm;
the on-off of the switching tube is controlled by a voltage hysteresis control algorithm, which comprises the following steps:
when the collected voltage value of the load end is smaller than the given value of the boost low voltage, the staggered parallel bidirectional buck/boost converter works in a boost mode, so that a power supply supplies power to the load;
when the voltage value of the load terminal is larger than the given value of the boost high voltage, the boost mode is terminated, so that the power supply stops supplying power to the load;
when the voltage value of the load end is larger than the buck high-voltage given value, the staggered parallel bidirectional buck/boost converter enters a buck mode, so that the load is discharged;
when the voltage value of the load terminal is smaller than the buck low-voltage given value, the buck mode is terminated, so that the load stops discharging;
and when the voltage value of the load terminal is between the boost low-voltage given value and the buck high-voltage given value, the switching tube keeps the current state.
2. The method of claim 1, further comprising, prior to S1:
and presetting and adjusting a boost low-voltage given value, a boost high-voltage given value, a buck low-voltage given value and a buck high-voltage given value of the staggered parallel bidirectional buck/boost converter so as to adjust the loop width of voltage hysteresis control.
3. The voltage hysteresis control method of a pulsed-load power supply according to any one of claims 1 to 2, wherein the load is a pulsed-load.
4. A method of controlling a voltage hysteresis of a pulsed-load power supply according to claim 3 wherein, when the load-side voltage level is below a boost low-voltage setpoint, boost mode is enabled and power is supplied to the pulsed load by the power supply through the interleaved bi-directional buck/boost converter; until the voltage of the load end reaches a boost high-voltage given value, ending the boost mode; and switching tubes of the staggered parallel bidirectional buck/boost converter are closed at the rest moments.
5. A pulse load power supply is characterized by comprising a staggered parallel type bidirectional buck/boost converter (1), a driving circuit (2), a sampling circuit (3) and a control circuit (4), wherein,
the staggered parallel type bidirectional buck/boost converter (1) is connected between the power supply (5) and the load (6) and is used for realizing voltage conversion and bidirectional energy transmission between the power supply (5) and the load (6);
the sampling circuit (3) is connected with one end, close to the load (6), of the staggered parallel type bidirectional buck/boost converter (1) and is used for collecting the load end voltage of the staggered parallel type bidirectional buck/boost converter (1);
the control circuit (4) is connected with the sampling circuit (3) and is used for comparing the load end voltage of the staggered parallel bidirectional buck/boost converter (1) with a preset threshold value and generating square wave pulse control voltage according to a comparison result, wherein the preset threshold value comprises a set boost low-voltage given value, a boost high-voltage given value, a buck low-voltage given value and a buck high-voltage given value;
the driving circuit (2) is connected between the control circuit (4) and the staggered parallel bidirectional buck/boost converter (1) and is used for amplifying square wave pulse control voltage generated by the control circuit (4) and transmitting the square wave pulse control voltage to a switching tube in the staggered parallel bidirectional buck/boost converter (1);
the switching tube in the staggered parallel type bidirectional buck/boost converter (1) is switched on and off based on a voltage hysteresis control algorithm;
the voltage hysteresis control algorithm specifically comprises:
when the voltage value of the load end acquired by the sampling circuit (3) is smaller than the given value of the boost low voltage, the staggered parallel bidirectional buck/boost converter (1) is controlled to work in a boost mode, so that the power supply (5) supplies power to the load (6);
when the voltage value of the load terminal is larger than the given value of the boost high voltage, controlling the boost mode to terminate so that the power supply (5) stops supplying power to the load (6);
when the voltage value of the load end is larger than the given value of the buck high voltage, controlling the staggered parallel bidirectional buck/boost converter (1) to enter a buck mode, so that the load (6) discharges;
when the voltage value of the load terminal is smaller than the buck low-voltage given value, controlling the buck mode to terminate so that the load (6) stops discharging;
when the voltage value of the load terminal is between the given value of the boost low voltage and the given value of the buck high voltage, the staggered parallel type bidirectional buck/boost converter (1) keeps the current state.
6. The pulse load power supply according to claim 5, wherein the driving circuit (2) comprises a first output end, a second output end, a third output end and a fourth output end which are respectively connected with different switching tubes of the staggered parallel bidirectional buck/boost converter (1), wherein the first output end and the second output end output two paths of complementary pulse voltage signals, the third output end outputs the pulse voltage signal which is 180 degrees shifted by the first output end, and the fourth output end outputs the pulse voltage signal which is 180 degrees shifted by the second output end.
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Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN203326914U (en) * | 2013-06-05 | 2013-12-04 | 中国石油大学(华东) | Hysteresis current control double Buck-Boost inverter |
| CN108574411A (en) * | 2018-05-22 | 2018-09-25 | 安徽工业大学 | Two-way DC/DC power inverters dual-port stable control method and its control circuit |
| CN111193397A (en) * | 2020-01-14 | 2020-05-22 | 四川航电微能源有限公司 | Dynamic dormancy control method for switching tubes of three-phase interleaved parallel bidirectional DC/DC converter |
Family Cites Families (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102315773B (en) * | 2010-07-02 | 2014-02-12 | 成都芯源系统有限公司 | Apparatus and method for switching converter |
| US8441231B2 (en) * | 2011-05-27 | 2013-05-14 | Eta Semiconductor Inc. | Bidirectional hysteretic power converter |
| KR101793009B1 (en) * | 2016-10-31 | 2017-11-03 | 한국과학기술원 | Current mode hysteretic buck converter employing auto-selectable frequency locking circuit |
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Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN203326914U (en) * | 2013-06-05 | 2013-12-04 | 中国石油大学(华东) | Hysteresis current control double Buck-Boost inverter |
| CN108574411A (en) * | 2018-05-22 | 2018-09-25 | 安徽工业大学 | Two-way DC/DC power inverters dual-port stable control method and its control circuit |
| CN111193397A (en) * | 2020-01-14 | 2020-05-22 | 四川航电微能源有限公司 | Dynamic dormancy control method for switching tubes of three-phase interleaved parallel bidirectional DC/DC converter |
Non-Patent Citations (1)
| Title |
|---|
| Microcontroller Based Implementation of Peak Current Control Method in a Bidirectional Buck-Boost DC-DC Converter;Nick Rigogiannis et al.;2018 20th International Symposium on Electrical Apparatus and Technologies (SIELA);第1-4页 * |
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