CN113872437A - High-efficiency pulse load power supply and voltage hysteresis control method thereof - Google Patents
High-efficiency pulse load power supply and voltage hysteresis control method thereof Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
- H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
- H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of DC power input into DC power output
- H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
- H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
- H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1582—Buck-boost converters
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
本发明公开了一种高效率脉冲负载电源及其电压滞环控制方法，所述电压滞环控制方法包括：利用采样电路采集连接在电源与负载之间的交错并联型双向buck/boost变换器的负载端电压；将所述交错并联型双向buck/boost变换器的负载端电压与预先设定的boost低压给定值、boost高压给定值、buck低压给定值和buck高压给定值进行比较，并根据比较结果产生相应的方波脉冲控制电压；将所述方波脉冲控制电压进行放大并传输至所述交错并联型双向buck/boost变换器中的开关管处，以利用电压滞环控制算法控制所述开关管的通断。本发明采用电压滞环双位控制方式，在该控制模式下，系统中开关管的动作次数明显降低，从而减小了系统的开关损耗，提高了系统的工作效率。
The invention discloses a high-efficiency pulse load power supply and a voltage hysteresis control method thereof. The voltage hysteresis control method comprises: using a sampling circuit to collect the data of an interleaved parallel bidirectional buck/boost converter connected between the power supply and the load. load terminal voltage; compare the load terminal voltage of the interleaved parallel bidirectional buck/boost converter with the preset boost low voltage given value, boost high voltage given value, buck low voltage given value and buck high voltage given value , and generate the corresponding square wave pulse control voltage according to the comparison result; amplify the square wave pulse control voltage and transmit it to the switch tube in the interleaved parallel bidirectional buck/boost converter, so as to use the voltage hysteresis control The algorithm controls the on-off of the switch tube. The present invention adopts the voltage hysteresis two-position control mode. In this control mode, the number of actions of the switching tube in the system is obviously reduced, thereby reducing the switching loss of the system and improving the working efficiency of the system.
Description
Technical Field
The invention belongs to the technical field of power electronic converters and control, and particularly relates to a high-efficiency pulse load power supply and a voltage hysteresis control method thereof.
Background
The bidirectional buck/boost converter has the advantages of high efficiency, high power density, simple structure and the like, has an energy bidirectional transmission function, and is suitable for various power supply systems, such as a radar base station power supply system, a vehicle-mounted battery, a photovoltaic grid-connected system, a wind power generation system and the like. By combining the staggered parallel technology, the capacity expansion and frequency multiplication can be carried out on the bidirectional buck/boost converter, so that the switching frequency of the system is improved, the output ripple wave is reduced, the volume of the magnetic element is reduced, and the power density of the system is improved.
The operating efficiency and the switching losses are very important indexes of the switching power supply. The switching loss, namely the reactive loss when the switching tube is switched on and off, can be enabled to work in a CRM (critical conduction) mode through the parameter design of the system in the bidirectional buck/boost converter, the effect of zero current conduction of the switching tube is achieved, and the switching loss is minimized, but the switching-off loss of the switching tube can only be reduced in a mode of adding an auxiliary circuit, and in addition, various auxiliary circuits are often too large in size, so that the bidirectional buck/boost converter is not beneficial to high-power density and integration of the system. When the requirement on the integration level of a switching power supply system is high, the working efficiency of the system is difficult to break through the bottleneck. In particular, in applications such as pulsed loads, continuous switching is often not required.
The pulse type load is a common one of nonlinear loads, has the characteristic of short-time high load and also has certain periodicity. Such as radar, ground navigation, broadcasting system and various communication devices, belong to pulse type loads, and are mainly characterized in that the peak value of instantaneous power is large and the average value is low. The common switching power supply is difficult to meet the power consumption requirement or has the characteristic of low working efficiency. The staggered parallel connection type bidirectional buck/boost converter is large in working capacity, small in total ripple of a system and capable of meeting the power consumption requirement of pulse type loads.
Although the interleaved parallel bidirectional buck/boost converter is widely applied to various power supply systems, due to the lack of a targeted control method, the traditional bidirectional buck/boost converter often adopts a PI (proportional, integral) closed-loop control mode. When applied to pulse type loads, the loads have the characteristic of intermittent operation, the loads are light and heavy, and the traditional control mode cannot meet the working efficiency of load change. The traditional control mode always enables the bidirectional buck/boost converter to work continuously, the switching tube is switched continuously, unnecessary continuous actions enable the system to generate larger switching loss continuously, the phenomena of constant reactive power and total power reduction of the system are presented, and therefore the efficiency of the system is reduced gradually.
Disclosure of Invention
In order to solve the problems in the prior art, the invention introduces a voltage hysteresis control algorithm, provides a high-efficiency pulse load power supply and a voltage hysteresis control method thereof, reduces the action times of a switching tube on the basis of not increasing any auxiliary hardware structure, better meets the power consumption requirement of a pulse type load, and can keep the characteristics of high efficiency and high power density. The technical problem to be solved by the invention is realized by the following technical scheme:
one aspect of the present invention provides a voltage hysteresis control method for a high-efficiency pulse load power supply, including:
s1: acquiring the load terminal voltage of a staggered parallel bidirectional buck/boost converter connected between a power supply and a load by using a sampling circuit;
s2: comparing the load terminal voltage of the staggered parallel bidirectional buck/boost converter with a preset boost low-voltage given value, a boost high-voltage given value, a buck low-voltage given value and a buck high-voltage given value, and generating corresponding square wave pulse control voltage according to the comparison result;
s3: and amplifying the square wave pulse control voltage and transmitting the amplified square wave pulse control voltage to a switch tube in the staggered parallel connection type bidirectional buck/boost converter so as to control the on-off of the switch tube by using a voltage hysteresis control algorithm.
In an embodiment of the present invention, before the S1, the method further includes:
and presetting and adjusting a boost low-voltage given value, a boost high-voltage given value, a buck low-voltage given value and a buck high-voltage given value of the staggered parallel bidirectional buck/boost converter so as to adjust the ring width of voltage hysteresis control.
In one embodiment of the present invention, the controlling the on/off of the switching tube by using a voltage hysteresis control algorithm includes:
when the collected load end voltage value is smaller than the boost low-voltage given value, the staggered parallel connection type bidirectional buck/boost converter works in a boost mode, so that a power supply supplies power to a load;
when the voltage value of the load terminal is larger than the given value of the boost high voltage, the boost mode is terminated, so that the power supply stops supplying power to the load;
when the voltage value of the load terminal is larger than the buck high-voltage given value, the staggered parallel bidirectional buck/boost converter enters a buck mode, so that the load discharges;
when the voltage value of the load end is smaller than the buck low-voltage given value, the buck mode is terminated, so that the load stops discharging;
when the voltage value of the load end is between the boost low-voltage given value and the buck high-voltage given value, the switch tube keeps the current state.
In one embodiment of the invention, the load is a pulse type load.
In one embodiment of the invention, once the voltage value of the load terminal is lower than the given value of boost low voltage, the boost mode is started, and the power supply supplies energy to the pulse load through the staggered parallel bidirectional buck/boost converter; ending the boost mode until the voltage of the load terminal reaches the boost high-voltage given value; and the switching tubes of the staggered parallel connection type bidirectional buck/boost converter are closed at the rest time.
Another aspect of the present invention provides a high efficiency pulsed load power supply comprising an interleaved parallel bi-directional buck/boost converter, a driving circuit, a sampling circuit and a control circuit, wherein,
the staggered parallel connection type bidirectional buck/boost converter is connected between a power supply and a load and is used for realizing voltage conversion and bidirectional energy transmission between the power supply and the load;
the sampling circuit is connected with one end, close to the load, of the staggered parallel bidirectional buck/boost converter and is used for collecting the load end voltage of the staggered parallel bidirectional buck/boost converter;
the control circuit is connected with the sampling circuit and used for comparing the load end voltage of the staggered parallel bidirectional buck/boost converter with a preset threshold value and generating square wave pulse control voltage according to a comparison result;
the driving circuit is connected between the control circuit and the staggered parallel bidirectional buck/boost converter and is used for amplifying the square-wave pulse control voltage generated by the control circuit and transmitting the amplified square-wave pulse control voltage to a switching tube in the staggered parallel bidirectional buck/boost converter;
and the switching tube in the staggered parallel connection type bidirectional buck/boost converter is switched on and off based on a voltage hysteresis control algorithm.
In one embodiment of the invention, the preset threshold comprises a set boost low-pressure given value, a boost high-pressure given value, a buck low-pressure given value and a buck high-pressure given value.
In an embodiment of the present invention, the voltage hysteresis control algorithm specifically includes:
when the voltage value of the load end collected by the sampling circuit is smaller than the given value of the boost low voltage, controlling the staggered parallel bidirectional buck/boost converter to work in a boost mode, so that the power supply supplies power to the load;
when the voltage value of the load terminal is larger than the given value of the boost high voltage, controlling the boost mode to be terminated so that the power supply stops supplying power to the load;
when the voltage value of the load terminal is larger than the buck high-voltage given value, controlling the staggered parallel bidirectional buck/boost converter to enter a buck mode, so that the load discharges;
when the voltage value of the load end is smaller than the buck low-voltage given value, controlling the buck mode to be terminated, and enabling the load to stop discharging;
when the voltage value of the load terminal is between the given value of the boost low voltage and the given value of the buck high voltage, the staggered parallel bidirectional buck/boost converter keeps the current state.
In an embodiment of the present invention, the driving circuit includes a first output terminal, a second output terminal, a third output terminal and a fourth output terminal of different switching tubes of the interleaved parallel bidirectional buck/boost converter, respectively, where the first output terminal and the second output terminal output two complementary pulse voltage signals, the third output terminal outputs a pulse voltage signal shifted by 180 ° from the first output terminal, and the fourth output terminal outputs a pulse voltage signal shifted by 180 ° from the second output terminal.
Compared with the prior art, the invention has the beneficial effects that:
1. the invention provides a high-efficiency pulse load power supply and a voltage hysteresis control method thereof. Firstly, enabling an interlaced parallel bidirectional buck/boost converter to work in a CRM (critical conduction) working mode; on the basis of reducing the system turn-on loss, the load end voltage is collected, a voltage hysteresis control algorithm is introduced, the load end voltage is compared with a preset threshold value, the aim of reducing turn-off loss to the maximum is achieved in a mode of minimizing the action times of a switching tube, the working efficiency of the staggered parallel bidirectional buck/boost converter is improved, and the effect in the field of pulse load is remarkable; secondly, based on a voltage hysteresis control method, energy bidirectional flow of the staggered parallel bidirectional buck/boost converter is achieved, and overvoltage of a load end caused by counter electromotive force or faults and the like is effectively restrained. It should be noted that, by adjusting the magnitude of the pre-threshold, the loop width of the voltage hysteresis control can be adjusted, so as to regulate and control the voltage ripple at the load end and the sensitivity of the system. The control method provided by the invention has strong applicability and is suitable for various switching power supply systems under various pulse loads.
2. By using the voltage hysteresis control method, under the application scenes of intermittent load, new energy charging and the like, when the charging of a new energy battery is finished, if the battery is in power shortage, the staggered parallel connection type bidirectional buck/boost converter works to provide energy for the battery; otherwise, the interleaved parallel bidirectional buck/boost converter is in a non-operating state, so that the switching loss of the interleaved parallel bidirectional buck/boost converter is obviously reduced. And, through reducing the action number of times of switch tube, improved the dead time and the life-span of component. And the function of protecting the storage battery is achieved in a reverse energy leakage mode.
The present invention will be described in further detail with reference to the accompanying drawings and examples.
Drawings
Fig. 1 is a flowchart of a voltage hysteresis control method of a high-efficiency pulse load power supply according to an embodiment of the present invention;
fig. 2 is a schematic diagram of a voltage hysteresis control process of a voltage hysteresis control method of a high-efficiency pulse load power supply according to an embodiment of the present invention;
fig. 3 is a schematic diagram of a voltage hysteresis control process in which a load is a pulse-type load according to an embodiment of the present invention;
FIG. 4 is a block diagram of a high efficiency pulsed load power supply according to an embodiment of the present invention;
FIG. 5 is a circuit diagram of a high efficiency pulsed load power supply according to an embodiment of the present invention;
FIG. 6 is a schematic diagram of a connection between a driving circuit and a control circuit according to an embodiment of the present invention;
FIG. 7 shows a switch tube (S) according to an embodiment of the present invention1And S3) The comparison of the drain-source voltage and the inductor current waveform;
FIG. 8 shows a driving voltage and a switching tube (S) under voltage hysteresis control according to an embodiment of the present invention1And S3) Drain-source voltage and negativeVoltage V at carrier0A schematic comparison of (a);
fig. 9 is a graph comparing the efficiency of the voltage hysteresis control provided by the embodiment of the present invention and the efficiency of the conventional PI control.
Detailed Description
In order to further explain the technical means and effects of the present invention adopted to achieve the predetermined object, the following detailed description is made in conjunction with the accompanying drawings and the detailed description to describe an intermittent new energy power supply system and method based on voltage hysteresis control according to the present invention.
The foregoing and other technical matters, features and effects of the present invention will be apparent from the following detailed description of the embodiments, which is to be read in connection with the accompanying drawings. The technical means and effects of the present invention adopted to achieve the predetermined purpose can be more deeply and specifically understood through the description of the specific embodiments, however, the attached drawings are provided for reference and description only and are not used for limiting the technical scheme of the present invention.
It is noted that, herein, relational terms such as first and second, and the like may be used solely to distinguish one entity or action from another entity or action without necessarily requiring or implying any actual such relationship or order between such entities or actions. Also, the terms "comprises," "comprising," or any other variation thereof, are intended to cover a non-exclusive inclusion, such that an article or device that comprises a list of elements does not include only those elements but may include other elements not expressly listed. Without further limitation, an element defined by the phrase "comprising an … …" does not exclude the presence of additional like elements in the article or device comprising the element.
Example one
Referring to fig. 1, fig. 1 is a flowchart of a voltage hysteresis control method of a high-efficiency pulse load power supply according to an embodiment of the present invention. The voltage hysteresis control method comprises the following steps:
s1: acquiring the load terminal voltage of a staggered parallel bidirectional buck/boost converter connected between a power supply and a load by using a sampling circuit;
s2: comparing the load terminal voltage of the staggered parallel bidirectional buck/boost converter with a preset boost low-voltage given value, a boost high-voltage given value, a buck low-voltage given value and a buck high-voltage given value, and generating corresponding square wave pulse control voltage according to the comparison result;
s3: and amplifying the square wave pulse control voltage and transmitting the amplified square wave pulse control voltage to a switch tube in the staggered parallel connection type bidirectional buck/boost converter so as to control the on-off of the switch tube by using a voltage hysteresis control algorithm.
Further, before the S1, the method further includes:
and presetting and adjusting a boost low-voltage given value, a boost high-voltage given value, a buck low-voltage given value and a buck high-voltage given value of the staggered parallel bidirectional buck/boost converter so as to adjust the ring width of voltage hysteresis control.
It should be noted that the loop width of hysteresis control can be adjusted by adjusting preset boost low-voltage given value, boost high-voltage given value, buck low-voltage given value and buck high-voltage given value, so as to adjust the load end voltage ripple and the sensitivity of the system.
The interleaved parallel bidirectional Buck/Boost converter is a two-phase interleaved parallel bidirectional Buck/Boost converter, 2 completely identical Buck/Boost circuits are connected in parallel, and the power borne by each phase is reduced to one half of that of a traditional Buck/Boost circuit, so that a larger space is brought to the type selection of devices, and the inductance value and the inductance volume can be reduced; when the two-phase circuit works, the two-phase circuit is conducted in a staggered mode at a phase difference of 180 degrees.
According to the characteristics of the staggered parallel connection type bidirectional buck/boost converter, the zero current switching-on of the switching tube can be realized through reasonable circuit parameters, so that the volume of a magnetic element is reduced, and the power density and the efficiency of a system are improved; the total inductive current ripple of the system is reduced to the maximum extent in a two-phase 180-degree staggered parallel mode; in a synchronous rectification mode, complementary pulse voltage is applied to the two switching tubes of the same phase, zero voltage switching-on of the upper tube is realized, and reverse recovery time of a body diode of the upper tube is shortened, so that on-state loss of a system is reduced; by adopting the novel SiC device, the system is high in frequency, the volume of the magnetic element is reduced, and the power density of the system is improved.
Further, referring to fig. 2, fig. 2 is a schematic diagram of a voltage hysteresis control process of a voltage hysteresis control method of a high-efficiency pulse load power supply according to an embodiment of the present invention. The method for controlling the on-off of the switching tube by using a voltage hysteresis control algorithm comprises the following steps:
when the collected load end voltage value is smaller than the boost low-voltage given value, the staggered parallel connection type bidirectional buck/boost converter works in a boost mode, so that a power supply supplies power to a load;
when the voltage value of the load terminal is larger than the given value of the boost high voltage, the boost mode is terminated, so that the power supply stops supplying power to the load;
when the voltage value of the load terminal is larger than the buck high-voltage given value, the staggered parallel bidirectional buck/boost converter enters a buck mode, so that the load discharges;
when the voltage value of the load end is smaller than the buck low-voltage given value, the buck mode is terminated, so that the load stops discharging;
when the voltage value of the load end is between the boost low-voltage given value and the buck high-voltage given value, the switch tube keeps the current state.
The load of this embodiment is a pulse type load. Referring to fig. 3, when the load is a pulse-type load, once the voltage value of the load terminal is lower than the boost low-voltage given value, the boost mode is turned on, and the power supply supplies energy to the pulse load through the interleaved parallel bidirectional buck/boost converter; ending the boost mode until the voltage of the load terminal reaches the boost high-voltage given value; and the square wave pulse voltage between the grid source electrode and the source electrode of the switching tube at other moments is zero, namely the switching tube is closed. The frequency of the switching tube action depends on the frequency of the pulse load, and it should be noted that the lower the frequency of the pulse load, the fewer the times of the switching tube action, that is, the smaller the switching loss, and the higher the working efficiency of the interleaved parallel bidirectional buck/boost converter.
The embodiment provides a voltage hysteresis control method of a high-efficiency pulse load power supply, and a system for executing the method comprises an interleaved parallel bidirectional buck/boost converter hardware system architecture and a DSP-based voltage hysteresis software control algorithm. Firstly, enabling an interlaced parallel bidirectional buck/boost converter to work in a CRM (critical conduction) working mode; on the basis of reducing the system turn-on loss, the load end voltage is collected, a voltage hysteresis control algorithm is introduced, the load end voltage is compared with a preset threshold value, the aim of reducing turn-off loss to the maximum is achieved in a mode of minimizing the action times of a switching tube, the working efficiency of the staggered parallel bidirectional buck/boost converter is improved, and the effect in the field of pulse load is remarkable; secondly, based on a voltage hysteresis control method, energy bidirectional flow of the staggered parallel bidirectional buck/boost converter is achieved, and overvoltage of a load end caused by counter electromotive force or faults and the like is effectively restrained. It should be noted that, by adjusting the magnitude of the pre-threshold, the loop width of the voltage hysteresis control can be adjusted, so as to regulate and control the voltage ripple at the load end and the sensitivity of the system. The control method provided by the invention has strong applicability and is suitable for various switching power supply systems under various pulse loads.
Example two
On the basis of the above embodiments, the present embodiment provides a high-efficiency pulse load power supply. Referring to fig. 4, fig. 4 is a block diagram of a high-efficiency pulse load power supply according to an embodiment of the present invention. The intermittent new energy power supply system comprises a staggered parallel type bidirectional buck/boost converter 1, a driving circuit 2, a sampling circuit 3 and a control circuit 4, wherein the staggered parallel type bidirectional buck/boost converter 1 is connected between a power supply 5 and a load 6 and is used for realizing voltage conversion and bidirectional energy transmission between the power supply 5 and the load 6; the sampling circuit 3 is connected with one end, close to the load 6, of the staggered parallel bidirectional buck/boost converter 1 and used for collecting the load end voltage of the staggered parallel bidirectional buck/boost converter 1; the control circuit 4 is connected with the sampling circuit 3 and used for comparing the load end voltage of the staggered parallel bidirectional buck/boost converter 1 with a preset threshold value and generating square wave pulse control voltage according to the comparison result; the driving circuit 2 is connected between the control circuit 4 and the interleaved parallel bidirectional buck/boost converter 1, and is used for amplifying the square-wave pulse control voltage generated by the control circuit 4 and transmitting the amplified square-wave pulse control voltage to the switching tube in the interleaved parallel bidirectional buck/boost converter 1 so as to control the on-off of the switching tube by using a voltage hysteresis control algorithm.
In this embodiment, the preset threshold includes a given boost low-pressure value, a given boost high-pressure value, a given buck low-pressure value, and a given buck high-pressure value.
The voltage hysteresis control algorithm of the present embodiment specifically includes:
when the voltage value of the load end collected by the sampling circuit 3 is smaller than the given value of the boost low voltage, the staggered parallel bidirectional buck/boost converter 1 is controlled to work in the boost mode, so that the power supply 5 supplies power to the load 6; when the voltage value of the load end is larger than the given value of the boost high voltage, the boost mode is terminated, so that the power supply 5 stops supplying power to the load 6; when the voltage value of the load end is larger than the buck high-voltage given value, controlling the staggered parallel bidirectional buck/boost converter 1 to enter a buck mode to enable the load 6 to discharge; when the voltage value of the load end is smaller than the buck low-voltage given value, the buck mode is terminated, and the load 6 stops discharging; when the voltage value of the load end is between the given value of boost low voltage and the given value of buck high voltage, the staggered parallel bidirectional buck/boost converter 1 keeps the current state.
Further, referring to fig. 5, fig. 5 is a circuit diagram of a high-efficiency pulse load power supply according to an embodiment of the present invention. The interleaved parallel bidirectional buck/boost converter 1 of the present embodiment includes a first capacitor C1A second capacitor C2A first inductor L1A second inductor L2A first MOS transistor S1A second MOS transistor S2And the third MOS transistor S3And the fourth MOS transistor S4A first parasitic diode D1A second parasitic diode D2A third parasitic diode D3And a fourth parasitic diode D4Wherein, in the step (A),
a first capacitor C1A second capacitor C connected between the output terminal of the power supply 5 and the ground terminal GND2Connected between the load 6 and the ground GND;
first MOS transistor S1Is connected to a first output terminal of the driving circuit 2, a first MOS transistor S1The source electrode of the first MOS transistor S is connected with a grounding terminal1Is connected with the second MOS tube S2Source electrode of (1), third MOS transistor S3Is connected to a third output terminal of the driving circuit 2, a third MOS transistor S3The source electrode of the first MOS transistor S is connected with a grounding end, and the third MOS transistor S3Is connected with the fourth MOS tube S4A source electrode of (a);
second MOS transistor S2Is connected to a second output terminal of the driving circuit 2, a second MOS transistor S2Is connected with a load 6, a fourth MOS transistor S4Is connected to the fourth output terminal of the driving module 2, and a fourth MOS transistor S4Is connected with a load 6;
first parasitic diode D1The anode of the first MOS tube S is connected with the first MOS tube S1The first parasitic diode D2The negative electrode of the first MOS tube S is connected with the first MOS tube S1The drain electrode of (D), the second parasitic diode D2The anode of the first MOS tube is connected with a second MOS tube S2Source electrode of the second parasitic diode D2The negative pole of the first MOS tube is connected with the second MOS tube S2The drain electrode of (D), the third parasitic diode D3The anode of the first MOS tube is connected with a third MOS tube S3Source electrode of (1), third parasitic diode D3Negative pole of the first MOS transistor is connected with a third MOS transistor S3The fourth parasitic diode D4The anode of the first MOS tube is connected with a fourth MOS tube S4Source electrode of (1), fourth parasitic diode D4Negative pole of the first MOS transistor S is connected with a fourth MOS transistor S4A drain electrode of (1);
first inductance L1Is connected to the power supply 5, and the other end is connected to the second MOS transistor S2Source electrode of, the second inductance L2Is connected to the power supply 5, and the other end is connected to the fourth MOS transistor S4Of the substrate.
Further, the first output end and the second output end of the driving circuit 2 are used for outputting two paths of complementary pulse voltage signals, so as to respectively drive the first MOS transistor S1And a second MOS transistor S2(ii) a Meanwhile, the third output end is used for outputting the pulse voltage which is shifted by 180 degrees by the first output end, and the fourth output end is used for outputting the pulse voltage which is shifted by 180 degrees by the second output endThe pulse voltage after DEG is used for driving the third MOS transistor S respectively3And a fourth MOS transistor S4。
It should be noted that the interleaved parallel bidirectional Buck/Boost converter 1 of the present embodiment is a two-phase interleaved parallel bidirectional Buck/Boost converter, and is formed by connecting 2 identical Buck/Boost circuits in parallel, wherein the first MOS transistor S is connected in parallel1A second MOS transistor S2And a first inductance L1Forming a third MOS transistor S3And the fourth MOS transistor S4And a second inductance L2The second phase is formed, so that the power borne by each phase is reduced to one half of that of a conventional Buck/Boost circuit, a larger space is brought to the type selection of devices, and the inductance value and the inductance volume can be reduced; when the two-phase circuit works, the two-phase circuit is conducted in a staggered mode at a phase difference of 180 degrees.
According to the characteristics of the staggered parallel connection type bidirectional buck/boost converter, the zero current switching-on of the switching tube can be realized through reasonable circuit parameters, so that the volume of a magnetic element is reduced, and the power density and the efficiency of a system are improved; the total inductive current ripple of the system is reduced to the maximum extent in a two-phase 180-degree staggered parallel mode; in a synchronous rectification mode, complementary pulse voltage is applied to the two switching tubes of the same phase, zero voltage switching-on of the upper tube is realized, and reverse recovery time of a body diode of the upper tube is shortened, so that on-state loss of a system is reduced; by adopting the novel SiC device, the system is high in frequency, the volume of the magnetic element is reduced, and the power density of the system is improved.
In this embodiment, the control circuit 4 is specifically composed of a DSP F28335 control chip, a peripheral power supply circuit thereof, an ePWM peripheral module, an ADC peripheral module, and the like. The DSP F28335 controls the interleaved parallel bidirectional buck/boost converter, and the voltage hysteresis control process is realized through C language codes. Further, the boost low pressure given value, the boost high pressure given value, the buck low pressure given value, and the buck high pressure given value may be preset and stored.
The driving circuit 2 of the present embodiment specifically comprises a Si8275 driving chip, an isolation power supply module and peripheral circuits thereof, wherein the Si8275 driving chip is mainly responsible for modulating and amplifying a square wave pulse control signal output by a DSP F28335 control chip to generate pulses required by a switching tube, and the isolation power supply module is mainly responsible for supplying power to each output of the driving chip and providing an isolation function, so that the isolation power supply module can be used for driving a high-side MOSFET; the peripheral circuit mainly comprises a driving resistor, a bypass capacitor and the like. In other embodiments, the driving circuit 2 and the control circuit 4 may also be other suitable circuits or modules capable of realizing the corresponding functions.
Referring to fig. 6, fig. 6 is a schematic connection diagram of a driving circuit and a control circuit according to an embodiment of the present invention. Because the switch tube selects the MOS tube, the control form selects the voltage type control, and in order to improve the output stability, a closed loop feedback loop is selected to be set up to control the switch tube. DSP F28335 is complete in inside function, can write through the procedure and accomplish a series of functions such as closed loop PI control, PWM pulse width modulation to the system, has saved a large amount of volumes, nevertheless because the voltage value of DSP F28335 output is not enough to drive the MOS pipe: the output voltage of the DSP F28335 is 3.3V at most, and the MOS tube generally needs to be driven by a grid electrode of 10V to 15V, so the voltage of a PWM wave must be increased to drive the MOS tube, and finally a Si8275 programmable MOS drive chip is selected. Referring to the data manual, the input side VDD voltage range requires 2.5-5.5V, the output side VDDA and VDDB power supply voltages must be between 4.2-30V, and the input side and output side bypass capacitors of the Si8275 driver chip help reduce high frequency noise and improve performance. The two drive outputs are independent of each other, so the polarity of the relative voltages of VOA and VOB can be opposite, i.e. the voltage of VOA can be higher or lower than the voltage of VOB. In the invention, four switching tubes need to be driven, and each driving chip only has two paths of outputs, namely, each driving chip can only drive two switching tubes, so that two Si8275 driving chips need to be provided to drive the four switching tubes. In this embodiment, as shown in fig. 6, the VOA terminal of the Si8275 driver chip is connected to the second MOS transistor S2The VOB end is connected with a first MOS tube S through a NOT gate1To respectively drive the first MOS transistor S1And a second MOS transistor S2And the VOA terminal and the VOB terminal output two complementary pulse voltage signals. Similarly, in anotherIn the driving chip, the VOA end is connected with a fourth MOS tube S4The VOB end is connected with a third MOS tube S through a NOT gate3To respectively control the third MOS transistor S3And a fourth MOS transistor S4On and off. It should be noted that, one DSP F28335 control chip is connected to two Si8275 driver chips at the same time.
The sampling circuit 3 of the present embodiment may be any suitable sampling circuit or module, and is not limited herein.
Preferably, the power source 5 is a dc power source and the load 6 is a battery or a pulse type load. When the load is a storage battery, if the storage battery needs to be charged, the staggered parallel connection type bidirectional buck/boost converter works normally to provide energy for the storage battery and stops when the storage battery is fully charged; when the storage battery is in power shortage, the converter is started again to supplement energy for the storage battery; at other moments, the converter does not work, so that the switching loss caused by continuous work is greatly reduced, and the average power of the system is improved. In addition, the staggered parallel connection type bidirectional buck/boost converter in the intermittent new energy power supply system has a reverse energy transmission function, and when the terminal voltage of the storage battery is overhigh due to the counter electromotive force or short circuit and other reasons of a load, the storage battery can discharge energy reversely through the converter, so that the storage battery is protected.
It should be noted that, according to the parameter design of the system, the system operates in CRM (critical conduction) operation mode. The number of the interleaved parallel phases of the interleaved parallel bidirectional buck/boost converter 1 of the embodiment is two, and when the duty ratio is 50%, the ripple peak values of the inductive currents of the system can be mutually offset, and the theoretical value of the total ripple is 0. Preferably, when the first inductance L is1And a second inductance L2When the inductance value is 68uH, the interleaved parallel bidirectional buck/boost converter 1 works in CRM mode, i.e. the switch tube S1And S3Zero current switching-on is realized, and the switching-on loss is reduced. By calculation, the capacitance C1And C2The capacitance value is 10uF, the volume is extremely small, and the effect of increasing the power density of the system is obvious.
Further, referring to fig. 7, fig. 7 is a switch tube (S) according to an embodiment of the present invention1And S3) Drain-source voltage ofThe diagram is compared with the inductive current waveform, wherein the abscissa represents time, and the drain-source voltage is the first MOS transistor S1With a drain-source voltage of L and an inductor current of L1The current of (2). In this embodiment, the first MOS transistor S1Before the switching-on, the current of the MOS tube is already reduced to 0, namely the MOS tube realizes the zero current switching-on; similarly, the third MOS transistor S3Zero current turn-on is also achieved. Thereby reducing the first MOS transistor S1And a third MOS transistor S3The switching loss of the system is improved, and the working efficiency of the system is improved. It can be seen that the system has the advantages that through reasonable design, the volume of the magnetic element is extremely small, and therefore the power density of the system is improved.
Referring to fig. 8, fig. 8 shows a driving voltage and a load terminal voltage V under voltage hysteresis control according to an embodiment of the present invention0Wherein, the abscissa represents time, the driving voltage is the output voltage of the driving circuit, and the drain-source voltage is the first MOS transistor S1And a third MOS transistor S3The output voltage of the drain-source voltage is the output voltage of the interleaved parallel bidirectional buck/boost converter 1, namely the load terminal voltage. It is easy to find that the control mode significantly reduces the number of switching tube actions compared to the conventional PI closed-loop control mode, thereby reducing the switching loss of the system. As can be seen from fig. 8, in this control mode, there are two phases of circuit operation and non-operation within one cycle. Taking a Boost working mode as an example, in a working stage, the circuit is started, the voltage hysteresis control works, the control signals are subjected to PWM modulation, two paths of control signals are kept complementary, and at the moment, the circuit is boosted. When the voltage rises to the upper limit of the Boost mode, the system stops the output of the PWM pulse voltage, so that the power supply supplies power to the load, and when the voltage drops to the lower limit of the Boost mode, the control circuit is restarted, and the process is repeated.
Further, referring to fig. 9, fig. 9 is a graph comparing efficiency of the voltage hysteresis control provided by the embodiment of the present invention and the conventional PI (proportional, integral) control. It is easy to see that, when the load is gradually reduced from a heavy load, the efficiency of the conventional PI control mode has a significant tendency to decrease, and thus the PI control mode is not suitable for the fields of intermittent load and the like. The voltage hysteresis control mode of the intermittent new energy power supply system provided by the embodiment has relatively stable efficiency, and particularly, the efficiency is gradually improved when the load is reduced, so that the intermittent new energy power supply system has important research significance in the fields of intermittent loads such as radar antennas and base station navigation, and in new energy scenes such as vehicle-mounted chargers and wind power generation.
The intermittent new energy power supply system adopts a voltage hysteresis double-position control mode, and the action times of a switch tube in the system are obviously reduced in the control mode, so that the switching loss of the system is reduced, and the system working efficiency is greatly improved. Under the application scenes of intermittent load, new energy charging and the like, when the charging of a new energy battery is finished, if the battery is in power shortage, the system works to provide energy for the storage battery; otherwise, the system is in a non-working state, which obviously reduces the switching loss of the system. And, through reducing the action number of times of switch tube, improved the dead time and the life-span of component. And the function of protecting the storage battery is achieved in a reverse energy leakage mode.
The foregoing is a more detailed description of the invention in connection with specific preferred embodiments and it is not intended that the invention be limited to these specific details. For those skilled in the art to which the invention pertains, several simple deductions or substitutions can be made without departing from the spirit of the invention, and all shall be considered as belonging to the protection scope of the invention.
Claims (9)
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