CN113746430A - Signal processing method and device - Google Patents
Signal processing method and device Download PDFInfo
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- CN113746430A CN113746430A CN202110992518.8A CN202110992518A CN113746430A CN 113746430 A CN113746430 A CN 113746430A CN 202110992518 A CN202110992518 A CN 202110992518A CN 113746430 A CN113746430 A CN 113746430A
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- 238000005070 sampling Methods 0.000 claims abstract description 62
- 238000001914 filtration Methods 0.000 claims abstract description 42
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- 230000003111 delayed effect Effects 0.000 claims abstract description 15
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03D—DEMODULATION OR TRANSFERENCE OF MODULATION FROM ONE CARRIER TO ANOTHER
- H03D7/00—Transference of modulation from one carrier to another, e.g. frequency-changing
- H03D7/16—Multiple-frequency-changing
- H03D7/165—Multiple-frequency-changing at least two frequency changers being located in different paths, e.g. in two paths with carriers in quadrature
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
- H03H17/00—Networks using digital techniques
- H03H17/02—Frequency selective networks
- H03H17/06—Non-recursive filters
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
- H03H17/00—Networks using digital techniques
- H03H2017/0072—Theoretical filter design
- H03H2017/0081—Theoretical filter design of FIR filters
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Abstract
The application discloses a signal processing method and a signal processing device, which relate to the technical field of signal processing, wherein the method comprises the following steps: acquiring sampling data of a zero intermediate frequency orthogonal analog signal; performing digital interpolation on the sampling data, and filtering the interpolated sampling data; carrying out complex frequency mixing on the filtered sampling data, carrying out Hilbert filtering on a Q branch signal, and carrying out delay filtering of the same order on an I branch; and determining a real signal according to the filtered Q branch signal and the delayed I branch signal, and outputting the real signal. The problem that in the prior art, an analog band-pass filter cannot be integrated in a new radio frequency band and therefore a plurality of scenes cannot be used is solved, and the effect that a corresponding real signal can be output without the integrated band-pass filter is achieved.
Description
Technical Field
The invention relates to a signal processing method and a signal processing device, and belongs to the technical field of signal processing.
Background
The existing high-integration radio frequency chip integrated with analog-to-digital conversion usually adopts a zero intermediate frequency quadrature sampling scheme. The advantages are obvious when the butt-jointed baseband processing unit adopts a Programmable logic Gate Array (FPGA). However, when the existing baseband dedicated processing chip based on the real signal sampling scheme is docked, the interface signal definition is not matched, and the interface signal cannot be directly used. And when a low-intermediate frequency sampling scheme is adopted, the problem that an analog band-pass filter is difficult to integrate in a radio frequency chip exists.
Disclosure of Invention
The present invention is directed to a signal processing method and apparatus, which are used to solve the problems in the prior art.
In order to achieve the purpose, the invention provides the following technical scheme:
according to a first aspect, an embodiment of the present invention provides a signal processing method, including:
acquiring sampling data of a zero intermediate frequency orthogonal analog signal;
performing digital interpolation on the sampling data, and filtering the interpolated sampling data;
carrying out complex frequency mixing on the filtered sampling data, carrying out Hilbert filtering on a Q branch signal, and carrying out delay filtering of the same order on an I branch;
and determining a real signal according to the filtered Q branch signal and the delayed I branch signal, and outputting the real signal.
Optionally, the interpolation rate for digitally interpolating the sampled data is determined by a ratio of a real signal sampling rate to a complex signal sampling rate.
Optionally, the interpolated sampling data includes:
wherein x isI(k) K is 0,1,2, … … isIn-phase branch data, x, of the sampled dataQ(k) And k is 0,1,2, … … is quadrature branch data in the acquired sample data, and L is the ratio of the real signal sampling rate to the complex signal sampling rate.
Optionally, the filtering the interpolated sample data includes:
and filtering the in-phase branch and the quadrature branch in the interpolated sampling data through the same filter.
Optionally, the filtering the in-phase branch and the quadrature branch in the interpolated sample data through the same filter includes:
where h (k) is the coefficient of the filter.
Optionally, the filter is an N-order FIR filter, and N is greater than a preset threshold.
Optionally, the filter includes a multiplier and an adder.
Optionally, the determining a real signal according to the filtered Q branch signal and the delayed I branch signal includes:
and determining the sum of the filtered Q branch signal and the delayed I branch signal as the real signal.
In a second aspect, there is provided a signal processing apparatus comprising a memory having at least one program instruction stored therein and a processor for implementing the method according to the first aspect by loading and executing the at least one program instruction.
In a third aspect, there is provided a signal processing apparatus, the apparatus comprising:
the data acquisition submodule is used for acquiring sampling data of the zero intermediate frequency orthogonal analog signal;
a digital interpolation sub-module for digitally interpolating the sampled data;
the digital filtering submodule is used for filtering the interpolated sampling data;
the complex frequency mixing submodule is used for carrying out complex frequency mixing on the filtered sampling data;
the phase rotation submodule is used for carrying out Hilbert filtering on the Q branch signal, and the I branch carries out delay filtering with the same order;
and the data superposition submodule is used for determining a real signal according to the filtered Q branch signal and the delayed I branch signal and outputting the real signal.
Acquiring sampling data of a zero intermediate frequency orthogonal analog signal; performing digital interpolation on the sampling data, and filtering the interpolated sampling data; carrying out complex frequency mixing on the filtered sampling data, carrying out Hilbert filtering on a Q branch signal, and carrying out delay filtering of the same order on an I branch; and determining a real signal according to the filtered Q branch signal and the delayed I branch signal, and outputting the real signal. The signal characteristics of the processed signal are the same as those of a signal obtained by sampling a real signal after a large-size analog band-pass filter is adopted in the existing scheme, so that the problem that a plurality of scenes cannot be used due to the fact that the analog band-pass filter cannot be integrated in a radio frequency new band in the prior art is solved, and the effect that the corresponding real signal can be output without the integrated band-pass filter is achieved.
The foregoing description is only an overview of the technical solutions of the present invention, and in order to make the technical solutions of the present invention more clearly understood and to implement them in accordance with the contents of the description, the following detailed description is given with reference to the preferred embodiments of the present invention and the accompanying drawings.
Drawings
Fig. 1 is a flowchart of a method of signal processing according to an embodiment of the present invention;
fig. 2 is a schematic diagram of a possible implementation of zero-if quadrature sampling according to an embodiment of the present invention;
FIG. 3 is a flow chart of one possible workflow provided by one embodiment of the present invention;
fig. 4 is a schematic structural diagram of a signal processing apparatus according to an embodiment of the present invention.
Detailed Description
The technical solutions of the present invention will be described clearly and completely with reference to the accompanying drawings, and it should be understood that the described embodiments are some, but not all embodiments of the present invention. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
In the description of the present invention, it should be noted that the terms "center", "upper", "lower", "left", "right", "vertical", "horizontal", "inner", "outer", etc., indicate orientations or positional relationships based on the orientations or positional relationships shown in the drawings, and are only for convenience of description and simplicity of description, but do not indicate or imply that the device or element being referred to must have a particular orientation, be constructed and operated in a particular orientation, and thus, should not be construed as limiting the present invention. Furthermore, the terms "first," "second," and "third" are used for descriptive purposes only and are not to be construed as indicating or implying relative importance.
In the description of the present invention, it should be noted that, unless otherwise explicitly specified or limited, the terms "mounted," "connected," and "connected" are to be construed broadly, e.g., as meaning either a fixed connection, a removable connection, or an integral connection; can be mechanically or electrically connected; they may be connected directly or indirectly through intervening media, or they may be interconnected between two elements. The specific meanings of the above terms in the present invention can be understood in specific cases to those skilled in the art.
In addition, the technical features involved in the different embodiments of the present invention described below may be combined with each other as long as they do not conflict with each other.
Referring to fig. 1, a flowchart of a method of processing a signal according to an embodiment of the present application is shown, where as shown in fig. 1, the method includes:
referring to fig. 2, a schematic diagram of a possible implementation of zero intermediate frequency quadrature sampling is shown. As can be seen from FIG. 2, the in-phase branch x of the sampled data can be obtainedI(k) K is 0,1,2, … …, and the quadrature branch x of the sampled dataQ(k),k＝0,1,2,……。
102, performing digital interpolation on the sampling data, and filtering the interpolated sampling data;
the interpolation rate for digitally interpolating the sampled data is determined by the ratio of the real signal sampling rate to the complex signal sampling rate, and in practical implementations, the ratio is usually an integer, i.e., the sampled data is interpolated by an integer multiple.
The interpolated sample data comprises:
wherein x isI(k) Where k is 0,1,2, … … denotes in-phase branch data in the acquired sample data, and x denotesQ(k) And k is 0,1,2, … … is quadrature branch data in the acquired sample data, and L is the ratio of the real signal sampling rate to the complex signal sampling rate.
After interpolation is carried out on the sampling data, an in-phase branch and a quadrature branch in the sampling data after interpolation are filtered through the same filter. Wherein the performance of the filter depends on the filter coefficients. In practical implementation, the filter may be an N-order finite impulse response FIR filter, where N is greater than a preset threshold, that is, a high-order finite impulse response FIR filter is used. In addition, in digital signal processing, the filter may be implemented by a multiplier and an adder.
In one possible embodiment, exemplified by filtering using an N-th order FIR filter, the filtered sample data is:
where h (k) is the coefficient of the filter.
103, performing complex frequency mixing on the filtered sampling data, performing Hilbert filtering on a Q branch signal, and performing same-order delay filtering on an I branch;
in practical implementation, complex mixing may be performed by a digital NCO (numerically controlled oscillator), where a digital local oscillator may be flexibly changed by a configuration control word.
And step 104, determining a real signal according to the filtered Q branch signal and the delayed I branch signal, and outputting the real signal.
Optionally, the sum of the filtered Q branch signal and the delayed I branch signal is determined as the real signal.
Referring to fig. 3, in one possible embodiment, after the sample data is obtained, the sample data is sequentially subjected to interpolation, FIR filter, complex mixing, and then delay filtering and hilbert filtering, and then the filtered signals are superimposed to obtain a final real signal.
In summary, sampling data of the zero intermediate frequency orthogonal analog signal is acquired; performing digital interpolation on the sampling data, and filtering the interpolated sampling data; carrying out complex frequency mixing on the filtered sampling data, carrying out Hilbert filtering on a Q branch signal, and carrying out delay filtering of the same order on an I branch; and determining a real signal according to the filtered Q branch signal and the delayed I branch signal, and outputting the real signal. The signal characteristics of the processed signal are the same as those of a signal obtained by sampling a real signal after a large-size analog band-pass filter is adopted in the existing scheme, so that the problem that a plurality of scenes cannot be used due to the fact that the analog band-pass filter cannot be integrated in a radio frequency new band in the prior art is solved, and the effect that the corresponding real signal can be output without the integrated band-pass filter is achieved.
The present application also provides a signal processing apparatus comprising a memory having at least one program instruction stored therein and a processor that implements the method as described above by loading and executing the at least one program instruction.
Referring to fig. 4, a schematic structural diagram of a signal processing apparatus provided in the present application is shown, and as shown in fig. 4, the apparatus includes:
the data acquisition submodule is used for acquiring sampling data of the zero intermediate frequency orthogonal analog signal;
a digital interpolation sub-module for digitally interpolating the sampled data;
the digital filtering submodule is used for filtering the interpolated sampling data;
the complex frequency mixing submodule is used for carrying out complex frequency mixing on the filtered sampling data;
the phase rotation submodule is used for carrying out Hilbert filtering on the Q branch signal, and the I branch carries out delay filtering with the same order;
and the data superposition submodule is used for determining a real signal according to the filtered Q branch signal and the delayed I branch signal and outputting the real signal.
In summary, sampling data of the zero intermediate frequency orthogonal analog signal is acquired; performing digital interpolation on the sampling data, and filtering the interpolated sampling data; carrying out complex frequency mixing on the filtered sampling data, carrying out Hilbert filtering on a Q branch signal, and carrying out delay filtering of the same order on an I branch; and determining a real signal according to the filtered Q branch signal and the delayed I branch signal, and outputting the real signal. The signal characteristics of the processed signal are the same as those of a signal obtained by sampling a real signal after a large-size analog band-pass filter is adopted in the existing scheme, so that the problem that a plurality of scenes cannot be used due to the fact that the analog band-pass filter cannot be integrated in a radio frequency new band in the prior art is solved, and the effect that the corresponding real signal can be output without the integrated band-pass filter is achieved.
The technical features of the embodiments described above may be arbitrarily combined, and for the sake of brevity, all possible combinations of the technical features in the embodiments described above are not described, but should be considered as being within the scope of the present specification as long as there is no contradiction between the combinations of the technical features.
The above-mentioned embodiments only express several embodiments of the present invention, and the description thereof is more specific and detailed, but not construed as limiting the scope of the invention. It should be noted that, for a person skilled in the art, several variations and modifications can be made without departing from the inventive concept, which falls within the scope of the present invention. Therefore, the protection scope of the present patent shall be subject to the appended claims.
Claims (10)
1. A method of signal processing, the method comprising:
acquiring sampling data of a zero intermediate frequency orthogonal analog signal;
performing digital interpolation on the sampling data, and filtering the interpolated sampling data;
carrying out complex frequency mixing on the filtered sampling data, carrying out Hilbert filtering on a Q branch signal, and carrying out delay filtering of the same order on an I branch;
and determining a real signal according to the filtered Q branch signal and the delayed I branch signal, and outputting the real signal.
2. The method of claim 1, wherein an interpolation rate for digitally interpolating the sampled data is determined by a ratio of a real signal sampling rate to a complex signal sampling rate.
3. The method of claim 2, wherein the interpolated sample data comprises:
wherein x isI(k) Where k is 0,1,2, … … denotes in-phase branch data in the acquired sample data, and x denotesQ(k) And k is 0,1,2, … … is quadrature branch data in the acquired sample data, and L is the ratio of the real signal sampling rate to the complex signal sampling rate.
4. The method of claim 3, wherein filtering the interpolated sample data comprises:
and filtering the in-phase branch and the quadrature branch in the interpolated sampling data through the same filter.
5. The method of claim 4, wherein the filtering the in-phase branch and the quadrature branch of the interpolated sample data through the same filter comprises:
where h (k) is the coefficient of the filter.
6. The method of claim 4, wherein the filter is an N-th order Finite Impulse Response (FIR) filter, and N is greater than a predetermined threshold.
7. The method of claim 4, wherein the filter comprises a multiplier and an adder.
8. The method according to any of claims 1 to 7, wherein determining the real signal from the filtered Q branch signal and the delayed I branch signal comprises:
and determining the sum of the filtered Q branch signal and the delayed I branch signal as the real signal.
9. A signal processing apparatus, comprising a memory having at least one program instruction stored therein and a processor, wherein the processor implements the method of any one of claims 1 to 8 by loading and executing the at least one program instruction.
10. A signal processing apparatus, characterized in that the apparatus comprises:
the data acquisition submodule is used for acquiring sampling data of the zero intermediate frequency orthogonal analog signal;
a digital interpolation sub-module for digitally interpolating the sampled data;
the digital filtering submodule is used for filtering the interpolated sampling data;
the complex frequency mixing submodule is used for carrying out complex frequency mixing on the filtered sampling data;
the phase rotation submodule is used for carrying out Hilbert filtering on the Q branch signal, and the I branch carries out delay filtering with the same order;
and the data superposition submodule is used for determining a real signal according to the filtered Q branch signal and the delayed I branch signal and outputting the real signal.
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Citations (8)
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|---|---|---|---|---|
| US5515402A (en) * | 1992-08-14 | 1996-05-07 | Harris Corporation | Quadrature filter with real conversion |
| US6459743B1 (en) * | 1998-08-07 | 2002-10-01 | Telefonaktiebolaget Lm Ericsson (Publ) | Digital reception with radio frequency sampling |
| CN101197606A (en) * | 2006-12-04 | 2008-06-11 | 京信通信技术(广州)有限公司 | Digital intermediate frequency conversion method and system used in repeater |
| US20090325518A1 (en) * | 2008-06-27 | 2009-12-31 | Sven Mattisson | Methods and Apparatus for Suppressing Strong-Signal Interference in Low-IF Receivers |
| CN102590794A (en) * | 2012-02-28 | 2012-07-18 | 北京航空航天大学 | Broadband coherent radar target simulator |
| US20140171009A1 (en) * | 2012-06-21 | 2014-06-19 | Huawei Technologies Co., Ltd. | Radio Frequency Receiver |
| CN104506161A (en) * | 2014-10-11 | 2015-04-08 | 中国电子科技集团公司第十研究所 | Fractional sampling rate conversion method for complex coefficient Hilbert band-pass filter |
| CN105375937A (en) * | 2015-11-11 | 2016-03-02 | 中国电子科技集团公司第四十一研究所 | Digital intermediate frequency variable bandwidth shaping filtering device and method |
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2021
- 2021-08-27 CN CN202110992518.8A patent/CN113746430A/en active Pending
Patent Citations (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5515402A (en) * | 1992-08-14 | 1996-05-07 | Harris Corporation | Quadrature filter with real conversion |
| US6459743B1 (en) * | 1998-08-07 | 2002-10-01 | Telefonaktiebolaget Lm Ericsson (Publ) | Digital reception with radio frequency sampling |
| CN101197606A (en) * | 2006-12-04 | 2008-06-11 | 京信通信技术(广州)有限公司 | Digital intermediate frequency conversion method and system used in repeater |
| US20090325518A1 (en) * | 2008-06-27 | 2009-12-31 | Sven Mattisson | Methods and Apparatus for Suppressing Strong-Signal Interference in Low-IF Receivers |
| CN102590794A (en) * | 2012-02-28 | 2012-07-18 | 北京航空航天大学 | Broadband coherent radar target simulator |
| US20140171009A1 (en) * | 2012-06-21 | 2014-06-19 | Huawei Technologies Co., Ltd. | Radio Frequency Receiver |
| CN104506161A (en) * | 2014-10-11 | 2015-04-08 | 中国电子科技集团公司第十研究所 | Fractional sampling rate conversion method for complex coefficient Hilbert band-pass filter |
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