CN113468850B - Non-isolated power supply electromagnetic radiation interference rapid prediction method - Google Patents

Non-isolated power supply electromagnetic radiation interference rapid prediction method Download PDF

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CN113468850B
CN113468850B CN202110683007.8A CN202110683007A CN113468850B CN 113468850 B CN113468850 B CN 113468850B CN 202110683007 A CN202110683007 A CN 202110683007A CN 113468850 B CN113468850 B CN 113468850B
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CN113468850A (en
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冯锟
管松敏
马宁
马惠
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CETC 14 Research Institute
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Abstract

The invention discloses a method for quickly predicting electromagnetic radiation interference of a non-isolated power supply, which comprises the following steps: step S1:under the condition that a non-isolated power supply is fully loaded, the waveform of a SW point nonlinear device in a time scale in a unit switching period is measured, and the amplitude-frequency characteristic V of the middle-frequency range noise is obtained Q1 And high and middle frequency band noise amplitude-frequency characteristic V Q2 (ii) a Step S2: establishing a transmission line four-port scattering model of the non-isolated power circuit, and step S3: establishing a transmission line two-port scattering model, and S4: and obtaining the non-isolated power supply scattering network according to the circuit four-port scattering model and the transmission line two-port impedance model. The method for quickly predicting the electromagnetic radiation interference of the non-isolated power supply can accurately predict the electromagnetic radiation interference intensity of the noise of the non-isolated power supply through the cable under the condition of only using an oscilloscope and a vector network analyzer.

Description

Non-isolated power supply electromagnetic radiation interference rapid prediction method
Technical Field
The invention relates to the field of switching power supplies, in particular to a method for quickly predicting electromagnetic radiation interference of a non-isolated power supply.
Background
The increasingly strong miniaturization demand of electronic products has pushed non-isolated power supplies (mainly buck-type buck converters and boost-type boost converters) to develop higher switching frequency and higher power density, and meanwhile, electromagnetic interference (EMI) with higher intensity is also brought. The electromagnetic interference is respectively electromagnetic conducted interference and electromagnetic radiation interference, wherein the electromagnetic radiation interference can be radiated to the surrounding space by the antenna effect of the input and output cable, so that the interference on a radio frequency circuit and a frequency source is caused, the distortion of communication signals and the abnormal work of a digital-analog circuit are caused, and even the health of a human body is harmed, so that the accurate test and the corresponding inhibition of the electromagnetic radiation interference have important significance for improving the overall performance of an electronic product.
Some international standards specify the qualitative and quantitative determination of electromagnetic radiation interference in different spatial scales, such as EN55022, EN55032, CISPR22 and CISPR25, and so on. The requirements of the standards on electromagnetic radiation interference are mainly in a frequency band of 30M-1G, and the radiation field intensity under different spatial scales from a noise source is limited. Meanwhile, a test method of electromagnetic radiation interference is specified, and the test tools are required to be a signal receiver (more than 1G), a frequency spectrograph (more than 1G), a microwave darkroom and a test antenna, wherein the specific test method is that in the microwave darkroom, a tested product rotates 360 degrees along with a test bench, the antenna is adjusted at different heights to search for the maximum radiation value, and the measurement unit of a test result is dBuV/m.
As can be seen from the test conditions and test methods specified by the international standard, the existing electromagnetic radiation interference test has the following disadvantages: requiring special test equipment, expensive testing, and special test sites, which are all inconvenient for product development.
Disclosure of Invention
In order to solve the above problems, the invention provides a method for quickly predicting electromagnetic radiation interference of a non-isolated power supply, where the non-isolated power supply includes a buck circuit and a boost circuit, the buck circuit of an input/output cable of the non-isolated power supply includes a first capacitor C1, a first noise source Q1, an inductor L and a second capacitor C2 which are located in series, a positive input node P1 is located between the first capacitor C1 and the first noise source Q1, a node M is located between the first noise source Q1 and the inductor L, a positive output node P2 is located between the inductor L and the second capacitor C2, a negative point N is located between the first capacitor C1 and the second capacitor C2, a second noise source Q2 is connected between a second port MN formed by the node M and the negative point N, two ends of the first capacitor C1 are connected in parallel with an input source Vin through an positive input cable and a negative input cable, and two ends of the second capacitor C2 are connected in parallel with a load through a positive output cable and a negative cable; the difference between the boost circuit of the input and output cable of the non-isolated power supply and the buck circuit of the input and output cable of the non-isolated power supply is that two ends of a second capacitor C2 of the boost circuit of the input and output cable of the non-isolated power supply are connected in parallel with an input source Vin through a positive input cable and a negative input cable, and two ends of a first capacitor C1 are connected in parallel with a load through a positive output cable and a negative output cable, and the method is characterized by comprising the following steps:
step S1: under the condition that a non-isolated power supply is fully loaded, the waveform of a SW point nonlinear device is measured in time scale in a unit switching period, and the amplitude-frequency characteristic V of the mid-frequency range noise is obtained Q1 Sum high and middle frequency band noise amplitude-frequency characteristic V Q2 ；
Step S2: establishing a transmission line four-port scattering model of a non-isolated power supply circuit, arranging four radio frequency interfaces at a first port P1M, a second port MN, a third port P1N and a fourth port P2N which are formed by a positive input node P1, a positive output node P2, a node M and a negative point N on the non-isolated power supply, connecting a test cable of a vector network analyzer to the four radio frequency interfaces on the non-isolated power supply, and measuring a reflection coefficient between every two ports
Figure BDA0003121332060000021
Wherein, a Am Indicating an incident wave from a negative pole point N to other nodes or an incident wave directed to positive pole input and output nodes P1 and P2, am indicating the number of the incident wave, and m =1,2,3,4; when m = n, b An Is represented by Am The corresponding reflected wave, an denotes the index to the reflected wave, n =1,2,3,4; namely a A1 Representing the incident wave, a, from the negative point N to the node M A2 Representing the incident wave, a, from node M to the positive input node P1 A3 Denotes the incident wave, a, from the negative point N to the positive output node P2 A4 Representing an incident wave from a negative point N to a positive input node P1; the buck circuit of the non-isolated power supply and the transmission cable four-port scattering model of the boost circuit are the same;
and step S3: establishing a two-port scattering model of the transmission line, keeping positive and negative cables of the transmission line parallel, respectively arranging radio frequency interfaces at a third port P1N and a fourth port P2N, and measuring a reflection coefficient between each two ports by using a vector network analyzer
Figure BDA0003121332060000022
Wherein, a Bp Indicating incident waves from a negative electrode point N to positive electrode input and output nodes P1 and P2, wherein Bp indicates the reference number of the incident waves, and P =1,2; when p = q, b Bq Is represented by a Bp Corresponding reflected waves, bq denotes the index to the reflected wave, q =1,2; namely a B1 Representing the incident wave, a, from node M to the positive output node P2 B2 Representing an incident wave from a negative point N to a positive input node P1;
and step S4: obtaining a non-isolated power supply scattering network according to a circuit four-port scattering model and a transmission line two-port impedance model, calculating scattering gains from a first noise source Q1 and a first noise source Q2 to positive input and output nodes P1 and P2 according to a loop theorem, and obtaining a medium-high frequency voltage V between the positive input and output nodes P1 and P2 P1P2 ；
Step S5: according to an antenna radiation model of the anode input and output cable, a vector analyzer is used for measuring reflection parameters on the anode input and output cable to obtain antenna radiation impedance R r +jX A Wherein R is r Representing the effective power of the antenna, X A Representing the reactive power of the antenna, j representing the imaginary part of the real number;
step S6: combining the directional coefficient and the space medium constant to calculate the electromagnetic radiation interference field strength under multiple spatial scales, wherein the specific calculation formula is as follows:
Figure BDA0003121332060000023
where η is a space dielectric constant, D is a directional coefficient, and r represents a distance between the non-isolated power supply and the isolated power supply.
2. The non-septum of claim 1The method for quickly predicting the electromagnetic radiation interference of the release type power supply is characterized in that the medium-high frequency voltage V P1P2 The calculation formula is specifically as follows:
V P1P2 ＝V Q1 ·G Q1P1 +V Q2 ·G Q2P1 -V Q1 ·G Q1P2 -V Q2 ·G Q2P2
wherein G is Q1P1 Is a transfer function, G, of a port formed by a first noise source Q1 to the positive input node P1 Q2P1 A transfer function, G, of a port formed by a first noise source Q2 to the positive input node P1 Q1P2 Transfer function, G, of the port formed by the first noise source Q1 to the positive output node P2 Q2P2 The transfer function of the port formed by the first noise source Q2 to the positive output node P2 is specifically expressed as:
Figure BDA0003121332060000031
Figure BDA0003121332060000032
Figure BDA0003121332060000033
Figure BDA0003121332060000034
and delta is the sum of loop gains in the non-isolated power supply scattering network.
Compared with the prior art, the invention has the following beneficial effects:
(1) On the basis of measuring the voltage amplitude-frequency characteristic of a noise source, the scattering gain of an actual circuit and the radiation impedance characteristic of a cable, the electromagnetic radiation interference intensity of non-isolated power supply noise generated by the cable can be accurately predicted;
(2) The method can quantitatively predict and evaluate the electromagnetic radiation interference characteristics of the product at low cost in the development iteration process before formal electromagnetic interference detection of the product, and provides an important reference for the inhibition of electromagnetic radiation interference;
(3) The research and development cost and the research and development period can be effectively saved.
Drawings
FIG. 1 is a flow chart of the method of the present invention.
FIG. 2 is a block circuit diagram of a non-isolated power supply.
Fig. 3 is a boost circuit diagram of a non-isolated power supply.
Fig. 4 is a four-port scattering model diagram of a non-isolated power buck circuit.
FIG. 5 is a four-port scattering model diagram of a non-isolated power boost circuit.
Fig. 6 is a diagram of a two-port scattering model of a transmission cable of a non-isolated power supply.
FIG. 7 is a diagram of a scattering network for a non-isolated power supply
FIG. 8 is a schematic diagram of antenna radiation of a positive input/output cable
FIG. 9 is a schematic diagram of an antenna radiation diagram of a cable with positive input and output electrodes
Detailed Description
The following describes a specific embodiment of a method for quickly predicting electromagnetic radiation interference of a non-isolated power supply in detail with reference to the accompanying drawings.
A buck circuit schematic diagram of an input and output cable of a non-isolated power supply is shown in figure 2, and a boost circuit schematic diagram of the input and output cable of the non-isolated power supply is shown in figure 3.
The buck circuit of the input and output cable of the non-isolation type power supply comprises a first capacitor C1, a first noise source Q1, an inductor L and a second capacitor C2 which are connected in series, wherein a positive electrode input node P1 is arranged between the first capacitor C1 and the first noise source Q1, a node M is arranged between the first noise source Q1 and the inductor L, a positive electrode output node P2 is arranged between the inductor L and the second capacitor C2, a negative electrode point N is arranged between the first capacitor C1 and the second capacitor C2, a second noise source Q2 is connected between a second port MN formed by the node M and the negative electrode point N, the two ends of the first capacitor C1 are connected with the input source Vin in parallel through the positive electrode input cable and the negative electrode input cable, and the two ends of the second capacitor C2 are connected with the load in parallel through the positive electrode output cable and the negative electrode output cable.
The boost circuit of the input and output cable of the non-isolated power supply is basically the same as the buck circuit of the input and output cable of the non-isolated power supply, and the difference is that two ends of a second capacitor C2 of the boost circuit of the input and output cable of the non-isolated power supply are connected in parallel with an input source Vin through a positive input cable and a negative input cable, and two ends of a first capacitor C1 are connected in parallel with a load through a positive output cable and a negative output cable.
The specific step flow of the electromagnetic radiation interference rapid prediction method based on the circuit is shown in fig. 1, and the method comprises the following steps:
step S1: under the condition that a non-isolated power supply is fully loaded, a high-sampling-rate oscilloscope is used for actually measuring the waveform of a SW point nonlinear device under the time scale in a unit switching period to obtain the amplitude-frequency characteristics (30M-200 MHZ) of the middle-frequency-band noise formed by the ringing effect and the amplitude-frequency characteristics (200M-1 GHZ) of the high-frequency-band noise formed by the recovery characteristic of a body diode, wherein the amplitude-frequency characteristics are V Q1 And V Q2 ；
Step S2: establishing a four-port scattering model of a non-isolated power supply circuit, wherein the node positions of the four-port scattering model of the non-isolated power supply circuit are shown in fig. 4 and 5, fig. 4 is the four-port scattering model of the non-isolated power supply buck circuit, fig. 5 is the four-port scattering model of the non-isolated power supply boost circuit, it can be seen from fig. 4 and 5 that the four-port scattering models of the buck circuit and the boost circuit are consistent, and the four ports in the non-isolated power supply buck circuit are respectively a first port P1M for accessing a first noise source Q1, a second port MN for accessing a second noise source Q2, a third port P1N for accessing a first capacitor C1, and a fourth port P2N for accessing a second capacitor C2. Four ports in the non-isolated power supply boost circuit are respectively a first port P1M for accessing a first noise source Q1, a second port MN for accessing a second noise source Q2, a third port P1N for accessing a first capacitor C1 and a third port P1N for accessing a second noise source Q2And a fourth port P2N of the second capacitor C2. Arranging four radio frequency interfaces on a non-isolated power supply actual circuit board corresponding to the port positions, nesting a test cable of a vector network analyzer into a magnetic ring, respectively connecting the test cable to the four radio frequency interfaces on the non-isolated power supply, and measuring four-port reflection coefficients, namely the reflection coefficient between every two ports
Figure BDA0003121332060000051
Wherein, a Am Indicating an incident wave from a negative pole point N to other nodes or an incident wave directed to positive pole input and output nodes P1 and P2, am indicating the number of the incident wave, and m =1,2,3,4; b An Is represented by a Am The corresponding reflected wave (when m = n), an denotes the index to the reflected wave, n =1,2,3,4; specifically, a A1 Representing the incident wave, a, from the negative point N to the node M A2 Representing the incident wave, a, from node M to the positive input node P1 a3 Denotes an incident wave, a, from the negative pole point N to the positive pole output node P2 A4 Which represents the incident wave from the negative point N to the positive input node P1.
And step S3: a transmission line two-port scattering model is established, and the port positions of the transmission line two-port scattering model are shown in fig. 6. Keeping the positive and negative cables of the transmission line parallel, respectively arranging radio frequency interfaces at the third port P1N and the fourth port P2N, nesting the test cable of the vector network analyzer into a magnetic ring, and measuring the reflection coefficient of the two ports, namely the reflection coefficient between every two ports
Figure BDA0003121332060000052
Wherein, a Bp Indicating incident waves from a negative electrode point N to positive electrode input and output nodes P1 and P2, wherein Bp indicates the reference number of the incident waves, and P =1,2; b is a mixture of Bq Is represented by Bp The corresponding reflected wave (when p = q), bq denotes the index to the reflected wave, q =1,2; specifically, a B1 Representing the incident wave, a, from node M to the positive output node P2 B2 Which represents the incident wave from the negative point N to the positive input node P1.
And step S4: circuit to be measuredThe four-port scattering model is connected with the transmission line two-port impedance model, after the weak scattering relation is ignored, a non-isolated power supply scattering network can be obtained as shown in fig. 7, and the scattering gains from the first noise source Q1 and the first noise source Q2 to the positive input and output nodes P1 and P2 are calculated according to the loop theorem, namely the medium-high frequency voltage V between the positive input and output nodes P1 and P2 is obtained P1P2 . Transfer functions of the first noise source Q1 and the first noise source Q2 to ports formed by the two positive input and output nodes P1 and P2 are respectively expressed by formulas (1 to 4), and a calculation formula of a port voltage between the two nodes P1 and P2 is expressed by (5):
Figure BDA0003121332060000053
Figure BDA0003121332060000054
Figure BDA0003121332060000055
Figure BDA0003121332060000056
V P1P2 ＝V Q1 ·G Q1P1 +V Q2 ·G Q2P1 -V Q1 ·G Q1P2 -V Q2 ·G Q2P2 (5)
where Δ is the sum of the loop gains in fig. 7.
Step S5: fig. 8 shows a schematic diagram of an antenna radiation model of the positive input/output cable, fig. 9 shows a model diagram of the antenna radiation model of the positive input/output cable, and a vector analyzer is used to measure reflection parameters on the positive input/output cable to obtain an antenna radiation impedance Rr + jXA, where Rr represents effective power of the antenna and X represents effective power of the antenna A Representing the reactive power of the antenna, j representing the imaginary part of the real number, said measurement and calculation methods being prior art.
Step S6: combining the directional coefficient and the space medium constant, the calculation formula of the electromagnetic radiation interference field strength under multiple spatial scales is formula (6):
Figure BDA0003121332060000061
where η is a space dielectric constant, D is a directional coefficient, and r represents a distance between the non-isolated power supply and the isolated power supply.
The method for rapidly predicting the electromagnetic radiation interference of the non-isolated power supply has the advantages that under the condition that only the oscilloscope and the vector network analyzer are used, the electromagnetic radiation interference intensity generated by the non-isolated power supply noise through the cable can be predicted accurately on the basis of measuring the voltage amplitude-frequency characteristic of a noise source, the scattering gain of an actual circuit and the radiation impedance characteristic of the cable; the method can quantitatively predict and evaluate the electromagnetic radiation interference characteristics of the product at low cost in the development iteration process before formal EMI detection of the product, and provides important reference for the inhibition of electromagnetic radiation interference, thereby effectively saving the research and development cost and the research and development period.
The above description is only for the purpose of illustrating the preferred embodiments of the present invention and is not to be construed as limiting the invention, and any modifications, equivalents, improvements and the like that fall within the spirit and principle of the present invention are intended to be included therein.

Claims (2)

1. A method for rapidly predicting electromagnetic radiation interference of a non-isolation type power supply comprises a buck circuit and a boost circuit, wherein the buck circuit of an input and output cable of the non-isolation type power supply comprises a first capacitor C1, a first noise source Q1, an inductor L and a second capacitor C2 which are connected in series, a positive input node P1 is arranged between the first capacitor C1 and the first noise source Q1, a node M is arranged between the first noise source Q1 and the inductor L, a positive output node P2 is arranged between the inductor L and the second capacitor C2, a negative point N is arranged between the first capacitor C1 and the second capacitor C2, a second noise source Q2 is connected between a second port MN formed by the node M and the negative point N, two ends of the first capacitor C1 are connected with an input source Vin in parallel through an anode input cable and a cathode input cable in parallel, and two ends of the second capacitor C2 are connected with a load in parallel through an anode output cable and a cathode cable in parallel; the boost circuit of the input and output cable of the non-isolated power supply is different from the buck circuit of the input and output cable of the non-isolated power supply in that two ends of a second capacitor C2 of the boost circuit of the input and output cable of the non-isolated power supply are connected with an input source Vin in parallel through a positive input cable and a negative input cable, and two ends of a first capacitor C1 are connected with a load in parallel through a positive output cable and a negative output cable, and the boost circuit of the input and output cable of the non-isolated power supply is characterized by comprising the following steps of:
step S1: under the condition that a non-isolated power supply is fully loaded, the waveform of a SW point nonlinear device in a time scale in a unit switching period is measured, and the amplitude-frequency characteristic V of the middle-frequency range noise is obtained Q1 Sum high and middle frequency band noise amplitude-frequency characteristic V Q2 ；
Step S2: establishing a transmission line four-port scattering model of a non-isolated power supply circuit, arranging four radio frequency interfaces at a first port P1M, a second port MN, a third port P1N and a fourth port P2N which are formed by a positive input node P1, a positive output node P2, a node M and a negative point N on the non-isolated power supply, connecting a test cable of a vector network analyzer to the four radio frequency interfaces on the non-isolated power supply, and measuring the reflection coefficient between every two ports
Figure FDA0003121332050000011
Wherein, a Am Indicating an incident wave from a negative pole point N to other nodes or an incident wave directed to positive pole input and output nodes P1 and P2, am indicating the number of the incident wave, and m =1,2,3,4; when m = n, b An Is represented by Am The corresponding reflected wave, an denotes the index to the reflected wave, n =1,2,3,4; namely a A1 Representing the incident wave, a, from the negative point N to the node M A2 Representing the incident wave, a, from node M to the positive input node P1 A3 Denotes an incident wave, a, from the negative pole point N to the positive pole output node P2 A4 Representing an incident wave from a negative point N to a positive input node P1; said is notThe buck circuit of the isolated power supply and the transmission cable four-port scattering model of the boost circuit are the same;
and step S3: establishing a two-port scattering model of the transmission line, keeping positive and negative cables of the transmission line parallel, respectively arranging radio frequency interfaces at a third port P1N and a fourth port P2N, and measuring a reflection coefficient between each two ports by using a vector network analyzer
Figure FDA0003121332050000012
Wherein, a Bp Indicating incident waves from a negative electrode point N to positive electrode input and output nodes P1 and P2, bp indicating the number of the incident waves, and P =1,2; when p = q, b Bq Is represented by a Bp Corresponding reflected waves, bq denotes the index to the reflected wave, q =1,2; namely a B1 Representing the incident wave, a, from node M to the positive output node P2 B2 Indicating an incident wave starting from a negative electrode point N to a positive electrode input node P1;
and step S4: obtaining a non-isolated power supply scattering network according to a circuit four-port scattering model and a transmission line two-port impedance model, calculating scattering gains from a first noise source Q1 and a first noise source Q2 to positive input and output nodes P1 and P2 according to a loop theorem, and obtaining a medium-high frequency voltage V between the positive input and output nodes P1 and P2 P1P2 ；
Step S5: according to an antenna radiation model of the anode input and output cable, a vector analyzer is used for measuring reflection parameters on the anode input and output cable to obtain antenna radiation impedance R r +jX A Wherein R is r Representing the effective power of the antenna, X A Representing the reactive power of the antenna, j representing the imaginary part of the real number;
step S6: combining the directional coefficient and the space medium constant to calculate the electromagnetic radiation interference field strength under multiple spatial scales, wherein the specific calculation formula is as follows:
Figure FDA0003121332050000021
where η is a space dielectric constant, D is a directional coefficient, and r represents a distance between the non-isolated power supply and the isolated power supply.
2. The method for rapidly predicting non-isolated power supply electromagnetic radiation interference according to claim 1, wherein the medium-high frequency voltage V P1P2 The calculation formula is specifically as follows:
V P1P2 ＝V Q1 ·G Q1P1 +V Q2 ·G Q2P1 -V Q1 ·G Q1P2 -V Q2 ·G Q2P2
wherein, G Q1P1 Transfer function, G, of the port formed by the first noise source Q1 to the positive input node P1 Q2P1 A transfer function, G, of a port formed by a first noise source Q2 to the positive input node P1 Q1P2 Transfer function, G, of the port formed by the first noise source Q1 to the positive output node P2 Q2P2 The transfer function of a port formed by the first noise source Q2 to the positive output node P2 is specifically expressed as:
Figure FDA0003121332050000022
Figure FDA0003121332050000023
Figure FDA0003121332050000024
Figure FDA0003121332050000025
and delta is the sum of loop gains in the non-isolated power supply scattering network.
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