CN113468850A - Non-isolated power supply electromagnetic radiation interference rapid prediction method - Google Patents

Non-isolated power supply electromagnetic radiation interference rapid prediction method Download PDF

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CN113468850A
CN113468850A CN202110683007.8A CN202110683007A CN113468850A CN 113468850 A CN113468850 A CN 113468850A CN 202110683007 A CN202110683007 A CN 202110683007A CN 113468850 A CN113468850 A CN 113468850A
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CN113468850B (en
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冯锟
管松敏
马宁
马惠
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CETC 14 Research Institute
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Abstract

The invention discloses a method for quickly predicting non-isolated power supply electromagnetic radiation interference, which comprises the following steps: step S1: under the condition that a non-isolated power supply is fully loaded, the waveform of a SW point nonlinear device in a time scale in a unit switching period is measured, and the amplitude-frequency characteristic V of the middle-frequency range noise is obtainedQ1Sum high and middle frequency band noise amplitude-frequency characteristic VQ2(ii) a Step S2: establishing a transmission line four-port scattering model of the non-isolated power circuit, and step S3: establishing a transmission line two-port scattering model, and step S4: and obtaining the non-isolated power supply scattering network according to the circuit four-port scattering model and the transmission line two-port impedance model. The method for rapidly predicting the electromagnetic radiation interference of the non-isolated power supply can accurately predict the electromagnetic radiation interference intensity of the non-isolated power supply noise generated by the cable under the condition of only using the oscilloscope and the vector network analyzer.

Description

Non-isolated power supply electromagnetic radiation interference rapid prediction method
Technical Field
The invention relates to the field of switching power supplies, in particular to a method for quickly predicting electromagnetic radiation interference of a non-isolated power supply.
Background
The increasingly strong miniaturization demand of electronic products has pushed non-isolated power supplies (mainly buck-type buck converters and boost-type boost converters) to develop higher switching frequency and higher power density, and meanwhile, electromagnetic interference (EMI) with higher intensity is also brought. The electromagnetic interference is electromagnetic conducted interference and electromagnetic radiation interference respectively, wherein the electromagnetic radiation interference can be radiated to the surrounding space by the antenna effect of the input and output cable, so that the interference to a radio frequency circuit and a frequency source is caused, the communication signal distortion and the working abnormity of a digital-to-analog circuit are caused, and even the health of a human body is damaged, so that the accurate test and the corresponding inhibition of the electromagnetic radiation interference have important significance for improving the overall performance of an electronic product.
Some international standards specify the qualitative and quantitative determination of electromagnetic radiation interference in different spatial scales, such as EN55022, EN55032, CISPR22 and CISPR25, and so on. The requirements of the standards on electromagnetic radiation interference are mainly in a frequency band of 30M-1G, and the radiation field intensity under different spatial scales from a noise source is limited. Meanwhile, a test method of electromagnetic radiation interference is specified, and the test tools are required to be a signal receiver (more than 1G), a frequency spectrograph (more than 1G), a microwave darkroom and a test antenna, wherein the specific test method is that in the microwave darkroom, a tested product rotates 360 degrees along with a test bench, the antenna is adjusted at different heights to search for the maximum radiation value, and the measurement unit of a test result is dBuV/m.
As can be seen from the test conditions and test methods specified by the international standard, the existing electromagnetic radiation interference test has the disadvantages that: requiring special test equipment, expensive test expenses, and special test sites, which are very inconvenient for product development.
Disclosure of Invention
In order to solve the problems, the invention provides a method for quickly predicting the electromagnetic radiation interference of a non-isolated power supply, the non-isolated power supply comprises a buck circuit and a boost circuit, the buck circuit of the input and output cable of the non-isolated power supply comprises a first capacitor C1, a first noise source Q1, an inductor L and a second capacitor C2 which are connected in series, a positive input node P1 is arranged between the first capacitor C1 and the first noise source Q1, a node M is arranged between the first noise source Q1 and the inductor L, a positive output node P2 is arranged between the inductor L and the second capacitor C2, a negative point N is arranged between the first capacitor C1 and the second capacitor C2, a second noise source Q2 is connected between a second port MN formed by the node M and the cathode point N, two ends of a first capacitor C1 are connected with an input source Vin in parallel through an anode input cable and a cathode input cable, and two ends of a second capacitor C2 are connected with a load in parallel through an anode output cable and a cathode output cable; the difference between the boost circuit of the input and output cable of the non-isolated power supply and the buck circuit of the input and output cable of the non-isolated power supply is that two ends of a second capacitor C2 of the boost circuit of the input and output cable of the non-isolated power supply are connected in parallel with an input source Vin through a positive input cable and a negative input cable, and two ends of a first capacitor C1 are connected in parallel with a load through a positive output cable and a negative output cable, and the method is characterized by comprising the following steps:
step S1: under the condition that a non-isolated power supply is fully loaded, the waveform of a SW point nonlinear device in a time scale in a unit switching period is measured, and the amplitude-frequency characteristic V of the middle-frequency range noise is obtainedQ1Sum high and middle frequency band noise amplitude-frequency characteristic VQ2；
Step S2: establishing a transmission line four-port scattering model of a non-isolated power supply circuit, and forming a first port P1M and a second port MN on a non-isolated power supply by using a positive input node P1, a positive output node P2, a node M and a negative point NFour radio frequency interfaces are arranged at the third port P1N and the fourth port P2N, a test cable of the vector network analyzer is connected to the four radio frequency interfaces on the non-isolated power supply, and the reflection coefficient between every two ports is measured
Figure BDA0003121332060000021
Wherein, aAmIndicating an incident wave from the negative electrode point N to another node or an incident wave directed to the positive electrode input/output nodes P1 and P2, Am indicating the reference numeral of the incident wave, and m is 1, 2, 3, 4; when m is n, bAnIs represented byAmThe corresponding reflected wave, An, is the reference number to the reflected wave, n is 1, 2, 3, 4; namely aA1Representing the incident wave, a, from the negative point N to the node MA2Representing the incident wave, a, from node M to the positive input node P1A3Denotes an incident wave, a, from the negative pole point N to the positive pole output node P2A4Represents the incident wave from the negative pole point N to the positive input node P1; the buck circuit of the non-isolated power supply and the transmission cable four-port scattering model of the boost circuit are the same;
step S3: establishing a transmission line two-port scattering model, keeping positive and negative cables of the transmission line parallel, respectively arranging radio frequency interfaces at a third port P1N and a fourth port P2N, and measuring the reflection coefficient between every two ports by using a vector network analyzer
Figure BDA0003121332060000022
Wherein, aBpDenotes an incident wave from the negative electrode point N to the positive electrode input/output nodes P1 and P2, Bp denotes an incident wave reference numeral, and P is 1, 2; when p is q, bBqIs represented byBpA corresponding reflected wave, Bq denotes the reference number of the reflected wave, q is 1, 2; namely aB1Representing the incident wave, a, from node M to the positive output node P2B2Represents the incident wave from the negative pole point N to the positive input node P1;
step S4: obtaining a non-isolated power supply scattering network according to a circuit four-port scattering model and a transmission line two-port impedance model, and calculating a first noise source Q1 and a first noise source Q2 toScattering gains of the positive input and output nodes P1 and P2 are obtained, namely the medium-high frequency voltage V between the positive input and output nodes P1 and P2P1P2；
Step S5: according to an antenna radiation model of the anode input and output cable, a vector analyzer is used for measuring reflection parameters on the anode input and output cable to obtain antenna radiation impedance Rr+jXAWherein R isrRepresenting the effective power of the antenna, XARepresenting the reactive power of the antenna, j representing the imaginary part of the real number;
step S6: combining the directional coefficient and the space medium constant to calculate the electromagnetic radiation interference field strength under multiple spatial scales, wherein the specific calculation formula is as follows:
Figure BDA0003121332060000023
where η is a space dielectric constant, D is a directional coefficient, and r represents a distance between the non-isolated power supply and the isolated power supply.
2. The method for rapidly predicting non-isolated power supply electromagnetic radiation interference according to claim 1, wherein the medium-high frequency voltage V isP1P2The calculation formula is specifically as follows:
VP1P2＝VQ1·GQ1P1+VQ2·GQ2P1-VQ1·GQ1P2-VQ2·GQ2P2
wherein G isQ1P1Is a transfer function, G, of the port formed by the first noise source Q1 to the positive input node P1Q2P1Is a transfer function, G, of the port formed by the first noise source Q2 to the positive input node P1Q1P2Is a transfer function, G, of the port formed by the first noise source Q1 to the positive output node P2Q2P2The transfer function of the port formed by the first noise source Q2 to the positive output node P2 is specifically expressed as:
Figure BDA0003121332060000031
Figure BDA0003121332060000032
Figure BDA0003121332060000033
Figure BDA0003121332060000034
and delta is the sum of loop gains in the non-isolated power supply scattering network.
Compared with the prior art, the invention has the following beneficial effects:
(1) the electromagnetic radiation interference intensity generated by the non-isolated power supply noise through the cable can be accurately predicted on the basis of measuring the voltage amplitude-frequency characteristic of the noise source, the actual circuit scattering gain and the cable radiation impedance characteristic;
(2) the method can quantitatively predict and evaluate the electromagnetic radiation interference characteristics of the product at low cost in the development iteration process before formal electromagnetic interference detection of the product, and provides an important reference for the inhibition of electromagnetic radiation interference;
(3) the research and development cost and the research and development period can be effectively saved.
Drawings
FIG. 1 is a flow chart of the method of the present invention.
FIG. 2 is a block circuit diagram of a non-isolated power supply.
Fig. 3 is a schematic diagram of a boost circuit of a non-isolated power supply.
Fig. 4 is a four-port scattering model diagram of a non-isolated power buck circuit.
FIG. 5 is a diagram of a four-port scattering model of a non-isolated power boost circuit.
FIG. 6 is a diagram of a scattering model of two ports of a transmission cable of a non-isolated power supply.
FIG. 7 is a diagram of a scattering network for a non-isolated power supply
FIG. 8 is a schematic diagram of antenna radiation for a positive input/output cable
FIG. 9 is a schematic diagram of an antenna radiation diagram of a cable with positive input and output electrodes
Detailed Description
The following describes a specific embodiment of a method for rapidly predicting non-isolated power supply electromagnetic radiation interference according to the present invention in detail with reference to the accompanying drawings.
A buck circuit schematic diagram of an input/output cable of a non-isolated power supply is shown in FIG. 2, and a boost circuit schematic diagram of the input/output cable of the non-isolated power supply is shown in FIG. 3.
The buck circuit of the input and output cable of the non-isolation type power supply comprises a first capacitor C1, a first noise source Q1, an inductor L and a second capacitor C2 which are connected in series, a positive electrode input node P1 is arranged between the first capacitor C1 and the first noise source Q1, a node M is arranged between the first noise source Q1 and the inductor L, a positive electrode output node P2 is arranged between the inductor L and the second capacitor C2, a negative electrode point N is arranged between the first capacitor C1 and the second capacitor C2, a second noise source Q2 is connected between a second port MN formed by the node M and the negative electrode point N, two ends of the first capacitor C1 are connected with the input source Vin in parallel through the positive electrode input cable and the negative electrode input cable, and two ends of the second capacitor C2 are connected with a load in parallel through the positive electrode output cable and the negative electrode output cable.
The boost circuit of the input and output cable of the non-isolated power supply is basically the same as the buck circuit of the input and output cable of the non-isolated power supply, and the difference is that two ends of a second capacitor C2 of the boost circuit of the input and output cable of the non-isolated power supply are connected in parallel with an input source Vin through a positive input cable and a negative input cable, and two ends of a first capacitor C1 are connected in parallel with a load through the positive output cable and the negative output cable.
The specific step flow of the electromagnetic radiation interference rapid prediction method based on the circuit is shown in fig. 1, and the method comprises the following steps:
step S1: under the condition that a non-isolated power supply is fully loaded, a high-sampling-rate oscilloscope is used for actually measuring the waveform of a SW point nonlinear device under the time scale in a unit switching period to obtain the ringing effectThe amplitude-frequency characteristics of the middle-frequency band noise (30M-200 MHZ) and the high-frequency band noise (200M-1 GHZ) formed by the body diode recovery characteristics are respectively VQ1And VQ2；
Step S2: establishing a four-port scattering model of a non-isolated power supply circuit, wherein the node positions of the four-port scattering model of the non-isolated power supply circuit are shown in fig. 4 and 5, fig. 4 is the four-port scattering model of the non-isolated power supply buck circuit, fig. 5 is the four-port scattering model of the non-isolated power supply boost circuit, it can be seen from fig. 4 and 5 that the four-port scattering models of the buck circuit and the boost circuit are consistent, and the four ports in the non-isolated power supply buck circuit are respectively a first port P1M for accessing a first capacitor Q1, a second port MN for accessing a second noise source Q2, a third port P1N for accessing a first capacitor C1, and a fourth port P2N for accessing a second capacitor C2. Four ports in the non-isolated power supply boost circuit are respectively a first port P1M for accessing a first noise source Q1, a second port MN for accessing a second noise source Q2, a third port P1N for accessing a first capacitor C1 and a fourth port P2N for accessing a second capacitor C2. Arranging four radio frequency interfaces on a non-isolated power supply actual circuit board corresponding to the port positions, nesting a test cable of a vector network analyzer into a magnetic ring, respectively connecting the test cable to the four radio frequency interfaces on the non-isolated power supply, and measuring four-port reflection coefficients, namely the reflection coefficient between every two ports
Figure BDA0003121332060000051
Wherein, aAmIndicating an incident wave from the negative electrode point N to another node or an incident wave directed to the positive electrode input/output nodes P1 and P2, Am indicating the reference numeral of the incident wave, and m is 1, 2, 3, 4; bAnIs represented byAmCorresponding reflected waves (when m is equal to n), An denotes the index of the reflected wave, n is equal to 1, 2, 3, 4; specifically, aA1Representing the incident wave, a, from the negative point N to the node MA2Representing the incident wave, a, from node M to the positive input node P1a3Denotes an incident wave, a, from the negative pole point N to the positive pole output node P2A4Indicates from the negative pole point NIncident wave to positive input node P1.
Step S3: a transmission line two-port scattering model is established, and the port positions of the transmission line two-port scattering model are shown in fig. 6. Keeping the positive and negative cables of the transmission line parallel, respectively arranging radio frequency interfaces at a third port P1N and a fourth port P2N, nesting the test cables of the vector network analyzer into magnetic rings, and measuring the reflection coefficients of the two ports, namely the reflection coefficient between every two ports
Figure BDA0003121332060000052
Wherein, aBpDenotes an incident wave from the negative electrode point N to the positive electrode input/output nodes P1 and P2, Bp denotes an incident wave reference numeral, and P is 1, 2; bBqIs represented byBpCorresponding reflected waves (when p is q), Bq denotes the index to the reflected wave, q is 1, 2; specifically, aB1Representing the incident wave, a, from node M to the positive output node P2B2Representing the incident wave from the negative point N to the positive input node P1.
Step S4: connecting the measured circuit four-port scattering model with the transmission line two-port impedance model, neglecting weak scattering relation, obtaining a non-isolated power supply scattering network as shown in fig. 7, and calculating the scattering gains from the first noise source Q1 and the first noise source Q2 to the positive input and output nodes P1 and P2 according to the loop theorem to obtain the medium-high frequency voltage V between the positive input and output nodes P1 and P2P1P2. The transfer functions of the first noise source Q1 and the first noise source Q2 to the port formed by the two positive input and output nodes P1 and P2 are respectively in formulas (1-4), and the calculation formula of the port voltage between the two nodes P1 and P2 is (5):
Figure BDA0003121332060000053
Figure BDA0003121332060000054
Figure BDA0003121332060000055
Figure BDA0003121332060000056
VP1P2＝VQ1·GQ1P1+VQ2·GQ2P1-VQ1·GQ1P2-VQ2·GQ2P2 (5)
where Δ is the sum of the loop gains in fig. 7.
Step S5: fig. 8 shows a schematic diagram of an antenna radiation model of the positive input/output cable, and fig. 9 shows a model diagram of the antenna radiation model of the positive input/output cable, and a vector analyzer is used to measure a reflection parameter on the positive input/output cable to obtain an antenna radiation impedance Rr + jXA, where Rr represents an effective power of the antenna, and X represents an effective power of the antenna, andArepresenting the reactive power of the antenna, j representing the imaginary part of the real number, said measurement and calculation methods being prior art.
Step S6: combining the directional coefficient and the space medium constant, the calculation formula of the electromagnetic radiation interference field strength under multiple spatial scales is formula (6):
Figure BDA0003121332060000061
where η is a space dielectric constant, D is a directional coefficient, and r represents a distance between the non-isolated power supply and the isolated power supply.
The method for rapidly predicting the electromagnetic radiation interference of the non-isolated power supply has the advantages that under the condition that only the oscilloscope and the vector network analyzer are used, the electromagnetic radiation interference intensity generated by the non-isolated power supply noise through the cable can be predicted accurately on the basis of measuring the voltage amplitude-frequency characteristic of a noise source, the scattering gain of an actual circuit and the radiation impedance characteristic of the cable; the method can quantitatively predict and evaluate the electromagnetic radiation interference characteristics of the product at low cost in the development iteration process before formal EMI detection of the product, and provides important reference for the inhibition of electromagnetic radiation interference, thereby effectively saving the research and development cost and the research and development period.
The above description is only for the purpose of illustrating the preferred embodiments of the present invention and is not to be construed as limiting the invention, and any modifications, equivalents, improvements and the like that fall within the spirit and principle of the present invention are intended to be included therein.

Claims (2)

1. A method for quickly predicting electromagnetic radiation interference of a non-isolated power supply comprises a buck circuit and a boost circuit, the buck circuit of the input and output cable of the non-isolated power supply comprises a first capacitor C1, a first noise source Q1, an inductor L and a second capacitor C2 which are connected in series, a positive input node P1 is arranged between the first capacitor C1 and the first noise source Q1, a node M is arranged between the first noise source Q1 and the inductor L, a positive output node P2 is arranged between the inductor L and the second capacitor C2, a negative point N is arranged between the first capacitor C1 and the second capacitor C2, a second noise source Q2 is connected between a second port MN formed by the node M and the cathode point N, two ends of a first capacitor C1 are connected with an input source Vin in parallel through an anode input cable and a cathode input cable, and two ends of a second capacitor C2 are connected with a load in parallel through an anode output cable and a cathode output cable; the difference between the boost circuit of the input and output cable of the non-isolated power supply and the buck circuit of the input and output cable of the non-isolated power supply is that two ends of a second capacitor C2 of the boost circuit of the input and output cable of the non-isolated power supply are connected in parallel with an input source Vin through a positive input cable and a negative input cable, and two ends of a first capacitor C1 are connected in parallel with a load through a positive output cable and a negative output cable, and the method is characterized by comprising the following steps:
step S1: under the condition that a non-isolated power supply is fully loaded, the waveform of a SW point nonlinear device in a time scale in a unit switching period is measured, and the amplitude-frequency characteristic V of the middle-frequency range noise is obtainedQ1Sum high and middle frequency band noise amplitude-frequency characteristic VQ2；
Step S2: establishing a transmission line four-port scattering model of a non-isolated power supply circuit, and inputting a node on the positive pole of the non-isolated power supplyFour radio frequency interfaces are arranged at a first port P1M, a second port MN, a third port P1N and a fourth port P2N which are formed by a P1, a positive pole node P2, a node M and a negative pole point N, a test cable of the vector network analyzer is connected to the four radio frequency interfaces on the non-isolated power supply, and the reflection coefficient between every two ports is measured
Figure FDA0003121332050000011
Wherein, aAmIndicating an incident wave from the negative electrode point N to another node or an incident wave directed to the positive electrode input/output nodes P1 and P2, Am indicating the reference numeral of the incident wave, and m is 1, 2, 3, 4; when m is n, bAnIs represented byAmThe corresponding reflected wave, An, is the reference number to the reflected wave, n is 1, 2, 3, 4; namely aA1Representing the incident wave, a, from the negative point N to the node MA2Representing the incident wave, a, from node M to the positive input node P1A3Denotes an incident wave, a, from the negative pole point N to the positive pole output node P2A4Represents the incident wave from the negative pole point N to the positive input node P1; the buck circuit of the non-isolated power supply and the transmission cable four-port scattering model of the boost circuit are the same;
step S3: establishing a transmission line two-port scattering model, keeping positive and negative cables of the transmission line parallel, respectively arranging radio frequency interfaces at a third port P1N and a fourth port P2N, and measuring the reflection coefficient between every two ports by using a vector network analyzer
Figure FDA0003121332050000012
Wherein, aBpDenotes an incident wave from the negative electrode point N to the positive electrode input/output nodes P1 and P2, Bp denotes an incident wave reference numeral, and P is 1, 2; when p is q, bBqIs represented byBpA corresponding reflected wave, Bq denotes the reference number of the reflected wave, q is 1, 2; namely aB1Representing the incident wave, a, from node M to the positive output node P2B2Represents the incident wave from the negative pole point N to the positive input node P1;
step S4: according to the four-port scattering model of the circuit and the two-port impedance of the transmission lineObtaining a non-isolated power supply scattering network by the model, calculating scattering gains from a first noise source Q1 and a first noise source Q2 to positive input and output nodes P1 and P2 according to a loop theorem, and obtaining a medium-high frequency voltage V between the positive input and output nodes P1 and P2P1P2；
Step S5: according to an antenna radiation model of the anode input and output cable, a vector analyzer is used for measuring reflection parameters on the anode input and output cable to obtain antenna radiation impedance Rr+jXAWherein R isrRepresenting the effective power of the antenna, XARepresenting the reactive power of the antenna, j representing the imaginary part of the real number;
step S6: combining the directional coefficient and the space medium constant to calculate the electromagnetic radiation interference field strength under multiple spatial scales, wherein the specific calculation formula is as follows:
Figure FDA0003121332050000021
where η is a space dielectric constant, D is a directional coefficient, and r represents a distance between the non-isolated power supply and the isolated power supply.
2. The method for rapidly predicting non-isolated power supply electromagnetic radiation interference according to claim 1, wherein the medium-high frequency voltage V isP1P2The calculation formula is specifically as follows:
VP1P2＝VQ1·GQ1P1+VQ2·GQ2P1-VQ1·GQ1P2-VQ2·GQ2P2
wherein G isQ1P1Is a transfer function, G, of the port formed by the first noise source Q1 to the positive input node P1Q2P1Is a transfer function, G, of the port formed by the first noise source Q2 to the positive input node P1Q1P2Is a transfer function, G, of the port formed by the first noise source Q1 to the positive output node P2Q2P2The transfer function of the port formed by the first noise source Q2 to the positive output node P2 is specifically expressed as:
Figure FDA0003121332050000022
Figure FDA0003121332050000023
Figure FDA0003121332050000024
Figure FDA0003121332050000025
and delta is the sum of loop gains in the non-isolated power supply scattering network.
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Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101629980A (en) * 2009-09-10 2010-01-20 南京师范大学 Method for testing performance of EMI filter based on scattering parameter
CN102981086A (en) * 2012-12-10 2013-03-20 江苏省产品质量监督检验研究院 Analysis and measurement method for electromagnetic radiation of voltage driven radiation source
CN110287558A (en) * 2019-06-13 2019-09-27 南京航空航天大学 The method for building up of DC/DC changer system far-field radiation prediction model

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101629980A (en) * 2009-09-10 2010-01-20 南京师范大学 Method for testing performance of EMI filter based on scattering parameter
CN102981086A (en) * 2012-12-10 2013-03-20 江苏省产品质量监督检验研究院 Analysis and measurement method for electromagnetic radiation of voltage driven radiation source
CN110287558A (en) * 2019-06-13 2019-09-27 南京航空航天大学 The method for building up of DC/DC changer system far-field radiation prediction model

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