CN113394996A - AC-DC resonant conversion circuit and control method thereof - Google Patents
AC-DC resonant conversion circuit and control method thereof Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4241—Arrangements for improving power factor of AC input using a resonant converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33584—Bidirectional converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The invention discloses an AC-DC resonance conversion circuit and a control method thereof, wherein the AC-DC resonance conversion circuit comprises an alternating current connection end, a PFC-BUS conversion module, a transformer and a secondary side conversion module which are sequentially connected; the PFC-BUS conversion module adopts a control pulse signal generated by an SVPWM (space vector pulse width modulation) algorithm to implement switching control, can correct the power factor of input alternating current, converts the alternating current into direct current and transmits the direct current to the primary side of the transformer; the secondary side conversion module controls the pulse signal to follow the PFC-BUS conversion module to control the pulse signal, and a phase shift control angle phi is arranged between the PFC-BUS conversion module control pulse signal and the secondary side conversion module control pulse signal; the PFC-BUS conversion module of the invention shares the switch tube, not only finishes the power factor and current waveform correction, but also finishes the regulation of the output voltage, and the two-stage conversion of the whole circuit shares the same switch device, so that the whole circuit has simple and compact structure and is convenient to control.
Description
Technical Field
The present invention relates to power supply circuits, and particularly to an AC-DC resonant converting circuit and a control method thereof.
Background
An AC-DC converter is a power supply device for converting alternating current into direct current, and the common AC-DC isolating converter at present is of a two-stage structure, wherein the front stage is a common PWM rectifier, and the rear stage is an isolated DC-DC converter. However, the converter is of a two-stage structure, an energy storage link is arranged in the middle of the converter, the working efficiency of the converter can be reduced, and the front stage and the rear stage in the two-stage structure need to be modulated and controlled respectively, so that the control complexity is greatly increased. As shown in fig. 1, an AC-DC converter in the prior art is configured such that energy of a three-phase or single-phase power supply is rectified by a PFC circuit, the energy is stored in a DC bus, a switch in a primary input module is adjusted to convert DC into AC, the AC is stored in a primary winding of a transformer T, the energy is stored in a secondary winding of the transformer by a certain turn ratio, and the AC is converted into DC by a secondary output module and is output. The middle part relates to an AC-DC and DC-DC two-stage energy transmission process, an energy storage link is also provided, the working efficiency of the converter is reduced, and the rectifying module, the primary side input module and the secondary side output module are required to be modulated and controlled respectively, so that the control difficulty is greatly increased.
Therefore, in order to solve the problems of low conversion efficiency and complex control of the two-stage conversion isolation type converter, an AC-DC resonant conversion circuit and a control method thereof with high conversion efficiency and low control difficulty are urgently needed to be provided in the industry.
Disclosure of Invention
In order to solve the above-mentioned defects in the prior art, the present invention provides an AC-DC resonant converting circuit and a control method thereof.
The technical scheme adopted by the invention is to design an AC-DC resonance conversion circuit, which comprises an alternating current connection end, a PFC-BUS conversion module, a transformer, a secondary side conversion module and a controller which are sequentially connected; the PFC-BUS conversion module adopts a control pulse signal generated by an SVPWM (space vector pulse width modulation) algorithm to implement switching control, can correct the power factor of input alternating current, converts the alternating current into direct current and transmits the direct current to the primary side of the transformer; the secondary side conversion module is connected with the secondary side of the transformer and can output direct current; the secondary side conversion module controls the pulse signal to follow the PFC-BUS conversion module control pulse signal, and a phase shift control angle phi is arranged between the PFC-BUS conversion module control pulse signal and the secondary side conversion module control pulse signal.
The PFC-BUS conversion module comprises three pairs of bridge arms consisting of 6 switches, wherein the upper bridge arms of the three pairs of bridge arms are connected with a positive direct current BUS, the lower bridge arms of the three pairs of bridge arms are connected with a negative direct current BUS, and the battery pack is connected between the positive direct current BUS and the negative direct current BUS; the first bridge arm comprises a first switch Q1 and a fourth switch Q4, an A wiring point is connected between the two switches, and the A wiring point is connected with a U phase in an alternating current electric connection end and a first resonance branch; the second bridge arm comprises a second switch Q2 and a fifth switch Q5, a B wiring point is connected between the two switches, and the B wiring point is connected with a V phase in the alternating current electric connection end and a second resonance branch; the third bridge arm comprises a third switch Q3 and a sixth switch Q6, a C wiring point is connected between the two switches, and the C wiring point is connected with the W phase in the alternating current electric connection end and the third resonance branch; the first, second and third resonance branches have the same structure and comprise resonance capacitors and resonance inductors which are connected in series; the first, second and third resonant branches are respectively connected with the head ends of three coils on the primary side of the transformer, and the tail ends of the three coils on the primary side of the transformer are connected with each other.
The secondary side conversion module comprises three pairs of bridge arms consisting of 6 switches, wherein the upper bridge arm of the three pairs of bridge arms is connected with the positive pole V + of the power supply, and the lower bridge arm of the three pairs of bridge arms is connected with the negative pole V-; the fourth bridge arm comprises a seventh switch Q7 and a tenth switch Q10, a D wiring point is connected between the two switches, and the D wiring point is connected with one end of a first isolation capacitor Cg 1; the fifth bridge arm comprises an eighth switch Q8 and an eleventh switch Q11, an E wiring point is connected between the two switches, and the E wiring point is connected with one end of a second isolation capacitor Cg 2; the sixth bridge arm comprises a ninth switch Q9 and a twelfth switch Q12, an F wiring point is connected between the two switches, and the F wiring point is connected with one end of a third isolation capacitor Cg 3; the other ends of the first isolation capacitor Cg1, the second isolation capacitor Cg2 and the third isolation capacitor Cg3 are respectively connected with the head ends of the three coils on the secondary side of the transformer, and the tail ends of the three coils on the secondary side of the transformer are connected with each other.
The A wiring point is connected with a U phase in an alternating current electric connection end through a first filter inductor L1; the B wiring point is connected with a V phase in the alternating current connection end through a second filter inductor L2; the C connection point is connected to the W phase in the ac electrical connection terminal through a third filter inductor L3.
The battery pack comprises a first capacitor C1 and a second capacitor C2 which are connected in series, and filter capacitors (Cf 1, Cf2 and Cf 3) are respectively connected between a connecting point between the first capacitor C1 and the second capacitor C2 and the U phase, the V phase and the W phase.
And a third capacitor C3 and a fourth capacitor C4 are connected between the positive electrode V + of the power supply and the negative electrode V-, and a connecting point between the third capacitor C3 and the fourth capacitor C4 is connected with the tail ends of the three coils on the secondary side of the transformer.
And a thirteenth switch Q13 and a fourteenth switch Q14 are connected between the positive direct current bus and the negative direct current bus in series, and a connection point between the thirteenth switch Q13 and the fourteenth switch Q14 is connected with a zero line of the alternating current.
The U phase in the alternating current connection end is connected with a first power switch S1 in series, the V phase is connected with a second power switch S2 in series, the W phase is connected with a third power switch S3 in series, and a fourth power switch S4 is connected between the A connection point and the first resonance branch circuit in series.
The power switches in the PFC-BUS conversion module and the secondary conversion module are both bidirectional switches, electric energy flows from the PFC-BUS conversion module to the secondary conversion module in a charging mode, and electric energy flows from the secondary conversion module to the PFC-BUS conversion module in an inversion mode.
In addition, the invention also provides an AC-DC resonance conversion circuit, wherein the positive direct current bus is connected with the cathode of a first diode D1, the anode of a first diode D1 is connected with the zero line of the alternating current and the cathode of a second diode D2, and the anode of a second diode D2 is connected with the negative direct current bus.
The invention also designs a control method of the AC-DC resonant conversion circuit, the conversion circuit adopts the AC-DC resonant conversion circuit, and the control method comprises the following steps: step 10, generating a PFC-BUS conversion module control pulse signal according to an SVPWM (space vector pulse width modulation) algorithm; and 20, controlling the secondary side conversion module to control a pulse signal to follow the PFC-BUS conversion module control pulse signal, and setting a phase shift control angle phi between the PFC-BUS conversion module control pulse signal and the secondary side conversion module control pulse signal.
The phase shift control angle phi in the charging mode is positive, and the phase shift control angle phi in the inverting mode is negative.
The phase shift control angle phi in the charging mode is 0 to 25% T, and the phase shift control angle phi in the inverting mode is 0 to-25% T; wherein T is the period of the control pulse signal of the PFC-BUS conversion module.
The step 10 is preceded by the steps of:
The technical scheme provided by the invention has the beneficial effects that:
the invention cancels the two-stage structure of the converter, does not need to modulate and control the front stage and the rear stage respectively, reduces the control complexity, improves the working efficiency of the converter, shares a switch tube in a PFC-BUS conversion module, not only finishes the power factor and the current waveform correction, but also finishes the regulation of the output voltage, shares the same switch device in the two-stage conversion of the whole circuit, ensures that the whole circuit has simple and compact structure and convenient control, and can increase the power supply power of the power supply equipment.
Drawings
The invention is described in detail below with reference to examples and figures, in which:
FIG. 1 is a schematic diagram of a prior art AC-DC converter architecture;
FIG. 2 is a block diagram of the AC-DC resonant conversion structure of the present invention;
FIG. 3 is a circuit diagram of a basic embodiment of the present invention;
FIG. 4 is a circuit diagram of an embodiment of a secondary side conversion module with additional filtering power connections according to the present invention;
FIG. 5 is a circuit diagram of an embodiment of the present invention in which a freewheeling diode is added to the PFC-BUS conversion module;
FIG. 6 is a circuit diagram of an embodiment of the present invention in which a PFC-BUS conversion module is added with a freewheeling switch;
FIG. 7 is a circuit diagram of a compatible single three phase AC-DC resonant conversion circuit in another embodiment of the present invention;
FIG. 8 is a schematic circuit diagram of a connection to a single phase grid;
FIG. 9 is a timing diagram of a simulation of the Q1-Q6 control pulse signals;
FIG. 10 is a graph of the resonant inductor current and output current variation during phase shifting;
FIG. 11 is a phase shift control angle versus output current plot;
FIG. 12 is a plot of inductance versus phase shift angle control output current;
FIG. 13 is a schematic diagram of an application scenario of the AC-DC resonant conversion circuit;
FIG. 14 is a transformer self-inductance and resonant circuit schematic;
fig. 15 is a schematic diagram of the zero voltage conduction of the switching tube Q1;
fig. 16 is a schematic diagram of the AC-DC resonant conversion circuit SVPWM control.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is described in further detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and are not intended to limit the invention.
The invention has the main technical points that the PFC rectification and the primary side input module in the prior art are combined, the power factor and current waveform correction can be completed, the output voltage can be adjusted, and the two-stage transformation of the whole circuit shares the same switch device, so that the whole circuit has simple and compact structure and convenient control, and the power supply power of power supply equipment can be increased. In the charging mode, energy flows through the PFC-BUS module by a three-phase power supply, the input alternating current is directly converted into direct current to be used as the primary input of the transformer, and the direct current is output to the secondary output module through the high-frequency transformer to finish the conversion of AC-DC.
The invention discloses an AC-DC resonance conversion circuit, which comprises an alternating current connection end, a PFC-BUS conversion module, a transformer, a secondary side conversion module and a controller, wherein the alternating current connection end, the PFC-BUS conversion module, the transformer, the secondary side conversion module and the controller are sequentially connected; the PFC-BUS conversion module adopts a control pulse signal generated by an SVPWM (space vector pulse width modulation) algorithm to implement switching control, can correct the power factor of input alternating current, converts the alternating current into direct current and transmits the direct current to the primary side of the transformer; the secondary side conversion module is connected with the secondary side of the transformer and can output direct current; the secondary side conversion module controls the pulse signal to follow the PFC-BUS conversion module control pulse signal, and a phase shift control angle phi is arranged between the PFC-BUS conversion module control pulse signal and the secondary side conversion module control pulse signal.
The invention uses a PFC-BUS conversion module to complete the functions of the conventional PFC module and the primary side conversion module, not only finishes the power factor and current waveform correction, but also can complete the regulation of output voltage by sharing a switching tube, and can stably output direct current by controlling the secondary side conversion module by using a phase-shifting technology. The two-stage conversion of the whole circuit shares the same switch device, so that the whole circuit is simple and compact in structure and convenient to control, and the power supply power of the power supply equipment can be increased.
Referring to the circuit diagram of the basic embodiment of the present invention shown in fig. 3, the PFC-BUS conversion module includes three pairs of bridge arms formed by 6 switches, an upper bridge arm of the three pairs of bridge arms is connected to a positive dc BUS, a lower bridge arm of the three pairs of bridge arms is connected to a negative dc BUS, and the battery pack is connected between the positive dc BUS and the negative dc BUS; the first bridge arm comprises a first switch Q1 and a fourth switch Q4, an A wiring point is connected between the two switches, and the A wiring point is connected with a U phase in an alternating current electric connection end and a first resonance branch; the second bridge arm comprises a second switch Q2 and a fifth switch Q5, a B wiring point is connected between the two switches, and the B wiring point is connected with a V phase in the alternating current electric connection end and a second resonance branch; the third bridge arm comprises a third switch Q3 and a sixth switch Q6, a C wiring point is connected between the two switches, and the C wiring point is connected with the W phase in the alternating current electric connection end and the third resonance branch; the first, second and third resonance branches have the same structure and comprise resonance capacitors and resonance inductors which are connected in series; the first, second and third resonant branches are respectively connected with the head ends of three coils on the primary side of the transformer, and the tail ends of the three coils on the primary side of the transformer are connected with each other. The first switch Q1, the second switch Q2 and the third switch Q3 are upper bridge arms, and the upper ends of the upper bridge arms are connected with a positive direct current bus. The fourth switch Q4, the fifth switch Q5 and the sixth switch Q6 are lower arms, and the lower ends thereof are connected to a negative dc bus. The first resonant branch comprises Cr1 and L4 in series, the second resonant branch comprises Cr2 and L5 in series, and the third resonant branch comprises Cr3 and L6 in series.
Referring to fig. 3, the secondary side conversion module includes three pairs of bridge arms formed by 6 switches, wherein an upper bridge arm of the three pairs of bridge arms is connected with a positive pole V + of the power supply, and a lower bridge arm of the three pairs of bridge arms is connected with a negative pole V-; the fourth bridge arm comprises a seventh switch Q7 and a tenth switch Q10, a D wiring point is connected between the two switches, and the D wiring point is connected with one end of a first isolation capacitor Cg 1; the fifth bridge arm comprises an eighth switch Q8 and an eleventh switch Q11, an E wiring point is connected between the two switches, and the E wiring point is connected with one end of a second isolation capacitor Cg 2; the sixth bridge arm comprises a ninth switch Q9 and a twelfth switch Q12, an F wiring point is connected between the two switches, and the F wiring point is connected with one end of a third isolation capacitor Cg 3; the other ends of the first isolation capacitor Cg1, the second isolation capacitor Cg2 and the third isolation capacitor Cg3 are respectively connected with the head ends of the three coils on the secondary side of the transformer, and the tail ends of the three coils on the secondary side of the transformer are connected with each other. The seventh switch Q7, the eighth switch Q8 and the ninth switch Q9 are upper bridge arms, and the upper ends of the seventh switch Q7, the eighth switch Q8 and the ninth switch Q9 are connected with a power supply positive electrode V +. The tenth switch Q10, the eleventh switch Q11 and the twelfth switch Q12 are lower arm, and the lower end thereof is connected to the negative electrode V of the power supply.
The A wiring point is connected with a U phase in an alternating current electric connection end through a first filter inductor L1; the B wiring point is connected with a V phase in the alternating current connection end through a second filter inductor L2; the C connection point is connected to the W phase in the ac electrical connection terminal through a third filter inductor L3. The inductance values of the first, second and third filter inductors are the same.
The battery pack comprises a first capacitor C1 and a second capacitor C2 which are connected in series, and filter capacitors (Cf 1, Cf2 and Cf 3) are respectively connected between a connecting point between the first capacitor C1 and the second capacitor C2 and the U phase, the V phase and the W phase. The filter capacitor is connected to the first capacitor C1 and the second capacitor C2 to decouple the current across the inductors L1-L3. It should be noted that the filter capacitor Cf may be a safety capacitor, and may be made into an input filter module with L1L2L 3.
Referring to fig. 3, the primary side of the transformer is provided with 3 sets of coils, which are correspondingly connected with a U phase, a V phase and a W phase; the secondary side of the transformer is provided with 3 groups of coils which are correspondingly connected with three bridge arms of the secondary side transformation module, and the turn ratio of the transformer coils can be determined according to actual requirements.
The PFC-BUS module and the secondary output module are composed of full-control switching devices, and bidirectional flow of energy can be achieved. In the charging mode, energy flows through the PFC-BUS module by a three-phase power supply, the input alternating current is directly converted into direct current to be used as the primary input of the transformer, and the direct current is output to the secondary output module through the high-frequency transformer to finish the conversion of AC-DC. The invention has the main technical points that one module is adopted to replace a PFC rectification and primary side input module in the prior art, not only can the power factor and current waveform correction be completed, but also the output voltage can be adjusted, and two-stage transformation of the whole circuit shares the same switch device, so that the whole circuit has simple and compact structure and convenient control, and can increase the power supply power of power supply equipment.
Referring to the embodiment shown in fig. 4, a third capacitor C3 and a fourth capacitor C4 are connected in series between the positive power supply V + and the negative power supply V-, and a connection point between the third capacitor C3 and the fourth capacitor C4 is connected with the tail ends of the three coils on the secondary side of the transformer. The third capacitor C3 and the fourth capacitor C4 are filter capacitors at the load end. The tail connection of the transformer is connected to the midpoint of capacitor C3C4 for the purpose of increasing the return current of the circuit. It should be noted that the technique of connecting the connection point of C3 and C4 to the tail ends of the three windings on the secondary side of the transformer is also applicable to other embodiments.
Referring to the embodiment of adding freewheeling switches shown in fig. 6, a thirteenth switch Q13 and a fourteenth switch Q14 are connected in series between the positive dc bus and the negative dc bus, and the connection point between the thirteenth switch Q13 and the fourteenth switch Q14 is connected to the neutral line of the alternating current. In this embodiment, two switches are added on the basis of fig. 3, and the thirteenth switch Q13 and the fourteenth switch Q14 function as free-wheeling switches.
Referring to the circuit diagram of the compatible single three phase AC-DC resonant conversion circuit shown in fig. 7, the U phase of the AC electrical connection is connected in series with the first power switch S1, the V phase is connected in series with the second power switch S2, the W phase is connected in series with the third power switch S3, and the fourth power switch S4 is connected between the a connection point and the first resonant branch. When the external power grid is a three-phase power grid, S1, S2, S3 and S4 are closed, and the conversion circuit operates in a three-phase mode and can be charged or inverted. When the external power grid is a single-phase power grid, S1 is closed, S2, S3 and S4 are opened, the loop structure of the external power grid is shown in FIG. 8, and the conversion circuit operates in a single-phase mode and can be charged or inverted. The input single-phase alternating current is converted into direct current through the PFC-BUS conversion module, then the electric energy is stored on the resonance inductor, and the energy is transmitted to the secondary side conversion module through the transformer. The switch tubes in the secondary side conversion module can be simultaneously opened to perform synchronous rectification and reduce conduction. The power switches S1, S2, S3, and S4 may be single-pole double-throw relays, selection switches, or the like.
In a preferred embodiment, the power switches in the PFC-BUS conversion module and the secondary conversion module both adopt bidirectional switches (also called fully-controlled switches), in the charging mode, the electric energy flows from the PFC-BUS conversion module to the secondary conversion module, and in the inversion mode, the electric energy flows from the secondary conversion module to the PFC-BUS conversion module.
Referring to the embodiment of the added freewheel switch shown in fig. 5, the positive dc bus is connected to the cathode of a first diode D1, the anode of a first diode D1 is connected to the neutral line of the alternating current and to the cathode of a second diode D2, and the anode of a second diode D2 is connected to the negative dc bus. In this embodiment, two switches are added on the basis of fig. 3, and the first diode D1 and the second diode D2 function as free-wheeling switches. Because the diode is not a bidirectional switch, bidirectional transmission of energy cannot be realized, only a charging mode can be realized, and an inversion mode cannot be completed.
One application scenario of the present invention is shown in fig. 13, which includes an ac power grid, a battery pack, and a dc high-voltage load. The battery pack and the direct-current high-voltage load are in an isolated topology, and the alternating-current power grid and the battery pack are in a non-isolated topology. Alternating current electric wire netting passes through PFC-BUS module can directly charge to the group battery, can also directly supply direct current high voltage load to use through DCDC conversion module simultaneously, and these three can all carry out the bidirectional transfer of energy between two liang, has greatly satisfied the multiple demand in present market, and has increased the power density of device, reduce cost.
The invention also discloses a control method of the AC-DC resonance conversion circuit, the conversion circuit adopts the AC-DC resonance conversion circuit, and the control method comprises the following steps:
and 20, controlling the secondary side conversion module to control a pulse signal to follow the PFC-BUS conversion module control pulse signal, and setting a phase shift control angle phi between the PFC-BUS conversion module control pulse signal and the secondary side conversion module control pulse signal.
The invention controls the PFC-BUS conversion module by adopting the duty ratio of the switching tube, the duty ratio of the switching tube of the secondary side conversion module follows the PFC-BUS conversion module, and the control of circuit output is completed by utilizing a phase-shifting control angle. When energy flows to a load end from a three-phase alternating current input end, namely in a charging mode, the energy is firstly rectified by a three-level PFC (power factor correction), is stored in an inductor of a transformer through LC (inductance-capacitance) resonance, and is transmitted to a secondary output module through the transformer; the inverter mode is that energy flows from the load end to the three-phase alternating current input end, and the selected switch tubes are all composed of two-way switches, and the working principle of the inverter mode is the same as that of the charging mode by controlling the switch tubes Q7-Q12 in the secondary output module.
Fig. 9 shows a simulation timing diagram of the control Pulse signals of the PFC-BUS conversion modules Q1-Q6, where the SVPWM modulation algorithm is also called space Vector Pulse Width modulation SVPWM (space Vector Pulse Width modulation), and actually corresponds to a special combination of the switching triggering sequence and the Pulse Width of the three-phase voltage source inverter power device in the ac induction motor or the permanent magnet synchronous motor, and the switching triggering sequence and the combination will generate a sine wave current waveform with three phases having an electrical angle of 120 ° difference and less distortion. The control pulse signals of the switching tubes Q7-Q12 of the secondary side conversion module follow the control pulse signals of the PFC-BUS conversion modules Q1-Q6, the phase-shifting control angle phi is determined by sampling the current value of the output end of the PFC-BUS conversion module, and the phase-shifting control angle phi acts on the pulse signals of Q7-Q12. The invention controls the switch tube of the PFC-BUS conversion module by adopting the duty ratio, controls the switch tube of the secondary side conversion module by phase shifting, and finishes the control of the output current by the modulation method.
Fig. 10 is a graph of the change in resonant inductor current and output current at a phase shift of 15% T, where T is the period of the switching tube pulse signal. Taking Q1 and Q7 switching tubes as examples, the pulse signal of Q7 is shifted to the right by phi degrees compared with the pulse signal of Q1, and the output current i (out) and the current of the resonant inductor L4 change along with the phase shift angle. The switching frequency of the switching tube is far higher than the frequency of a power grid, the input voltage is approximately unchanged in a switching period, the current of the inductor L4 is linearly changed during the conduction period of the Q1 switch, the pulse signal of the Q7 is shifted to the right by an angle phi, at the moment, the Q7 is conducted, and the current of the inductor L4 linearly rises; during the off period of the switching tube Q1, when the Q7 is still in the on state, the current of the inductor L4 is linearly reduced, and the discharge to the load is started, and when both Q1 and Q7 are in the off period, the inductor L4 is in the discharge state. Therefore, the PFC rectifier switching tube adopts the duty ratio setting, and the resonance inductor can synthesize the high-frequency electricity with positive and negative alternation, so that the magnetic reset requirement of the high-frequency transformer is met.
The output current i (out) is related to the phase shift control angle Φ, as shown in fig. 11, and the data is shown in table 1, where the resonant inductance is 15 u. As the phase shift control angle increases, the output current increases and, correspondingly, the output power increases, and the output power can be calculated according to P = UI, assuming that the output voltage is stabilized at 600V, when the phase shift control angle is 0, the output power P1=1.7kW, and when the phase shift angle is 25% T, the output current reaches the maximum, P2=26.7 kW. However, when the phase-shifting control angle exceeds 25% T, the output current will start to decrease, and the relationship between the phase-shifting control angle and the output current is monotonous within the range of [ -25% T, 25% T ] through simulation verification. Therefore, by controlling the phase-shifting angle, the output power of the circuit can be controlled, so that the circuit can meet the application requirement of high power. Wherein the phase shift to the right is a charging mode and the phase shift to the left is an inverting mode. Example (c): 15% T is phase right shift, 15% T is phase left shift.
The phase shift control angle phi in the charging mode is positive, and the phase shift control angle phi in the inverting mode is negative. In a preferred embodiment, the phase shift control angle Φ in the charging mode is 0 to 25% T, and the phase shift control angle Φ in the inverting mode is 0 to-25% T; wherein T is the period of the control pulse signal of the PFC-BUS conversion module.
TABLE 1 relationship of output current to phase-shift control Angle
| Phase-shift |
0 | 5%* |
8%* |
10%* |
15%* |
25%*T | -5%*T | -10%*T | -15%*T | -25%*T |
| Average of output currentvalue/A | 2.88 | 23.097 | 32.024 | 36.559 | 44.09 | 44.56 | -20.67 | -38.08 | -48.03 | -49.98 |
On the other hand, the inductance values of the resonant inductors (L4, L5, L6) in the resonant tank also affect the magnitude of the output current. Fig. 12 is a graph of the effect of resonant inductance L and phase shift control angle Φ on output current, made from simulation data. As mentioned above, the relationship between the average value of the output current and the variation of the phase shift control angle Φ is described, when the resonant inductance is smaller, the average value of the output current is larger, and the output power is also increased, when the resonant inductance Lr =10u and the phase shift control angle is 25% by T, the output voltage is 600V in the charging mode, the output power can reach 40.8Kw, and the output power can reach 48Kw in the inverting mode. Therefore, the output power can be further increased by adjusting the inductance value of the resonant inductor, and the resonant inductor is suitable for the application of some high-power devices.
In an embodiment, the self-inductance of the transformer and the resonant circuit can be in a parallel connection relationship, and only a small exciting current flows through the transformer without influencing the operation of the resonant network. An excitation inductor Lm (see fig. 14, Cr represents a resonant capacitor, and may be Cr1, Cr2, or Cr3, Lr represents a resonant inductor, and may be L4, L5, or L6) is also present in the resonant circuit, and the inductance value of Lm is sufficiently large and can be ignored.
According to the switching frequency
And the resonant frequency
The relationship of (a) is divided into three modes,
、
、
when is coming into contact with
When the circuit is in use, the whole circuit presents capacitance, and the reverse recovery stress of the switch device is large. Since a large reverse recovery current spike cannot flow through the resonant circuit, it will flow through the other MOSFET. This results in large switching losses and current and voltage spikes can cause device failure. Therefore, the converter needs to avoid operating in this area; when in use
When the load is adjusted, the impedance is 0, and the gain Q = 1; when in use
In the process, the excitation inductor Lm is clamped at nV0 by the output voltage through a transformer all the time and does not participate in the resonant operation, and the Lm can be regarded as a passive load of the series resonant converter at the moment. The whole circuit is inductive, a reverse recovery process exists in a switching device, ZVS can be realized by a switching tube, and switching loss is small. As shown in fig. 15, the solid line indicates the switching state of the switching tube Q1, the dotted line indicates the driving voltage of the switching tube Q1, and the driving voltage of the switching tube drops to 0 before the switching tube is turned on and goes through the body diode of the switching tube, so that the switching tube can be realizedThe current 0 voltage is on, the voltage of the switching tube Q1 is 0 when the switching tube Q1 is turned off, and 0 voltage turn-off can be realized, so that the switching loss is greatly reduced. Therefore, the switching frequency setting in the circuit works at
The working area is optimal.
In a preferred embodiment, the PFC-BUS conversion module SVPWM control adopts the Clark conversion and Park conversion control manners, referring to fig. 16, the step 10 includes the following steps:
ud=ed-i* d+id+（iqω L) formula 1
Wherein u isdAdjusting the voltage u for the D-axisd ，edSensing voltage e for axis Dd，i* dFor D-axis reference current i* d ，idDetecting a current i for the D-axisd ，iqDetecting a current i for the Q-axisq ω is the angular frequency of the alternating current, L is the filter inductance value of the alternating current (L1, L2, L3); the relationship between the alternating current angular frequency ω and the frequency f is: ω =2 π f.
Calculating the Q-axis adjustment voltage u according to equation 2q ，
uq=eq-i* q+iq-（idω L) formula 2
Wherein u isqAdjusting the voltage u for the Q-axisq ，eqDetecting voltage e for the Q-axisq，i* qFor Q-axis reference current i* q ，iqDetecting a current i for the Q-axisq ，idDetecting a current i for the D-axisd ω is the angular frequency of the alternating current, L is the filter inductance value of the alternating current (L1, L2, L3);
step 19. adjusting the voltage u to the D-axisd And Q-axis regulated voltage uq And (4) carrying out Park inverse transformation (dq/alpha beta module) and Clark inverse transformation (SVPWM module) to generate a control pulse signal of the PFC-BUS transformation module, and turning to the step 20.
In the preferred embodiment, the Q-axis reference current i* qEqual to zero.
In order to be compatible with a single/three-phase ac power grid, step 10 is preceded by the steps of:
step 9, turning on the first power switch S1, the second power switch S2, the third power switch S3 and the fourth power switch S4, turning to step 10;
step 13, turning on the first power switch S1, turning off the second power switch S2, the third power switch S3 and the fourth power switch S4, and turning to step 14;
and step 14, a first switch Q1, a fourth switch Q4, a thirteenth switch Q13 and a fourteenth switch Q4 form a PFC rectifying module, a second switch Q2, a third switch Q3, a fifth switch Q5 and a sixth switch Q6 form a primary side conversion module, an eighth switch Q8, a ninth switch Q9, an eleventh switch Q11 and a twelfth switch Q12 form a secondary side conversion module, and the controller respectively controls the PFC rectifying module, the primary side conversion module and the secondary side conversion module.
The control method has the beneficial effects that: the circuit can be automatically switched according to the input end, the switching of a three-phase-single-phase circuit is realized, the compatibility of an AC-DC resonance conversion circuit is improved, a switching tube is reused in a two-stage structure of an isolation converter, power factor and current waveform correction can be completed by using the switching tube, and output voltage adjustment can be completed.
The foregoing examples are illustrative only and are not intended to be limiting. Any equivalent modifications or variations without departing from the spirit and scope of the present application should be included in the claims of the present application.
Claims (14)
1. An AC-DC resonance conversion circuit is characterized by comprising an alternating current connection end, a PFC-BUS conversion module, a transformer and a secondary side conversion module which are sequentially connected;
the PFC-BUS conversion module adopts a control pulse signal generated by an SVPWM (space vector pulse width modulation) algorithm to implement switching control, can correct the power factor of input alternating current, converts the alternating current into direct current and transmits the direct current to the primary side of the transformer;
the secondary side conversion module is connected with the secondary side of the transformer and can output direct current; the secondary side conversion module controls the pulse signal to follow the PFC-BUS conversion module control pulse signal, and a phase shift control angle phi is arranged between the PFC-BUS conversion module control pulse signal and the secondary side conversion module control pulse signal.
2. The AC-DC resonant conversion circuit according to claim 1, wherein the PFC-BUS conversion module comprises three pairs of bridge arms consisting of 6 switches, wherein the upper bridge arm of the three pairs of bridge arms is connected with a positive direct current BUS, and the lower bridge arm of the three pairs of bridge arms is connected with a negative direct current BUS;
the first bridge arm comprises a first switch Q1 and a fourth switch Q4, an A wiring point is connected between the two switches, and the A wiring point is connected with a U phase in an alternating current electric connection end and a first resonance branch;
the second bridge arm comprises a second switch Q2 and a fifth switch Q5, a B wiring point is connected between the two switches, and the B wiring point is connected with a V phase in the alternating current electric connection end and a second resonance branch;
the third bridge arm comprises a third switch Q3 and a sixth switch Q6, a C wiring point is connected between the two switches, and the C wiring point is connected with the W phase in the alternating current electric connection end and the third resonance branch;
the first, second and third resonance branches have the same structure and comprise resonance capacitors and resonance inductors which are connected in series; the first, second and third resonant branches are respectively connected with the head ends of three coils on the primary side of the transformer, and the tail ends of the three coils on the primary side of the transformer are connected with each other.
3. The AC-DC resonant conversion circuit according to claim 2, wherein the secondary side conversion module comprises three pairs of bridge arms consisting of 6 switches, wherein the upper bridge arm of the three pairs of bridge arms is connected with a positive pole V + of the power supply, and the lower bridge arm of the three pairs of bridge arms is connected with a negative pole V-;
the fourth bridge arm comprises a seventh switch Q7 and a tenth switch Q10, a D wiring point is connected between the two switches, and the D wiring point is connected with one end of a first isolation capacitor Cg 1;
the fifth bridge arm comprises an eighth switch Q8 and an eleventh switch Q11, an E wiring point is connected between the two switches, and the E wiring point is connected with one end of a second isolation capacitor Cg 2;
the sixth bridge arm comprises a ninth switch Q9 and a twelfth switch Q12, an F wiring point is connected between the two switches, and the F wiring point is connected with one end of a third isolation capacitor Cg 3;
the other ends of the first isolation capacitor Cg1, the second isolation capacitor Cg2 and the third isolation capacitor Cg3 are respectively connected with the head ends of the three coils on the secondary side of the transformer, and the tail ends of the three coils on the secondary side of the transformer are connected with each other.
4. An AC-DC resonant conversion circuit according to claim 2, wherein the a terminal is connected to the U phase in the AC electrical connection terminal through a first filter inductance L1; the B wiring point is connected with a V phase in the alternating current connection end through a second filter inductor L2; the C connection point is connected to the W phase in the ac electrical connection terminal through a third filter inductor L3.
5. An AC-DC resonant conversion circuit according to claim 2, characterized in that the battery pack comprises a first capacitor C1 and a second capacitor C2 connected in series, and filter capacitors (Cf 1, Cf2, Cf 3) are respectively connected between a connection point between the first capacitor C1 and the second capacitor C2 and the U phase, the V phase and the W phase.
6. The AC-DC resonant conversion circuit according to claim 3, wherein a third capacitor C3 and a fourth capacitor C4 are connected in series between the positive power supply V + and the negative power supply V-, and a connection point between the third capacitor C3 and the fourth capacitor C4 is connected with the tail ends of the three windings on the secondary side of the transformer.
7. The AC-DC resonant conversion circuit of claim 2, wherein a thirteenth switch Q13 and a fourteenth switch Q14 are connected in series between the positive DC bus and the negative DC bus, and a connection point between the thirteenth switch Q13 and the fourteenth switch Q14 is connected to the zero line of the alternating current.
8. An AC-DC resonant conversion circuit as claimed in claim 7, wherein the U phase of the AC connection is connected in series with the first power switch S1, the V phase is connected in series with the second power switch S2, the W phase is connected in series with the third power switch S3, and the fourth power switch S4 is connected between the A connection point and the first resonant branch.
9. The AC-DC resonant conversion circuit according to any of claims 1 to 8, wherein the power switches of the PFC-BUS conversion module and the secondary conversion module are bidirectional switches, and in the charging mode, the power flows from the PFC-BUS conversion module to the secondary conversion module, and in the inverting mode, the power flows from the secondary conversion module to the PFC-BUS conversion module.
10. The AC-DC resonant conversion circuit of claim 2, wherein the positive DC bus is connected to the cathode of a first diode D1, the anode of a first diode D1 is connected to the neutral line of the alternating current and the cathode of a second diode D2, and the anode of a second diode D2 is connected to the negative DC bus.
11. An AC-DC resonant conversion circuit control method, wherein the AC-DC resonant conversion circuit according to any one of claims 1 to 9 is used as the conversion circuit, the control method comprising the steps of:
step 10, generating a PFC-BUS conversion module control pulse signal according to an SVPWM (space vector pulse width modulation) algorithm;
and 20, controlling the secondary side conversion module to control a pulse signal to follow the PFC-BUS conversion module control pulse signal, and setting a phase shift control angle phi between the PFC-BUS conversion module control pulse signal and the secondary side conversion module control pulse signal.
12. The AC-DC resonant conversion circuit control method of claim 11, wherein the phase shift control angle Φ in the charging mode is positive, and the phase shift control angle Φ in the inverting mode is negative.
13. An AC-DC resonant conversion circuit control method according to claim 12, wherein the phase shift control angle Φ in the charging mode is 0 to 25% T, and the phase shift control angle Φ in the inverting mode is 0 to-25% T; wherein T is the period of the control pulse signal of the PFC-BUS conversion module.
14. The AC-DC resonant conversion circuit control method of claim 11, further comprising, before said step 10, the step of:
step 8, detecting alternating current, if the alternating current is three-phase alternating current to step 9, if the alternating current is single-phase alternating current to step 13;
step 9, turning on the first power switch S1, the second power switch S2, the third power switch S3 and the fourth power switch S4, turning to step 10;
step 13, turning on the first power switch S1, turning off the second power switch S2, the third power switch S3 and the fourth power switch S4, and turning to step 14;
and step 14, a first switch Q1, a fourth switch Q4, a thirteenth switch Q13 and a fourteenth switch Q4 form a PFC rectifying module, a second switch Q2, a third switch Q3, a fifth switch Q5 and a sixth switch Q6 form a primary side conversion module, an eighth switch Q8, a ninth switch Q9, an eleventh switch Q11 and a twelfth switch Q12 form a secondary side conversion module, and the controller respectively controls the PFC rectifying module, the primary side conversion module and the secondary side conversion module.
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