CN111864776B - Charging device of super-capacitor energy storage station and control method - Google Patents

Charging device of super-capacitor energy storage station and control method Download PDF

Info

Publication number
CN111864776B
CN111864776B CN201910360424.1A CN201910360424A CN111864776B CN 111864776 B CN111864776 B CN 111864776B CN 201910360424 A CN201910360424 A CN 201910360424A CN 111864776 B CN111864776 B CN 111864776B
Authority
CN
China
Prior art keywords
voltage
signal
current
capacitor
converter
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
CN201910360424.1A
Other languages
Chinese (zh)
Other versions
CN111864776A (en
Inventor
康颖
毛凯
张艳清
蔡华
韦克康
赵克
凡绍贵
季旭
杜修方
胡良辉
朱然
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Harbin Institute of Technology
Casic Feihang Technology Research Institute of Casia Haiying Mechanical and Electronic Research Institute
Original Assignee
Harbin Institute of Technology
Casic Feihang Technology Research Institute of Casia Haiying Mechanical and Electronic Research Institute
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Harbin Institute of Technology, Casic Feihang Technology Research Institute of Casia Haiying Mechanical and Electronic Research Institute filed Critical Harbin Institute of Technology
Priority to CN201910360424.1A priority Critical patent/CN111864776B/en
Publication of CN111864776A publication Critical patent/CN111864776A/en
Application granted granted Critical
Publication of CN111864776B publication Critical patent/CN111864776B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/28—Arrangements for balancing of the load in a network by storage of energy
    • H02J3/32—Arrangements for balancing of the load in a network by storage of energy using batteries with converting means
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/34—Parallel operation in networks using both storage and other dc sources, e.g. providing buffering
    • H02J7/345—Parallel operation in networks using both storage and other dc sources, e.g. providing buffering using capacitors as storage or buffering devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T90/00—Enabling technologies or technologies with a potential or indirect contribution to GHG emissions mitigation
    • Y02T90/10—Technologies relating to charging of electric vehicles
    • Y02T90/12—Electric charging stations

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Rectifiers (AREA)

Abstract

The invention provides a charging device and a control method for a super-capacitor energy storage station, wherein the device comprises a three-phase four-wire PWM rectifier, an isolated three-level DC/DC converter, a first bus capacitor subunit and a second bus capacitor subunit; an alternating current input port of the three-phase four-wire PWM rectifier is connected with a power grid system in parallel, a high-voltage input port of the isolation three-level DC/DC converter is connected with a direct current output port of the three-phase four-wire PWM rectifier, and a low-voltage output port of the isolation three-level DC/DC converter is connected with a super capacitor bank; and the first bus capacitor subunit and the second bus capacitor subunit are connected in series and then connected in parallel to a direct current output port of the three-phase four-wire PWM rectifier. The charging device for the super-capacitor energy storage station can realize isolated charging with small volume and high efficiency. The device adopts the maximum power charge control strategy, can reduce the charge time to shorten the preparation time in earlier stage.

Description

Charging device of super-capacitor energy storage station and control method
Technical Field
The invention relates to the technical field of power system control, in particular to a charging device of a super-capacitor energy storage station and a control method.
Background
One of the key technologies supporting electromagnetic emission technology is pulsed power technology. The pulse power supply based on super capacitor energy storage has the characteristics of long service life, large instantaneous power, wide working temperature range and the like, and can be used as a pulse power supply for electromagnetic emission. Before electromagnetic emission, the super capacitor energy storage station should be charged to a full charge state. Considering that electromagnetic emission is generally installed on a launching vehicle or a ship and other mobile carriers, a high-quality power grid cannot be provided, and the installation space is limited, the charging device for the super-capacitor energy storage station has strong adaptability to the power grid and has a small size. In view of safety, a transformer should be used to electrically isolate the super capacitor energy storage station from the grid. A conventional energy storage device charging topology is shown in fig. 1.
Referring to fig. 1, a conventional energy storage device charging topology adopts a two-stage structure, and a three-phase three-wire PWM rectifier is adopted at a front stage to convert ac power into dc power, so as to achieve unit power factor rectification. And the rear stage adopts a phase-shifted full-bridge DC/DC converter to charge the super capacitor bank, so that isolated charging is realized.
The voltage stress of a switch tube of a phase-shifted full-bridge converter adopted by the traditional energy storage device charging topology is direct-current bus voltage. Because the PWM rectifier has a boosting function, the direct current bus voltage is higher. The voltage level of the switching tube adopted by the phase-shifted full-bridge converter is higher, and the switching tube with a high voltage level often has a lower switching frequency. A lower switching frequency results in a larger high-frequency transformer volume and a larger ripple current.
Disclosure of Invention
The invention provides a charging device and a control method for a super-capacitor energy storage station, and aims to solve the problems that a high-frequency transformer is large in size and large in output current ripple due to the fact that a DC/DC converter of a traditional charging device is low in switching frequency.
In one aspect of the invention, a charging device for a super capacitor energy storage station is provided, the device comprises a three-phase four-wire PWM rectifier, an isolated three-level DC/DC converter, a first bus capacitor subunit and a second bus capacitor subunit;
an alternating current input port of the three-phase four-wire PWM rectifier is connected with a power grid system in parallel, a high-voltage input port of the isolation three-level DC/DC converter is connected with a direct current output port of the three-phase four-wire PWM rectifier, and a low-voltage output port of the isolation three-level DC/DC converter is connected with a super capacitor bank;
and the first bus capacitor subunit and the second bus capacitor subunit are connected in series and then connected in parallel to a direct current output port of the three-phase four-wire PWM rectifier.
The isolation three-level DC/DC converter comprises an upper half-bridge submodule, a lower half-bridge submodule, a first capacitor unit and a first transformer unit;
the direct current input end of the upper half-bridge submodule is connected to the first bus capacitor subunit in parallel, the direct current input end of the lower half-bridge submodule is connected to the second bus capacitor subunit in parallel, the upper half-bridge submodule and the lower half-bridge submodule respectively comprise a bridge arm midpoint, and the bridge arm midpoints of the upper half-bridge submodule and the lower half-bridge submodule are connected to a primary winding of the first transformer in series through the first capacitor unit.
The isolated three-level DC/DC converter further comprises a first commutation auxiliary circuit and a second commutation auxiliary circuit;
the first commutation auxiliary circuit comprises a first auxiliary inductor and a first auxiliary capacitor, one end of the first auxiliary inductor is connected with the middle point of a bridge arm of the upper half-bridge sub-module, the other end of the first auxiliary inductor is connected with the anode of the first auxiliary capacitor, and the cathode of the first auxiliary capacitor is connected with the cathode of the first bus capacitor sub-unit;
the second commutation auxiliary circuit comprises a second auxiliary inductor and a second auxiliary capacitor, one end of the second auxiliary inductor is connected with the middle point of a bridge arm of the lower half-bridge submodule, the other end of the second auxiliary inductor is connected with the anode of the second auxiliary capacitor, and the cathode of the second auxiliary capacitor is connected with the cathode of the second bus capacitor subunit.
The isolated three-level DC/DC converter further comprises an AC/DC conversion unit connected with the secondary winding of the first transformer, and an alternating current port of the AC/DC conversion unit is connected to the secondary winding of the first transformer.
The charging device of the super-capacitor energy storage station further comprises a control circuit;
and the control circuit is respectively connected with the three-phase four-wire PWM rectifier and the isolated three-level DC/DC converter and is used for controlling the working parameters of the three-phase four-wire PWM rectifier and the isolated three-level DC/DC converter.
In another aspect of the present invention, there is also provided a control method applied to the charging device of the super capacitor energy storage station, the method including:
setting signal u according to DC voltageDCAnd collected DC side voltage uDCCalculating positive and negative sequence dq axis voltage control signals;
converting the positive and negative sequence dq axis voltage control signals into positive and negative sequence alpha beta axis voltage control signals;
according to the voltage u of the first bus capacitor subunitDC1And the voltage u of the second bus capacitor subunitDC2Calculating a zero sequence voltage control signal;
generating three-phase PWM driving signals of the three-phase four-wire PWM rectifier according to the positive and negative sequence alpha beta shaft voltage control signals and the zero sequence voltage control signal;
and realizing output control of the isolated three-level DC/DC converter by adopting output current closed-loop control.
Wherein the given signal u is based on a DC voltageDCAnd collected DC side voltage uDCCalculating positive and negative sequence dq axis voltage control signals, comprising:
giving a DC voltage to a signal uDCAnd collected DC side voltage uDCComparing to obtain a direct voltage deviation signal;
inputting the direct voltage deviation signal into a first PI controllerTaking the output signal of the first PI controller as a current given signal i of a current loopDC*；
According to the current given signal iDCSum of DC voltage given signal uDCCalculating an active power given signal;
calculating a grid current positive and negative sequence dq axis component according to the grid voltage dq axis component signal and the active power given signal;
inputting the grid current positive sequence d-axis component into a second PI controller, and taking an output signal of the second PI controller as a positive sequence d-axis voltage control signal;
inputting the grid current positive sequence q-axis component into a third PI controller, and taking an output signal of the third PI controller as a positive sequence q-axis voltage control signal;
inputting the grid current negative sequence d-axis component into a fourth PI controller, and taking an output signal of the fourth PI controller as a negative sequence d-axis voltage control signal;
and inputting the grid current negative sequence q-axis component into a fifth PI controller, and taking an output signal of the fifth PI controller as a negative sequence q-axis voltage control signal.
Wherein the voltage u according to the first bus capacitor subunitDC1And the voltage u of the second bus capacitor subunitDC2Calculating zero sequence voltage control signal v0An apparatus, comprising:
converting the voltage u of the first bus capacitor subunitDC1And the voltage u of the second bus capacitor subunitDC2Comparing to obtain an output capacitance voltage difference signal;
inputting the output capacitance voltage difference signal into a sixth PI controller, wherein the output signal of the sixth PI controller is used as a zero-sequence current given signal i0*；
Giving a zero sequence current to a signal i0Sum collected zero sequence current i0Comparing to obtain a zero sequence current difference signal;
inputting the zero sequence current difference signal into a seventh PI controller, and using the output signal of the seventh PI controller as zero sequence voltage controlSystem signal v0*。
The super-capacitor energy storage station charging device provided by the embodiment of the invention is divided into two stages, wherein the front stage adopts a three-phase four-wire PWM rectifying device to convert alternating current into direct current, so that unit power factor rectification is realized, two-path series voltage is provided for the rear stage isolation three-level DC/DC converter, and the rear stage adopts the isolation three-level DC/DC converter to charge a super-capacitor bank, so that small-size and high-efficiency isolation charging is realized.
The control method of the charging device of the super-capacitor energy storage station provided by the embodiment of the invention adopts a maximum power charging strategy, and reduces the charging time, thereby shortening the early-stage preparation time of equipment.
The foregoing description is only an overview of the technical solutions of the present invention, and the embodiments of the present invention are described below in order to make the technical means of the present invention more clearly understood and to make the above and other objects, features, and advantages of the present invention more clearly understandable.
Drawings
Various other advantages and benefits will become apparent to those of ordinary skill in the art upon reading the following detailed description of the preferred embodiments. The drawings are only for purposes of illustrating the preferred embodiments and are not to be construed as limiting the invention. Also, like reference numerals are used to refer to like parts throughout the drawings. In the drawings:
FIG. 1 is a schematic circuit diagram of a conventional charging apparatus for a super capacitor energy storage station in the prior art;
fig. 2 is a schematic circuit diagram of a charging device for a super capacitor energy storage station according to an embodiment of the present invention;
FIG. 3 is a schematic circuit diagram of another charging apparatus for a super capacitor energy storage station according to an embodiment of the present invention;
FIG. 4 is a waveform diagram illustrating an isolated three-level DC/DC converter in an embodiment of the present invention;
FIG. 5 is a first schematic diagram illustrating the current flow of the isolated three-level DC/DC converter according to the embodiment of the present invention;
FIG. 6 is a schematic diagram illustrating the current flow of the isolated three-level DC/DC converter according to the embodiment of the present invention;
FIG. 7 is a third schematic diagram illustrating the current flow of the isolated three-level DC/DC converter according to the embodiment of the present invention;
FIG. 8 is a current flow diagram of the isolated three-level DC/DC converter of the present invention;
FIG. 9 is a schematic diagram of the current flow of the isolated three-level DC/DC converter of the embodiment of the present invention;
FIG. 10 is a sixth schematic illustrating the current flow of the isolated three-level DC/DC converter of the present invention;
FIG. 11 is a seventh schematic diagram illustrating the current flow of the isolated three-level DC/DC converter of the present invention;
FIG. 12 is a schematic diagram illustrating the current flow of the isolated three-level DC/DC converter according to an embodiment of the present invention;
FIG. 13 is a ninth schematic diagram illustrating the current flow of the isolated three-level DC/DC converter according to the present invention;
FIG. 14 is a current flow diagram illustrating a method for isolating a three-level DC/DC converter according to an embodiment of the present invention;
fig. 15 is a flowchart of a control method of a charging device of a super capacitor energy storage station according to an embodiment of the present invention;
FIG. 16 is a block diagram illustrating the overall control of a charging apparatus for a super capacitor energy storage station according to an embodiment of the present invention;
FIG. 17 is a control block diagram of a three-phase four-wire PWM rectifier according to an embodiment of the present invention;
FIG. 18 is a block diagram of a grid voltage positive and negative sequence dq component voltage detection control according to an embodiment of the present invention;
fig. 19 is a control block diagram of an isolated three-level DC/DC converter according to an embodiment of the present invention.
Detailed Description
Exemplary embodiments of the present disclosure will be described in more detail below with reference to the accompanying drawings. While exemplary embodiments of the present disclosure are shown in the drawings, it should be understood that the present disclosure may be embodied in various forms and should not be limited to the embodiments set forth herein. Rather, these embodiments are provided so that this disclosure will be thorough and complete, and will fully convey the scope of the disclosure to those skilled in the art.
As used herein, the singular forms "a", "an", "the" and "the" are intended to include the plural forms as well, unless the context clearly indicates otherwise. It will be further understood that the terms "comprises" and/or "comprising," when used in this specification, specify the presence of stated features, integers, steps, operations, elements, and/or components, but do not preclude the presence or addition of one or more other features, integers, steps, operations, elements, components, and/or groups thereof.
It will be understood by those skilled in the art that, unless otherwise defined, all terms (including technical and scientific terms) used herein have the same meaning as commonly understood by one of ordinary skill in the art to which this invention belongs. It will be further understood that terms, such as those defined in commonly used dictionaries, should be interpreted as having a meaning that is consistent with their meaning in the context of the prior art and will not be interpreted in an idealized or overly formal sense unless expressly so defined herein.
Fig. 2 schematically shows a circuit block diagram of a charging device for a super capacitor energy storage station according to an embodiment of the present invention. Referring to fig. 2, the charging apparatus for a super capacitor energy storage station according to an embodiment of the present invention includes a three-phase four-wire PWM rectifier 10, an isolated three-level DC/DC converter 20, a first bus capacitor subunit 30, and a second bus capacitor subunit 40. Wherein:
an alternating current input port of the three-phase four-wire PWM rectifier 10 is connected to a power grid system in parallel, a high-voltage input port of the isolation three-level DC/DC converter 20 is connected to a direct current output port of the three-phase four-wire PWM rectifier 10, and a low-voltage output port of the isolation three-level DC/DC converter 20 is connected to a super capacitor bank;
the first bus capacitor subunit 10 and the second bus capacitor subunit 20 are connected in series and then connected in parallel to a direct current output port of the three-phase four-wire PWM rectifier.
In one embodiment, as shown in FIG. 3, the isolated three-level DC/DC converter 20 includes an upper half-bridge sub-module 201,Lower half-bridge submodule 202 and first capacitor unit CbAnd a first transformer unit 203, wherein the transformer leakage inductance of the first transformer unit 203 is Lr；
The dc input end of the upper half-bridge submodule 201 is connected to the first bus capacitor subunit 30 in parallel, the dc input end of the lower half-bridge submodule 202 is connected to the second bus capacitor subunit 40 in parallel, the upper half-bridge submodule 201 and the lower half-bridge submodule 202 respectively include a bridge arm midpoint, and the first capacitor unit CbThe bridge leg midpoints of the upper half-bridge submodule 201 and the lower half-bridge submodule 202 are connected in series to a primary winding of the first transformer 203.
Further, as shown in fig. 3, the isolated three-level DC/DC converter 20 further includes a first commutation auxiliary circuit 204 and a second commutation auxiliary circuit 205, where the first commutation auxiliary circuit 204 includes a first auxiliary inductor LA1And a first auxiliary capacitor CA1The first auxiliary inductor LA1One end of the first auxiliary capacitor C is connected to the middle point of the bridge arm of the upper half-bridge sub-module 201, and the other end of the first auxiliary capacitor C is connected to the first auxiliary capacitor CA1The first auxiliary capacitor CA1Is connected to the negative pole of the first bus capacitor subunit 30;
the second commutation auxiliary circuit 205 comprises a second auxiliary inductor LA2And a second auxiliary capacitor CA2Said second auxiliary inductance LA2Is connected to the bridge arm midpoint of the lower half-bridge sub-module 202, and the other end is connected to the second auxiliary capacitor CA2The second auxiliary capacitor CA2Is connected to the negative pole of the second bus capacitor subunit 40.
In this embodiment, the isolated three-level DC/DC converter 20 further includes an AC/DC conversion unit connected to the secondary winding of the first transformer, and an AC port of the AC/DC conversion unit is connected to the secondary winding of the first transformer.
In this embodiment, the charging device of the super capacitor energy storage station further includes a control circuit; and the control circuit is respectively connected with the three-phase four-wire PWM rectifier and the isolated three-level DC/DC converter and is used for controlling the working parameters of the three-phase four-wire PWM rectifier and the isolated three-level DC/DC converter.
The invention is illustrated in detail below by means of a specific example.
As shown in FIG. 3, the three-phase four-wire PWM rectifier outputs two-way voltage uDC1，uDC2And supplying power to the isolated three-level DC/DC converter. Switch tube S1，S2Forming an upper half-bridge, S, of an isolated three-level DC/DC converter3，S4Form a lower half-bridge, LrIs leakage inductance of transformer, CbIs a dc blocking capacitor. C1～C4The equivalent parallel capacitor of the main switch tube comprises a switch tube parasitic capacitor and a parallel buffer capacitor, and the equivalent parallel capacitor can realize zero voltage turn-off of the switch tube, C1～C4Voltages are respectively VS1～VS4. Switch tube S2,S4ZVS is easier to implement because the energy to implement ZVS comes from the output filter inductance as well as the transformer leakage inductance. And S1,S3ZVS is not easily implemented because the energy to implement ZVS comes only from transformer leakage inductance. The proposed isolated three-level DC/DC converter adopts a converter auxiliary circuit and a switching tube S1～S4ZVS can be achieved over the full load range. The commutation auxiliary circuit is composed of a small auxiliary inductor LAA capacitor CAAnd (4) forming. Auxiliary inductor LAIs a small resonant inductor, capacitor CALarge enough that the voltage across the capacitor can be considered constant during one cycle. Fig. 4 is a schematic diagram of waveforms of an isolated three-level DC/DC converter including a commutation auxiliary circuit according to an embodiment of the present invention, where the positive direction of voltage and current is shown in fig. 3. One switching cycle is divided into 10 stages, and the current flow in each stage is shown in fig. 5 to 14. Capacitance C is assumed before analysisd1，Cd2Voltage uDC1＝uDC2＝Vin/2, blocking capacitance CbVoltage Vb＝Vin/2, the output inductance is sufficient that the output current I can be assumedoThe capacitance C remaining constant during a periodA1，CA2Large enough to assume electricityPressure VCA1，VCA2Is kept constant for one period. The analysis at each stage is as follows:
stage 1 (t)0～t1): referring to FIG. 5, the switch tubes S1, S4 are turned on, and the capacitor C is turned ond1，Cd2To the load and blocking capacitor CbAnd (5) supplying power. Capacitor Cd1Through a switch tube S1 to CA1Charging, bringing in a current iA1The linearity decreases. Capacitor CA2Discharging through a switching tube S4 to bring a current iA2Increasing linearly. Current iA1，iA2The variation at this stage can be expressed as formulas (1), (2).
Figure BDA0002046688960000081
Figure BDA0002046688960000082
Stage 2 (t)1～t2): see FIG. 6, t1At the moment, the switching tube S1 is turned off, and S1 achieves zero-voltage turn-off due to the clamping effect of the snubber capacitor C1. Current iA1And iLrC1 was charged and C2 was discharged. When the voltage of C2 is discharged to zero, the switch tube S2 reaches the zero voltage switch-on condition, t2At this time, the switch tube S2 realizes zero voltage turn-on. Due to the large output filter inductance, enough energy can be provided for the S2 soft switch. Even if the output current is small, because of the current iA1The S2 can also realize soft switching smoothly under the discharging action of C2.
Stage 3 (t)2～t3): see FIG. 7, t2At this time, the switch tube S2 is turned on at zero voltage. Current iLrWill flow through freewheeling diode D2 due to uDC2＝Vb＝Vin/2, thus the transformer winding voltage VmAt 0, the converter enters the freewheel phase. Current iA1Linear increase, as shown in equation (3).
Figure BDA0002046688960000091
In the formula
Figure BDA0002046688960000092
Stage 4 (t)3～t4): see FIG. 8, t3At the moment, the switching tube S4 is turned off, and S4 achieves zero-voltage turn-off due to the clamping effect of the snubber capacitor C4. Current iA2And iLrC4 was charged and C3 was discharged. When the voltage of C3 discharges to zero, the switch tube S3 reaches the zero voltage turn-on condition, t4At this time, the switch tube S3 realizes zero voltage turn-on. The stage is in a follow current stage, and the energy for realizing soft switching comes from the leakage inductance of the transformer and iA2. Due to the auxiliary current iA2The S3 can smoothly realize soft switching for the discharging action of the C3.
Stage 5 (t)4～t5): referring to FIG. 9, the switch tubes S2, S3 are turned on, and the capacitor C is turned onbPower is supplied to the load. Capacitor Cd2Through a switch tube S3 to CA2Charging, bringing in a current iA2The linearity decreases. Capacitor CA1Discharging through a switching tube S2 to bring a current iA1Increasing linearly. Current iA2The variation at this stage can be expressed as formula (4).
Figure BDA0002046688960000093
In the formula
Figure BDA0002046688960000094
Stage 6 (t)5～t6): referring to FIG. 10, at t5, current iA2Decreases to zero, starts to reverse, and the current iA1Increasing to zero and starting the reverse. Current iA2Continue to decrease iA1The increase is continued as shown in formulas (5) and (6).
Figure BDA0002046688960000095
Figure BDA0002046688960000096
Stage 7 (t)6～t7): see FIG. 11, t6At the moment, the switching tube S3 is turned off, and S3 achieves zero-voltage turn-off due to the clamping effect of the snubber capacitor C3. Current iA2And iLrC3 was charged and C4 was discharged. When the voltage of C4 discharges to zero, the switch tube S4 reaches the zero voltage turn-on condition, t7At this time, the switch tube S4 realizes zero voltage turn-on. Due to the large output filter inductance, enough energy can be provided for the S4 soft switch. Even if the output current is small, because of the current iA2The S4 can also realize soft switching smoothly for the discharging action of C4.
Stage 8 (t)7～t8): see FIG. 12, t7At this time, the switch tube S4 is turned on at zero voltage. Current iLrWill flow through freewheeling diode D4 due to uDC2＝Vb＝Vin/2, thus the transformer winding voltage VmAt 0, the converter enters the freewheel phase again. Current iA2Linear increase, as shown in equation (7).
Figure BDA0002046688960000101
In the formula
Figure BDA0002046688960000102
Stage 9 (t)8～t9): see FIG. 13, t8At the moment, the switching tube S2 is turned off, and S2 achieves zero-voltage turn-off due to the clamping effect of the snubber capacitor C2. Current iA1And iLrC2 was charged and C1 was discharged. When the voltage of C1 discharges to zero, the switch tube S1 reaches the zero voltage turn-on condition, t9At this time, the switch tube S1 realizes zero voltage turn-on. The stage is in a follow current stage, and the energy for realizing soft switching comes from the leakage inductance of the transformer and iA1. Due to the auxiliary current iA1Discharge to C1In effect, S1 can smoothly realize soft switching.
Stage 10 (t)9～t10): referring to FIG. 14, the switch tubes S1, S4 are turned on, and the capacitor C is turned ond1，Cd2To the load and blocking capacitor CbAnd (5) supplying power. Capacitor Cd1Through a switching tube S1 to CA1Charging, bringing in a current iA1The linearity decreases. Capacitor CA2Discharging through a switching tube S4 to bring a current iA2Increasing linearly. At t10Current iA1Reduced to zero, current iA2Increasing to zero, the cycle ends and a new cycle begins.
According to the analysis, the voltage stress of the switching tube of the proposed isolated three-level DC/DC converter is VinAnd 2, a low-voltage grade switching tube can be selected, so that higher switching frequency is realized. And the adopted commutation auxiliary circuit can realize soft switching in a full-load range, thereby further improving the switching frequency and improving the efficiency of the converter.
Fig. 15 is a flowchart of a control method applied to the charging device of the super capacitor energy storage station according to the embodiment of the present invention. Referring to fig. 15, the control method of the charging device for the super capacitor energy storage station according to the embodiment of the present invention specifically includes the following steps:
s101, setting a signal u according to the direct-current voltageDCAnd collected DC side voltage uDCCalculating positive and negative sequence dq axis voltage control signals;
s102, converting the positive and negative sequence dq axis voltage control signals into positive and negative sequence alpha beta axis voltage control signals;
s103, according to the voltage u of the first bus capacitor subunitDC1And the voltage u of the second bus capacitor subunitDC2Calculating a zero sequence voltage control signal;
s104, generating three-phase PWM driving signals of the three-phase four-wire PWM rectifier according to the positive and negative sequence alpha beta shaft voltage control signals and the zero sequence voltage control signal;
and S105, realizing output control of the isolated three-level DC/DC converter by adopting output current closed-loop control.
Considering that electromagnetic emission is generally installed on a mobile carrier such as a launch vehicle or a ship and the like, a high-quality power grid cannot be provided, the PWM rectifying device should be capable of normally operating under an unbalanced power grid and achieving unity power factor rectification. The three-phase four-wire PWM rectification also needs to provide two stable and equal-voltage voltages for the rear-stage isolation three-level DC/DC converter. The isolated three-level DC/DC converter realizes the control of the charging current, so the closed-loop control of the output current is adopted. The proposed overall control strategy for the charging device of the super capacitor energy storage station is shown in fig. 16.
In a specific embodiment, the signal u is given according to a DC voltageDCAnd collected DC side voltage uDCCalculating positive and negative sequence dq axis voltage control signals, specifically comprising: giving a DC voltage to a signal uDCAnd collected DC side voltage uDCComparing to obtain a direct voltage deviation signal; inputting the direct voltage deviation signal into a first PI controller, and taking the output signal of the first PI controller as a current given signal i of a current loopDCA first step of; according to the current given signal iDCSum of DC voltage given signal uDCCalculating an active power given signal; calculating a grid current positive and negative sequence dq axis component according to the grid voltage dq axis component signal and the active power given signal; inputting the grid current positive sequence d-axis component into a second PI controller, and taking an output signal of the second PI controller as a positive sequence d-axis voltage control signal; inputting the grid current positive sequence q-axis component into a third PI controller, and taking an output signal of the third PI controller as a positive sequence q-axis voltage control signal; inputting the grid current negative sequence d-axis component into a fourth PI controller, and taking an output signal of the fourth PI controller as a negative sequence d-axis voltage control signal; and inputting the grid current negative sequence q-axis component into a fifth PI controller, and taking an output signal of the fifth PI controller as a negative sequence q-axis voltage control signal.
In the embodiment of the invention, the three-phase four-wire PWM rectifier realizes the closed-loop control of output voltage and the balanced control of the voltage difference of the output capacitor, and the DC/DC converter realizes the closed-loop control of output current.
Under the unbalanced power grid, the PWM output voltage can generate double-frequency fluctuation, and positive and negative sequence dq axis components can be respectively controlled by adopting a positive and negative sequence separation method to inhibit the fluctuation of the output voltage. Meanwhile, the zero-sequence component is controlled by the voltage difference of the output capacitor, and the control block diagram of the three-phase four-wire PWM rectifier is shown in FIG. 17.
As shown in fig. 17, the output capacitance voltage difference control loop is independent of the power control loop, the output capacitance voltage difference control system is set to zero, a zero-sequence current set signal is generated after PI closed-loop control, and a zero-sequence voltage set signal is generated after zero-sequence current closed-loop control. DC voltage uDCAfter PI closed loop, a current given signal is generated and multiplied by a voltage given signal to obtain an active power given signal. Under the unbalanced power grid, the power generated by the positive sequence voltage and the negative sequence current is as shown in the formula (8).
Figure BDA0002046688960000121
In the formula
Figure BDA0002046688960000122
For the grid voltage dq axis positive sequence component,
Figure BDA0002046688960000123
is the negative sequence component of the grid voltage dq axis,
Figure BDA0002046688960000124
for the grid-connected current dq axis positive sequence component,
Figure BDA0002046688960000125
for negative sequence component of grid-connected current dq axis, P0Active power DC component, Pc2 Active power 2 frequency multiplication cosine oscillation component, Ps2 Active power 2 frequency multiplication sinusoidal oscillation component, Q0Reactive power DC component, Qc2 Reactive power 2 times the cosine oscillation component, Qs2The reactive power 2 multiplies the frequency of the sinusoidal oscillation component.
The control quantity of the controller is
Figure BDA0002046688960000126
Four degrees of freedom, and power has P0,Pc2,Ps2,Q0,Qc2,Qs2And the six degrees of freedom can only select four powers to control. Active P0Must be controlled, and secondly, in order to avoid the double frequency fluctuation of the direct current bus, the double frequency component P of the active powerc2＝0，P s20. To achieve unity power factor grid connection, reactive power Q 00. Thus P0,Pc2,Ps2,Q0Is selected, the expression of which is shown in equation (9). Active power DC component setting
Figure BDA0002046688960000131
Is obtained by outputting a direct current voltage closed loop,
Figure BDA0002046688960000132
Figure BDA0002046688960000133
given the known power, for the matrix M4×4Inversion can be carried out, and a given expression of the dq-axis current can be obtained as shown in the formula (10).
Figure BDA0002046688960000134
Figure BDA0002046688960000135
In the formula
Figure BDA0002046688960000136
From equation (10), it can be seen that, in addition to the power specification, the grid voltage dq axis component needs to be obtained
Figure BDA0002046688960000137
Figure BDA0002046688960000138
The current dq axis setpoint can be obtained. In the voltage detection process, dq axis components influence each other and contain 2 frequency multiplication oscillation. A simple approach is to eliminate the 2 times frequency oscillation by adding a wave trap. However, the wave trap reduces the system phase angle margin, which deteriorates the system stability. A positive and negative sequence decoupling voltage detection method is adopted. The dq-axis component of the grid voltage can be expressed as shown in equation (11).
Figure BDA0002046688960000139
In the formula
Figure BDA00020466889600001310
Is the average value of positive sequence and negative sequence components, is useful information,
Figure BDA00020466889600001311
is a transformation matrix, as shown in equation (12).
Figure BDA00020466889600001312
In the formula, omega is the grid voltage vector angular frequency obtained by the phase-locked loop.
The grid voltage positive and negative sequence dq-axis component detection control obtained according to equation (11) is shown in fig. 18. The average value of the dq axis components is obtained through filtering by a Low Pass Filter (LPF), and then the average value is utilized to decouple the alternating current, so that the oscillation of the output average value is effectively reduced. The LPF cut-off frequency can be selected from the group consisting of attenuation of AC signals and rapidity
Figure BDA00020466889600001313
Where ω is the grid angular frequency. The method for detecting the positive and negative sequence dq axis components of the power grid current is the same as the voltage detection method.
As shown in FIG. 17, after positive and negative sequence currents are decoupled through dq axes, the PI regulators can be controlled in a closed loop mode according to engineering design through the PI regulatorsAnd (4) designing a method. And (3) obtaining a dq axis voltage control signal after current closed-loop control, and then converting the dq axis control voltage to an alpha beta axis through conversion shown in a formula (13). The zero sequence voltage control signal is obtained by an output capacitor voltage difference control loop. Generating three-phase PWM driving signal S according to given alpha beta 0 axis voltageabc。
Figure BDA0002046688960000141
The above is a control method of three-phase four-wire PWM rectification.
In a specific embodiment, the voltage u according to the first bus capacitor subunitDC1And the voltage u of the second bus capacitor subunitDC2Calculating zero sequence voltage control signal v0Specifically, the method comprises the following steps: converting the voltage u of the first bus capacitor subunitDC1And the voltage u of the second bus capacitor subunitDC2Comparing to obtain an output capacitance voltage difference signal; inputting the output capacitance voltage difference signal into a sixth PI controller, wherein the output signal of the sixth PI controller is used as a zero-sequence current given signal i0A first step of; giving a zero sequence current to a signal i0Sum collected zero sequence current i0Comparing to obtain a zero sequence current difference signal; inputting the zero sequence current difference signal into a seventh PI controller, and using the output signal of the seventh PI controller as a zero sequence voltage control signal v0*。
In the embodiment of the invention, the isolated three-level DC/DC converter charges the super capacitor bank, so that an output current closed-loop control strategy is adopted for the converter. Modeling the isolated three-level DC/DC converter by adopting a state space averaging method to obtain a converter with a steady-state working point VSC＝DuDCAnd/2 n, the transfer function of the duty cycle to the output current is shown as equation (14).
Figure BDA0002046688960000142
N transformer transformation ratio, uDCInput DC bus voltage，LoAnd outputting the filter inductor.
The output current closed loop control block diagram is shown in FIG. 19, where Gfi(s) is the current sampling link transfer function, TsIs a PWM period. The PI regulator can be designed by adopting an engineering design method, and the system is designed into a typical II-type system.
In order to realize the quick charging of the super capacitor bank and reduce the transmission preparation time, a maximum power charging strategy is adopted for the super capacitor bank. If the designed maximum charging power is PmaxThen the isolated three-level DC/DC converter current can be given as shown in equation (15).
Figure BDA0002046688960000151
In the formula VSCIs the terminal voltage of the super capacitor bank.
It should be noted that in addition to the implementation circuits exemplified in the embodiments of the present invention, more complex soft switching isolated three-level DC/DC converters with wide load range may be used to accomplish some of the objects of the present invention. The soft switching auxiliary circuit adopted by the invention only adopts smaller inductor and capacitor to realize the soft switching in the full load range, is simpler than any other soft switching method, adopts the least devices and does not need additional control. And because no energy consumption device exists in the switching process, the soft switching auxiliary circuit consumes almost no energy.
It should be noted that, besides the implementation circuit exemplified in the embodiment of the present invention, other rectifier methods may be adopted to supply power to the isolated three-level DC/DC converter. But the use of a three-phase four-wire PWM rectifier is the simplest and most optimal power supply. The main body is as follows: 1. the three-phase four-wire PWM rectifier has the advantages that the structure is simple, two paths of equal voltages can be output by the three-phase four-wire PWM rectifier, and the two paths of equal voltages can be kept equal through control. 2. Unity power factor rectification can be achieved. 3. Can adapt to unbalanced electric wire netting.
In the charging device for the super-capacitor energy storage station, the voltage stress of the switching tube in the isolation three-level DC/DC converter is reduced by half, and the switching tube with a lower voltage grade can be selected, so that the switching frequency is improved, and the size of the converter is reduced.
The charging device of the super-capacitor energy storage station provided by the invention adopts the auxiliary converter circuit consisting of the inductor and the capacitor to realize the soft switching of the DC/DC converter, thereby widening the soft switching range. The converter can realize soft switching in a full load range or even under the no-load condition, and the efficiency of the converter is effectively improved.
The charging device of the super-capacitor energy storage station provided by the invention adopts the three-phase four-wire system PWM rectifying device to provide power for the isolation three-level DC/DC converter, can realize unit power rectification at an alternating current side, and reduces harmonic pollution. And the converter can still normally work under the unbalanced power grid through a positive-negative sequence separation decoupling control algorithm.
The charging device for the super-capacitor energy storage station provided by the embodiment of the invention is divided into two stages, wherein the front stage adopts a three-phase four-wire PWM rectifying device to convert alternating current into direct current, so that unit power factor rectification is realized, two-path series voltage is provided for the rear stage isolation three-level DC/DC converter, and the rear stage adopts the isolation three-level DC/DC converter to charge the super-capacitor bank, so that the isolation charging with small volume and high efficiency is realized.
The control method of the charging device of the super-capacitor energy storage station provided by the embodiment of the invention adopts a maximum power charging strategy, and reduces the charging time, thereby shortening the early-stage preparation time of equipment.
Those skilled in the art will appreciate that although some embodiments herein include some features included in other embodiments, not others, combinations of features of different embodiments are meant to be within the scope of the invention and form different embodiments. For example, in the following claims, any of the claimed embodiments may be used in any combination.
Finally, it should be noted that: the above examples are only intended to illustrate the technical solution of the present invention, but not to limit it; although the present invention has been described in detail with reference to the foregoing embodiments, it should be understood by those of ordinary skill in the art that: the technical solutions described in the foregoing embodiments may still be modified, or some technical features may be equivalently replaced; and such modifications or substitutions do not depart from the spirit and scope of the corresponding technical solutions of the embodiments of the present invention.

Claims (6)

1. A charging device for a super-capacitor energy storage station is characterized by comprising a three-phase four-wire PWM rectifier, an isolated three-level DC/DC converter, a first bus capacitor subunit and a second bus capacitor subunit;
an alternating current input port of the three-phase four-wire PWM rectifier is connected with a power grid system in parallel, a high-voltage input port of the isolation three-level DC/DC converter is connected with a direct current output port of the three-phase four-wire PWM rectifier, and a low-voltage output port of the isolation three-level DC/DC converter is connected with a super capacitor bank;
the first bus capacitor subunit and the second bus capacitor subunit are connected in series and then connected in parallel to a direct current output port of the three-phase four-wire PWM rectifier;
the isolation three-level DC/DC converter comprises an upper half-bridge submodule, a lower half-bridge submodule, a first capacitor unit and a first transformer unit; the direct current input end of the upper half-bridge submodule is connected to a first bus capacitor subunit in parallel, the direct current input end of the lower half-bridge submodule is connected to a second bus capacitor subunit in parallel, the upper half-bridge submodule and the lower half-bridge submodule respectively comprise a bridge arm midpoint, and the bridge arm midpoints of the upper half-bridge submodule and the lower half-bridge submodule are connected to a primary winding of a first transformer in series through the first capacitor unit;
the isolated three-level DC/DC converter further comprises a first commutation auxiliary circuit and a second commutation auxiliary circuit;
the first commutation auxiliary circuit comprises a first auxiliary inductor and a first auxiliary capacitor, one end of the first auxiliary inductor is connected with the middle point of a bridge arm of the upper half-bridge sub-module, the other end of the first auxiliary inductor is connected with the anode of the first auxiliary capacitor, and the cathode of the first auxiliary capacitor is connected with the cathode of the first bus capacitor sub-unit;
the second commutation auxiliary circuit comprises a second auxiliary inductor and a second auxiliary capacitor, one end of the second auxiliary inductor is connected with the middle point of a bridge arm of the lower half-bridge sub-module, the other end of the second auxiliary inductor is connected with the anode of the second auxiliary capacitor, and the cathode of the second auxiliary capacitor is connected with the cathode of the second bus capacitor sub-unit.
2. The supercapacitor energy storage station charging device according to claim 1, wherein the isolated three-level DC/DC converter further comprises an AC/DC conversion unit connected to the secondary winding of the first transformer, an AC port of the AC/DC conversion unit being connected to the secondary winding of the first transformer.
3. The supercapacitor energy storage station charging device according to claim 1, further comprising a control circuit;
and the control circuit is respectively connected with the three-phase four-wire PWM rectifier and the isolated three-level DC/DC converter and is used for controlling the working parameters of the three-phase four-wire PWM rectifier and the isolated three-level DC/DC converter.
4. A control method applied to the charging device of the super capacitor energy storage station as claimed in any one of claims 1 to 3, wherein the method comprises the following steps:
setting a signal according to a DC voltage
Figure FDA0003322392490000021
With the collected DC side voltage uDCCalculating positive and negative sequence dq axis voltage control signals;
converting the positive and negative sequence dq axis voltage control signals into positive and negative sequence alpha beta axis voltage control signals;
according to the voltage u of the first bus capacitor subunitDC1And the voltage u of the second bus capacitor subunitDC2Calculating a zero sequence voltage control signal;
generating three-phase PWM driving signals of the three-phase four-wire PWM rectifier according to the positive and negative sequence alpha beta shaft voltage control signals and the zero sequence voltage control signal;
and realizing output control of the isolated three-level DC/DC converter by adopting output current closed-loop control.
5. Method according to claim 4, characterized in that the signal is given as a function of a direct voltage
Figure FDA0003322392490000022
With the collected DC side voltage uDCCalculating positive and negative sequence dq axis voltage control signals, comprising:
giving a DC voltage to a signal
Figure FDA0003322392490000023
With the collected DC side voltage uDCComparing to obtain a direct voltage deviation signal;
inputting the direct voltage deviation signal into a first PI controller, and using the output signal of the first PI controller as a current setting signal of a current loop
Figure FDA0003322392490000024
Setting a signal according to the current
Figure FDA0003322392490000025
And a given signal of DC voltage
Figure FDA0003322392490000026
Calculating an active power given signal;
calculating a grid current positive and negative sequence dq axis component according to the grid voltage dq axis component signal and the active power given signal;
inputting the grid current positive sequence d-axis component into a second PI controller, and taking an output signal of the second PI controller as a positive sequence d-axis voltage control signal;
inputting the grid current positive sequence q-axis component into a third PI controller, and taking an output signal of the third PI controller as a positive sequence q-axis voltage control signal;
inputting the grid current negative sequence d-axis component into a fourth PI controller, and taking an output signal of the fourth PI controller as a negative sequence d-axis voltage control signal;
and inputting the grid current negative sequence q-axis component into a fifth PI controller, and taking an output signal of the fifth PI controller as a negative sequence q-axis voltage control signal.
6. Method according to claim 4, characterized in that the voltage u according to the first bus capacitor subunitDC1And the voltage u of the second bus capacitor subunitDC2Calculating zero sequence voltage control signals
Figure FDA0003322392490000031
The method comprises the following steps:
converting the voltage u of the first bus capacitor subunitDC1And the voltage u of the second bus capacitor subunitDC2Comparing to obtain an output capacitance voltage difference signal;
inputting the output capacitance voltage difference signal into a sixth PI controller, wherein the output signal of the sixth PI controller is used as a zero-sequence current given signal
Figure FDA0003322392490000032
Giving a zero sequence current to a signal
Figure FDA0003322392490000033
And the collected zero sequence current i0Comparing to obtain a zero sequence current difference signal;
inputting the zero sequence current difference signal into a seventh PI controller, and using the output signal of the seventh PI controller as a zero sequence voltage control signal
Figure FDA0003322392490000034
CN201910360424.1A 2019-04-30 2019-04-30 Charging device of super-capacitor energy storage station and control method Active CN111864776B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN201910360424.1A CN111864776B (en) 2019-04-30 2019-04-30 Charging device of super-capacitor energy storage station and control method

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN201910360424.1A CN111864776B (en) 2019-04-30 2019-04-30 Charging device of super-capacitor energy storage station and control method

Publications (2)

Publication Number Publication Date
CN111864776A CN111864776A (en) 2020-10-30
CN111864776B true CN111864776B (en) 2022-05-20

Family

ID=72965703

Family Applications (1)

Application Number Title Priority Date Filing Date
CN201910360424.1A Active CN111864776B (en) 2019-04-30 2019-04-30 Charging device of super-capacitor energy storage station and control method

Country Status (1)

Country Link
CN (1) CN111864776B (en)

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN116054361B (en) * 2023-03-30 2023-06-06 浙江大学杭州国际科创中心 Method for reducing bus capacitor volume and mobile power supply

Family Cites Families (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN100353652C (en) * 2004-10-13 2007-12-05 南京航空航天大学 Combined type full-bridge three-level DC converter and full-bridge three-level DC converter
US20110273909A1 (en) * 2010-05-04 2011-11-10 Chicony Power Technology Co., Ltd. Full-bridge phase-shift converter with auxiliary zero-voltage-switching circuit
CN105024582B (en) * 2015-07-27 2018-08-21 江苏大学 A kind of novel two-stage type bidirectional energy-storage converter control system and its control method
CN109391161A (en) * 2017-08-10 2019-02-26 台达电子企业管理（上海）有限公司 Technics of Power Electronic Conversion unit and system
CN109104108B (en) * 2018-09-19 2024-06-28 南京航空航天大学 Soft switch type single-stage high-frequency isolation rectifier with active clamp

Also Published As

Publication number Publication date
CN111864776A (en) 2020-10-30

Similar Documents

Publication Publication Date Title
CN111697837B (en) Direct-current transformer topology based on three-level CLLLC resonant converter and control method
US12095381B2 (en) Three phase bidirectional AC-DC converter with bipolar voltage fed resonant stages
CN111064359A (en) Wide-range bidirectional conversion circuit and control method
CN109104108B (en) Soft switch type single-stage high-frequency isolation rectifier with active clamp
CN112600454B (en) Current source input high-frequency isolation matrix converter and regulation and control method thereof
US11689115B2 (en) Bidirectional AC-DC converter with multilevel power factor correction
Zhao et al. AC–DC–DC isolated converter with bidirectional power flow capability
CN114448274A (en) Three-phase single-stage resonant type electric energy conversion device and control method
CN108736756B (en) Improved double-auxiliary resonant-pole three-phase soft switching inverter circuit
Yang et al. Single-phase high-gain bidirectional dc/ac converter based on high step-up/step-down dc/dc converter and dual-input dc/ac converter
CN113394996A (en) AC-DC resonant conversion circuit and control method thereof
Li et al. An interleaved three-phase PWM single-stage resonant rectifier with high-frequency isolation
Ohnuma et al. A control method for a single-to-three-phase power converter with an active buffer and a charge circuit
Dong et al. Zero input current ripple llc resonant converter with integrated interleaved boost converter
CN108448923B (en) Frequency conversion control method for realizing soft switch of three-phase inverter
Zhang et al. A single-stage three-phase isolated AC-DC converter for medium voltage solid state transformer applications
CN113965096A (en) Series 12-pulse rectifier with auxiliary power factor correction circuit
CN111864776B (en) Charging device of super-capacitor energy storage station and control method
Tseng et al. Interleaved coupled-inductor boost converter with boost type snubber for PV system
Takuma et al. Isolated DC to three-phase AC converter using indirect matrix converter with ZVS applied to all switches
Song et al. A novel three-phase single-stage isolated AC-DC converter with symmetrical structure for battery charger
Sha et al. Unequal PWM control for a current-fed dc-dc converter for battery application
Babaei et al. Basic and quasi structures of step-up switched based dc/dc converter: Steady-state analysis and design in different operating modes
CN114759781A (en) Input interleaved parallel soft-switching high-voltage gain DC-DC converter based on switched capacitor
Han et al. Circulating current-less phase-shifted full-bridge converter with new rectifier structure

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant