CN113364326A - Overmodulation method and system for 3D-SVPWM modulation strategy with minimum instantaneous error - Google Patents

Overmodulation method and system for 3D-SVPWM modulation strategy with minimum instantaneous error Download PDF

Info

Publication number
CN113364326A
CN113364326A CN202110746997.5A CN202110746997A CN113364326A CN 113364326 A CN113364326 A CN 113364326A CN 202110746997 A CN202110746997 A CN 202110746997A CN 113364326 A CN113364326 A CN 113364326A
Authority
CN
China
Prior art keywords
modulation
phase
voltage vector
reference voltage
svpwm
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
CN202110746997.5A
Other languages
Chinese (zh)
Other versions
CN113364326B (en
Inventor
杨淑英
王顺
谢震
张兴
刘芳
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Hefei University of Technology
Original Assignee
Hefei University of Technology
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Hefei University of Technology filed Critical Hefei University of Technology
Priority to CN202110746997.5A priority Critical patent/CN113364326B/en
Publication of CN113364326A publication Critical patent/CN113364326A/en
Application granted granted Critical
Publication of CN113364326B publication Critical patent/CN113364326B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H02M7/5395—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from AC input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/42—Conversion of DC power input into AC power output without possibility of reversal
    • H02M7/44—Conversion of DC power input into AC power output without possibility of reversal by static converters
    • H02M7/48—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • H02M7/53875—Conversion of DC power input into AC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current with analogue control of three-phase output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/0003—Control strategies in general, e.g. linear type, e.g. P, PI, PID, using robust control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/0085—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation specially adapted for high speeds, e.g. above nominal speed
    • H02P21/0089—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation specially adapted for high speeds, e.g. above nominal speed using field weakening
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/14—Estimation or adaptation of machine parameters, e.g. flux, current or voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
    • H02P21/24—Vector control not involving the use of rotor position or rotor speed sensors
    • H02P21/28—Stator flux based control
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/022—Synchronous motors
    • H02P25/024—Synchronous motors controlled by supply frequency
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/02—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using supply voltage with constant frequency and variable amplitude
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using DC to AC converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using DC to AC converters or inverters with pulse width modulation
    • H02P27/12—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using DC to AC converters or inverters with pulse width modulation pulsing by guiding the flux vector, current vector or voltage vector on a circle or a closed curve, e.g. for direct torque control

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)

Abstract

一种输出谐波最小化3D‑SVPWM调制策略过调制方法及系统，属于逆变器调制技术领域，解决如何计算出3D‑SVPWM调制策略最大线性调制度，在不改变3D‑SVPWM调制策略同时调制差模分量和共模分量的特性的同时，通过过调制技术提升3D‑SVPWM调制策略的调制范围的问题，通过计算得出3D‑SVPWM调制策略最大线性调制度，给出一种空间调制参考矢量所在的空间调制体判断，过调制时联立相应的压缩平面约束方程和瞬时误差最小压缩方案约束方程，在不改变3D‑SVPWM调制策略同时调制差模分量和共模分量的特性的前提下，通过过调制技术，保持过调制时输出电压矢量瞬时误差最小，提升3D‑SVPWM调制策略的调制范围。

Figure 202110746997

A 3D-SVPWM modulation strategy overmodulation method and system for minimizing output harmonics belong to the technical field of inverter modulation, and solve how to calculate the maximum linear modulation degree of a 3D-SVPWM modulation strategy, and simultaneously modulate the 3D-SVPWM modulation strategy without changing the 3D-SVPWM modulation strategy. At the same time of the characteristics of the differential mode component and the common mode component, the modulation range of the 3D-SVPWM modulation strategy is improved by the overmodulation technology. The maximum linear modulation degree of the 3D-SVPWM modulation strategy is obtained by calculation, and a spatial modulation reference vector is given. Judging from the spatial modulation body where it is located, the corresponding compression plane constraint equation and the instantaneous error minimum compression scheme constraint equation are simultaneously established during overmodulation, and on the premise of not changing the characteristics of the 3D‑SVPWM modulation strategy to modulate the differential mode component and the common mode component at the same time, Through the over-modulation technique, the instantaneous error of the output voltage vector during over-modulation is kept to a minimum, and the modulation range of the 3D‑SVPWM modulation strategy is improved.

Figure 202110746997

Description

一种瞬时误差最小的3D-SVPWM调制策略过调制方法及系统A 3D-SVPWM modulation strategy overmodulation method and system with minimum instantaneous error

技术领域technical field

本发明属于逆变器调制技术领域，涉及一种瞬时误差最小的3D-SVPWM调制策略过调制方法及系统。The invention belongs to the technical field of inverter modulation, and relates to a 3D-SVPWM modulation strategy overmodulation method and system with minimum instantaneous error.

背景技术Background technique

3D-SVPWM调制(三维空间矢量脉宽调制)策略能够同时对参考电压矢量的差模分量和共模分量进行调制，因此被广泛应用于需要调制共模电压的零序环流控制中，如共直流母线及共中线双逆变器开绕组拓扑结构、三相四桥臂逆变器等。相比传统的仅关注差模分量调制的SVPWM调制策略，3D-SVPWM调制策略因同时调制共模分量而导致其差模分量调制输出范围受限，因此亟需相关的线性调制范围计算及相应的过调制方案来拓展其调制范围，提升3D-SVPWM调制策略的适用性。The 3D-SVPWM modulation (three-dimensional space vector pulse width modulation) strategy can modulate the differential mode component and common mode component of the reference voltage vector at the same time, so it is widely used in zero-sequence circulating current control that needs to modulate the common mode voltage, such as common DC Busbar and common neutral dual inverter open-winding topology, three-phase four-arm inverter, etc. Compared with the traditional SVPWM modulation strategy that only focuses on the modulation of the differential mode component, the 3D-SVPWM modulation strategy limits the output range of the differential mode component modulation due to the simultaneous modulation of the common mode component. Therefore, it is urgent to calculate the relevant linear modulation range and the corresponding The over-modulation scheme is used to expand its modulation range and improve the applicability of the 3D-SVPWM modulation strategy.

现有技术中，公开日期为2019年10月的文献《四桥臂三电平逆变器3D-SVPWM调制策略》(任思远等，电力系统及其自动化学报，2019年第31卷第10期125-132页)，公开了使用3D-SVPWM调制策略应用于四桥臂三电平逆变器，但该文献并没有具体给出3D-SVPWM调制策略最大线性调制度及相关的过调制策略。公开日期为2018年11月5日的文献《共直流母线开绕组永磁同步电机的弱磁控制策略》(年珩等，中国电机工程学报，2018年第38卷第21期6461-6469页)公开了使用3D-SVPWM调制策略实现共直流母线双逆变器开绕组系统零序环流闭环控制，但其没有给出3D-SVPWM调制策略线性调制度范围及相关的过调制策略。In the prior art, the document "3D-SVPWM modulation strategy of four-arm three-level inverter" (Ren Siyuan et al., Journal of Electric Power Systems and Automation, Vol. 31, Issue 10, 2019) was published in October 2019. 125 -132 pages), discloses the use of 3D-SVPWM modulation strategy applied to the four-arm three-level inverter, but the document does not specifically give the 3D-SVPWM modulation strategy maximum linear modulation degree and related overmodulation strategy. The publication dated November 5, 2018, "Field Weakening Control Strategy for Open-winding Permanent Magnet Synchronous Motors with Common DC Bus" (Nian Heng et al., Chinese Journal of Electrical Engineering, Vol. 38, No. 21, 2018, pp. 6461-6469) The use of the 3D-SVPWM modulation strategy to realize the zero-sequence loop closed-loop control of the open-winding system of the common DC bus and dual inverters is disclosed, but it does not give the linear modulation range of the 3D-SVPWM modulation strategy and the related overmodulation strategy.

综上所述，现有技术存在以下问题：1)对于3D-SVPWM调制策略，现有技术仅给出了基础合成原理及实现过程，没有给出3D-SVPWM调制策略的线性调制范围，即最大线性调制度；2)没有给出3D-SVPWM调制策略过调制时的约束方案，因而无法采用过调制约束方案有效拓展3D-SVPWM调制策略的适用范围。To sum up, the prior art has the following problems: 1) For the 3D-SVPWM modulation strategy, the prior art only provides the basic synthesis principle and implementation process, but does not provide the linear modulation range of the 3D-SVPWM modulation strategy, that is, the maximum Linear modulation degree; 2) The constraint scheme of the 3D-SVPWM modulation strategy when overmodulation is not given, so the overmodulation constraint scheme cannot be used to effectively expand the scope of application of the 3D-SVPWM modulation strategy.

发明内容SUMMARY OF THE INVENTION

本发明的目的在于如何计算出3D-SVPWM调制策略最大线性调制度，在不改变3D-SVPWM调制策略同时调制差模分量和共模分量的特性的前提下，通过过调制技术，保持过调制时输出电压矢量瞬时误差最小，提升3D-SVPWM调制策略的调制范围。The purpose of the invention is how to calculate the maximum linear modulation degree of the 3D-SVPWM modulation strategy, without changing the characteristics of the 3D-SVPWM modulation strategy to modulate the differential mode component and the common mode component at the same time, through the overmodulation technology, keep the overmodulation time The instantaneous error of the output voltage vector is the smallest, which improves the modulation range of the 3D-SVPWM modulation strategy.

本发明是通过以下技术方案解决上述技术问题的：The present invention solves the above-mentioned technical problems through the following technical solutions:

一种瞬时误差最小的3D-SVPWM调制策略过调制方法，包括以下步骤：A 3D-SVPWM modulation strategy overmodulation method with minimum instantaneous error, comprising the following steps:

步骤S1，计算参考电压矢量Vref的α-β平面分量的幅值m1、相位

Figure BDA0003143310430000021
和调制度M1，计算参考电压矢量Vref的γ轴分量Vγ的幅值m3及相位
Figure BDA0003143310430000022
计算参考电压矢量Vref的特征相位差
Figure BDA0003143310430000023
Step S1, calculate the amplitude m 1 and phase of the α-β plane component of the reference voltage vector V ref
Figure BDA0003143310430000021
and the modulation degree M 1 , calculate the amplitude m 3 and phase of the γ-axis component V γ of the reference voltage vector V ref
Figure BDA0003143310430000022
Calculate the characteristic phase difference of the reference voltage vector Vref
Figure BDA0003143310430000023

步骤S2，根据步骤S1中的幅值m3及特征相位差

Figure BDA0003143310430000024
计算3D-SVPWM调制策略最大线性调制度Mmax1及最大压缩调制度Mmax2；Step S2, according to the amplitude m 3 and the characteristic phase difference in step S1
Figure BDA0003143310430000024
Calculate the maximum linear modulation degree M max1 and the maximum compression modulation degree M max2 of the 3D-SVPWM modulation strategy;

步骤S3，根据调制度M1、最大线性调制度Mmax1及最大压缩调制度Mmax2，进行过调制判断：Step S3, according to the modulation degree M 1 , the maximum linear modulation degree M max1 and the maximum compression modulation degree M max2 , perform overmodulation judgment:

当计算M1<Mmax1时，为线性调制区域，采用线性调制区域发波控制，方法为：根据Vα、Vβ和Vγ，使用3D-SVPWM调制策略计算基础电压矢量作用时间t0、t1、t2和t7进行发波控制；When M 1 < M max1 is calculated , it is a linear modulation region, and the linear modulation region is used for wave control. t 1 , t 2 and t 7 perform wave emission control;

当计算Mmax1≤M1≤Mmax2时，为过调制区域，采用过调制区域发波控制，方法为：When M max1 ≤M 1 ≤M max2 is calculated, it is the over-modulation region, and the over-modulation region is used for wave control. The method is as follows:

当t0≥0且t7≥0时，为过调制区域的圆弧区，根据Vα、Vβ和Vγ，使用3D-SVPWM调制策略计算基础电压矢量作用时间t0、t1、t2和t7进行发波控制；When t 0 ≥ 0 and t 7 ≥ 0, it is the arc area of the overmodulation area. According to V α , V β and V γ , the 3D-SVPWM modulation strategy is used to calculate the basic voltage vector action time t 0 , t 1 , t 2 and t 7 for wave control;

当t0<0或t7<0时，为过调制区域的边界区，对参考电压矢量Vref的α-β平面分量进行修改：When t 0 <0 or t 7 <0, it is the boundary region of the overmodulation region, and the α-β plane component of the reference voltage vector Vref is modified:

首先根据Vα、Vβ和Vγ对参考电压矢量Vref所在的调制体进行调制体序号判断，由判断的调制体序号选择对应的压缩平面约束方程；Firstly, according to V α , V β and V γ , the modulation body serial number is judged for the modulation body where the reference voltage vector V ref is located, and the corresponding compression plane constraint equation is selected according to the judged modulation body serial number;

然后与瞬时误差最小压缩方案约束方程联立计算得出修改后参考电压矢量α轴分量

Figure BDA0003143310430000025
参考电压矢量β轴分量
Figure BDA0003143310430000026
所述的瞬时误差最小压缩方案约束方程如下：Then, the α-axis component of the modified reference voltage vector is calculated simultaneously with the constraint equation of the minimum compression scheme of the instantaneous error.
Figure BDA0003143310430000025
Reference voltage vector β-axis component
Figure BDA0003143310430000026
The constraint equation of the minimum instantaneous error compression scheme described is as follows:

Figure BDA0003143310430000027
Figure BDA0003143310430000027

其中，P1、P2、P3分别为所选择的压缩平面约束方程中

Figure BDA0003143310430000031
前的系数及常数项；Among them, P 1 , P 2 , and P 3 are respectively in the selected compression plane constraint equation
Figure BDA0003143310430000031
The previous coefficients and constant terms;

最后根据修改后参考电压矢量α轴分量

Figure BDA0003143310430000032
修改后参考电压矢量β轴分量
Figure BDA0003143310430000033
和Vγ，使用3D-SVPWM调制策略计算修改后基础电压矢量作用时间
Figure BDA0003143310430000034
和
Figure BDA0003143310430000035
进行发波控制。Finally, according to the α-axis component of the modified reference voltage vector
Figure BDA0003143310430000032
Modified reference voltage vector β-axis component
Figure BDA0003143310430000033
and V γ , use the 3D-SVPWM modulation strategy to calculate the modified base voltage vector action time
Figure BDA0003143310430000034
and
Figure BDA0003143310430000035
Perform wave control.

本发明的技术方案通过计算得出3D-SVPWM调制策略最大线性调制度，给出一种空间调制参考矢量所在的空间调制体判断，过调制时联立相应的压缩平面约束方程和瞬时误差最小压缩方案约束方程，在不改变3D-SVPWM调制策略同时调制差模分量和共模分量的特性的前提下，通过过调制技术，保持过调制时输出电压矢量瞬时误差最小，提升3D-SVPWM调制策略的调制范围。The technical scheme of the present invention obtains the maximum linear modulation degree of the 3D-SVPWM modulation strategy through calculation, provides a spatial modulation volume judgment where the spatial modulation reference vector is located, and simultaneously combines the corresponding compression plane constraint equation and the minimum instantaneous error compression during overmodulation The scheme constraint equation, on the premise of not changing the characteristics of the 3D-SVPWM modulation strategy to modulate the differential mode component and the common mode component at the same time, through the overmodulation technology, the instantaneous error of the output voltage vector during overmodulation is kept to a minimum, and the performance of the 3D-SVPWM modulation strategy is improved. modulation range.

作为本发明技术方案的进一步改进，步骤S1中计算参考电压矢量Vref的α-β平面分量的幅值m1、相位

Figure BDA0003143310430000036
和调制度M1的公式为：As a further improvement of the technical solution of the present invention, in step S1, the amplitude m 1 and phase of the α-β plane component of the reference voltage vector V ref are calculated.
Figure BDA0003143310430000036
The formula for the sum modulation degree M 1 is:

Figure BDA0003143310430000037
Figure BDA0003143310430000037

其中，Vα、Vβ分别为参考电压矢量Vref对三维空间坐标系中坐标轴α、β轴的投影分量以直流电压Udc进行标幺化后的值。Among them, V α and V β are respectively the values of the reference voltage vector V ref after the projection components of the coordinate axes α and β in the three-dimensional space coordinate system are per unitized by the DC voltage U dc .

作为本发明技术方案的进一步改进，步骤S1中计算参考电压矢量Vref的γ轴分量Vγ的幅值m3及相位

Figure BDA0003143310430000038
的公式为：As a further improvement of the technical solution of the present invention, in step S1, the amplitude m 3 and the phase of the γ-axis component V γ of the reference voltage vector V ref are calculated
Figure BDA0003143310430000038
The formula is:

Figure BDA0003143310430000039
Figure BDA0003143310430000039

其中，Vγ，1为第一正交分量、Vγ，2为第二正交分量；第一正交分量、第二正交分量是对Vγ进行正交分解，得出两个相差90度的分量。Among them, V γ,1 is the first quadrature component, V γ, 2 is the second quadrature component; the first quadrature component and the second quadrature component are the orthogonal decomposition of V γ , and the difference between the two is obtained by 90 degree component.

作为本发明技术方案的进一步改进，步骤S1中计算参考电压矢量Vref的特征相位差

Figure BDA0003143310430000041
计算式如下：As a further improvement of the technical solution of the present invention, the characteristic phase difference of the reference voltage vector Vref is calculated in step S1
Figure BDA0003143310430000041
The calculation formula is as follows:

Figure BDA0003143310430000042
Figure BDA0003143310430000042

其中，

Figure BDA0003143310430000043
为参考电压矢量Vref的γ轴分量Vγ的相位，
Figure BDA0003143310430000044
为参考电压矢量Vref的α-β平面分量的相位。in,
Figure BDA0003143310430000043
is the phase of the γ-axis component V γ of the reference voltage vector V ref ,
Figure BDA0003143310430000044
is the phase of the α-β plane component of the reference voltage vector Vref .

作为本发明技术方案的进一步改进，步骤S2中计算3D-SVPWM调制策略最大线性调制度Mmax1及最大压缩调制度Mmax2具体为：As a further improvement of the technical solution of the present invention, the calculation of the maximum linear modulation degree M max1 and the maximum compression modulation degree M max2 of the 3D-SVPWM modulation strategy in step S2 is specifically:

定义函数式W1，Define the functional formula W 1 ,

Figure BDA0003143310430000045
Figure BDA0003143310430000045

定义函数式W2，Define the functional formula W 2 ,

Figure BDA0003143310430000046
Figure BDA0003143310430000046

其中，θ1的取值范围为

Figure BDA0003143310430000047
在θ1的取值范围内计算函数式W1最小值为W1min，计算函数式W2最小值为W2min，当W1min≤W2min时，Mmax1＝W1min，当W1min>W2min时，Mmax1＝W2min，计算函数式曲线W1和函数式W2曲线交点的函数值即为Mmax2。Among them, the value range of θ1 is
Figure BDA0003143310430000047
Within the value range of θ 1 , the minimum value of the calculation function formula W 1 is W 1min , and the minimum value of the calculation function formula W 2 is W 2min . When W 1min ≤W 2min , M max1 =W 1min , and when W 1min >W 2min When M max1 =W 2min , the function value of the intersection of the curve W 1 of the functional formula and the curve of the functional formula W 2 is calculated as M max2 .

作为本发明技术方案的进一步改进，所述的调制体序号判断的具体方式为：As a further improvement of the technical solution of the present invention, the specific method for determining the serial number of the modulation body is:

定义调制体序号判断的中间变量为第一变量A、第二变量B、第三变量C、第四变量N、第五变量A1、第六变量B1、第七变量C1、第八变量N1，定义函数式F1，

Figure BDA0003143310430000048
定义函数式F2，F2＝2Vγ-Vα，定义函数式F3，
Figure BDA0003143310430000049
定义函数式F4，F4＝Vβ，定义函数式F5，
Figure BDA00031433104300000410
定义函数式F6，
Figure BDA00031433104300000411
则：The intermediate variables that define the modulation body serial number judgment are the first variable A, the second variable B, the third variable C, the fourth variable N, the fifth variable A 1 , the sixth variable B 1 , the seventh variable C 1 , and the eighth variable N 1 , define the functional formula F 1 ,
Figure BDA0003143310430000048
Define the functional formula F 2 , F 2 =2V γ -V α , define the functional formula F 3 ,
Figure BDA0003143310430000049
Define functional formula F 4 , F 4 =V β , define functional formula F 5 ,
Figure BDA00031433104300000410
Define the functional formula F 6 ,
Figure BDA00031433104300000411
but:

当F1≥0时，A＝1；当F1<0时，A＝0；当F2≥0时，B＝1；当F2<0时，B＝0；当F3≥0时，C＝1；当F3<0时，C＝0；N＝A+2B+4C；When F 1 ≥ 0, A=1; when F 1 <0, A=0; when F 2 ≥ 0, B=1; when F 2 <0, B=0; when F 3 ≥ 0 , C=1; when F 3 <0, C=0; N=A+2B+4C;

当F4≥0时，A1＝1；当F4<0时，A1＝0；当F5≥0时，B1＝1；当F5<0时，B1＝0；当F6≥0时，C1＝1；当F6<0时，C1＝0；N1＝A1+2B1+4C1；When F 4 ≥ 0, A 1 =1; when F 4 <0, A 1 =0; when F 5 ≥ 0, B 1 =1; when F 5 <0, B 1 =0; When 6 ≥ 0, C 1 =1; when F 6 <0, C 1 =0; N 1 =A 1 +2B 1 +4C 1 ;

第四变量N的每一个值对应一个调制体序号，具体如下：N＝5对应调制体1；N＝1对应调制体2；N＝3对应调制体3；N＝2对应调制体4；N＝6对应调制体5；N＝4对应调制体6；N＝0时需要结合第八变量N1值做进一步判断，其中当N1＝1或N1＝3时对应调制体2，当N1＝4或N1＝5时对应调制体4，当N1＝2或N1＝6时对应调制体6；N＝7时需要结合第八变量N1值做进一步判断，其中当N1＝2或N1＝3时对应调制体1，当N1＝1或N1＝5时对应调制体3，当N1＝4或N1＝6时对应调制体5。Each value of the fourth variable N corresponds to a modulation body serial number, as follows: N=5 corresponds to modulation body 1; N=1 corresponds to modulation body 2; N=3 corresponds to modulation body 3; N=2 corresponds to modulation body 4; N =6 corresponds to modulating body 5; N=4 corresponds to modulating body 6; when N=0, further judgment needs to be made in conjunction with the value of the eighth variable N 1 , wherein when N 1 =1 or N 1 =3, it corresponds to modulating body 2, and when N When 1 = 4 or N 1 =5, it corresponds to modulator 4; when N 1 =2 or N 1 =6, it corresponds to modulator 6; when N = 7, it is necessary to make further judgments based on the value of the eighth variable N 1 , where when N 1 = 2 or N 1 =3, it corresponds to modulator 1, when N 1 =1 or N 1 =5, corresponds to modulator 3, and when N 1 =4 or N 1 =6, corresponds to modulator 5.

作为本发明技术方案的进一步改进，所述的由判断的调制体序号选择对应的压缩平面约束方程的具体方式为：As a further improvement of the technical solution of the present invention, the specific method for selecting the corresponding compression plane constraint equation according to the determined modulation volume serial number is:

调制体1的压缩平面约束方程为：

Figure BDA0003143310430000051
The compression plane constraint equation of modulating body 1 is:
Figure BDA0003143310430000051

调制体2的压缩平面约束方程为：

Figure BDA0003143310430000052
The compression plane constraint equation of modulation volume 2 is:
Figure BDA0003143310430000052

调制体3的压缩平面约束方程为：

Figure BDA0003143310430000053
The compression plane constraint equation of modulation volume 3 is:
Figure BDA0003143310430000053

调制体4的压缩平面约束方程为：

Figure BDA0003143310430000054
The compression plane constraint equation of modulation volume 4 is:
Figure BDA0003143310430000054

调制体5的压缩平面约束方程为：

Figure BDA0003143310430000055
The compression plane constraint equation of the modulation body 5 is:
Figure BDA0003143310430000055

调制体6的压缩平面约束方程为：

Figure BDA0003143310430000056
The compression plane constraint equation of modulating body 6 is:
Figure BDA0003143310430000056

一种应用于所述的输出谐波最小化3D-SVPWM调制策略过调制方法的系统，包括：第一直流源Udc1、第二直流源Udc2、第一三相两电平逆变器VSI1、第二三相两电平逆变器VSI2、三相定子绕组OEWIM、中线I、电容C1、电容C2、电容C3和电容C4；A system applied to the 3D-SVPWM modulation strategy overmodulation method for minimizing output harmonics, comprising: a first DC source U dc1 , a second DC source U dc2 , and a first three-phase two-level inverter VSI1, the second three-phase two-level inverter VSI2, the three-phase stator winding OEWIM, the neutral line I, the capacitor C1, the capacitor C2, the capacitor C3 and the capacitor C4;

所述电容C1和电容C2串联后连接在第一直流源Udc1的直流正母线P与直流负母线N之间，电容C1、电容C2的公共节点记为点O；所述电容C3和电容C4串联后连接在第二直流源Udc2的直流正母线P'与直流负母线N'之间，电容C3、电容C4的公共节点记为点O'，所述中线I连接点O与点O'，第一直流源Udc1和第二直流源Udc2直流电压均为Udc；The capacitor C1 and the capacitor C2 are connected in series between the DC positive bus P and the DC negative bus N of the first DC source U dc1 , and the common node of the capacitor C1 and the capacitor C2 is marked as point O; the capacitor C3 and the capacitor C4 is connected in series between the DC positive busbar P' and the DC negative busbar N' of the second DC source U dc2 , the common node of the capacitors C3 and C4 is marked as point O', and the neutral line I connects point O and point O ', the direct current voltages of the first direct current source U dc1 and the second direct current source U dc2 are both U dc ;

所述第一三相两电平逆变器VSI1的三相桥臂中，每相桥臂包括2个带反并联二极管的开关管，即第一三相两电平逆变器VSI1共包括6个带反并联二极管的开关管，6个开关管分别记为Sn1j，其中n表示相序，n＝a,b,c，j表示开关管的序号，j＝1,2；第一三相两电平逆变器VSI1的三相桥臂相互并联在直流正母线P与直流负母线N之间，即开关管Sa11、Sb11、Sc11的集电极并联后连接直流正母线P，开关管Sa12、Sb12、Sc12的发射极并联后连接直流负母线N；在第一三相两电平逆变器VSI1的三相桥臂中，开关管Sa11和开关管Sa12串联，开关管Sb11和开关管Sb12串联，开关管Sc11和开关管Sc12串联，其连接点分别记为第一三相两电平逆变器VSI1的三相桥臂中点a1、b1、c1；In the three-phase bridge arms of the first three-phase two-level inverter VSI1, each phase bridge arm includes two switch tubes with anti-parallel diodes, that is, the first three-phase two-level inverter VSI1 includes a total of six 6 switches with anti-parallel diodes, 6 switches are respectively denoted as S n1j , where n represents the phase sequence, n=a, b, c, j represents the serial number of the switches, j=1, 2; the first three-phase The three-phase bridge arms of the two-level inverter VSI1 are connected in parallel between the DC positive busbar P and the DC negative busbar N, that is, the collectors of the switch tubes S a11 , S b11 , and S c11 are connected in parallel and then connected to the DC positive bus bar P, the switch The emitters of the tubes S a12 , S b12 , and S c12 are connected in parallel and then connected to the DC negative busbar N; in the three-phase bridge arm of the first three-phase two-level inverter VSI1, the switch tube S a11 and the switch tube S a12 are connected in series, The switch tube S b11 and the switch tube S b12 are connected in series, and the switch tube S c11 and the switch tube S c12 are connected in series. 1 , c1 ;

所述第二三相两电平逆变器VSI2的三相桥臂中，每相桥臂包括2个带反并联二极管的开关管，即第二三相两电平逆变器VSI2共包括6个带反并联二极管的开关管，6个开关管分别记为Sn2j；第二三相两电平逆变器VSI2的三相桥臂相互并联在直流正母线P'与直流负母线N'之间，即开关管Sa21、Sb21、Sc21的集电极并联后连接直流正母线P'，开关管Sa22、Sb22、Sc22的发射极并联后连接直流负母线N'；在第二三相两电平逆变器VSI2的三相桥臂中，开关管Sa21和开关管Sa22串联，开关管Sb21和开关管Sb22串联，开关管Sc21和开关管Sc22串联，其连接点分别记为第二三相两电平逆变器VSI2的三相桥臂中点a2、b2、c2；In the three-phase bridge arms of the second three-phase two-level inverter VSI2, each phase bridge arm includes two switch tubes with anti-parallel diodes, that is, the second three-phase two-level inverter VSI2 includes a total of six 1 switch tubes with anti-parallel diodes, 6 switch tubes are respectively denoted as Sn2j ; the three-phase bridge arms of the second three-phase two-level inverter VSI2 are connected in parallel between the DC positive busbar P' and the DC negative busbar N'. between the collectors of the switches S a21 , S b21 , and S c21 are connected in parallel to the DC positive bus P', and the emitters of the switches S a22 , S b22 , and S c22 are connected in parallel and then connected to the DC negative bus N'; in the second In the three-phase bridge arm of the three-phase two-level inverter VSI2, the switch tube S a21 and the switch tube S a22 are connected in series, the switch tube S b21 and the switch tube S b22 are connected in series, and the switch tube S c21 and the switch tube S c22 are connected in series. The connection points are respectively recorded as midpoints a 2 , b 2 , and c 2 of the three-phase bridge arms of the second three-phase two-level inverter VSI2;

所述三相定子绕组OEWIM中包括三相绕组，A相绕组、B相绕组和C相绕组的左端口分别接第一三相两电平逆变器VSI1的三相桥臂中点a1、b1、c1，A相绕组、B相绕组和C相绕组的右端口分别接第二三相两电平逆变器VSI2的三相桥臂中点a2、b2、c2。The three-phase stator winding OEWIM includes three-phase windings, and the left ports of the A-phase winding, the B-phase winding and the C-phase winding are respectively connected to the midpoints a 1 of the three-phase bridge arms of the first three-phase two-level inverter VSI1, b 1 , c 1 , the right ports of the A-phase winding, the B-phase winding and the C-phase winding are respectively connected to the midpoints a 2 , b 2 and c 2 of the three-phase bridge arms of the second three-phase two-level inverter VSI2.

本发明的优点在于：The advantages of the present invention are:

本发明的技术方案通过计算得出3D-SVPWM调制策略最大线性调制度，给出一种空间调制参考矢量所在的空间调制体判断，过调制时联立相应的压缩平面约束方程和瞬时误差最小压缩方案约束方程，在不改变3D-SVPWM调制策略同时调制差模分量和共模分量的特性的同时，通过过调制技术，保持过调制时输出电压矢量瞬时误差最小，提升3D-SVPWM调制策略的调制范围。The technical scheme of the present invention obtains the maximum linear modulation degree of the 3D-SVPWM modulation strategy through calculation, provides a spatial modulation volume judgment where the spatial modulation reference vector is located, and simultaneously combines the corresponding compression plane constraint equation and the minimum instantaneous error compression during overmodulation The scheme constraint equation does not change the characteristics of the 3D-SVPWM modulation strategy to modulate the differential mode component and the common mode component at the same time, and through the overmodulation technology, the instantaneous error of the output voltage vector during overmodulation is kept to a minimum, and the modulation of the 3D-SVPWM modulation strategy is improved. scope.

附图说明Description of drawings

图1为本发明中涉及的共中线开绕组拓扑结构；Fig. 1 is the common neutral open winding topology structure involved in the present invention;

图2为本发明实施例中任意一个调制体内的过调制运行流程图；FIG. 2 is a flow chart of the overmodulation operation in any one of the modulation bodies in the embodiment of the present invention;

图3为本发明实施例中3D-SVPWM调制策略总调制体说明图；3 is an explanatory diagram of the overall modulation volume of the 3D-SVPWM modulation strategy in the embodiment of the present invention;

图4为本发明实施例中3D-SVPWM调制策略调制体分开说明图；FIG. 4 is a separate explanatory diagram of a 3D-SVPWM modulation strategy modulation body in an embodiment of the present invention;

图5为实验中各参数准确情况下，通过步骤S1计算得出的参考电压矢量γ轴分量Vγ的幅值m3的变化情况示意图；5 is a schematic diagram of the variation of the amplitude m 3 of the reference voltage vector γ-axis component V γ calculated through step S1 when the parameters in the experiment are accurate;

图6为实验中各参数准确情况下，通过步骤S1计算得出的参考电压矢量Vref的特征相位差

Figure BDA0003143310430000071
的变化情况示意图；Figure 6 shows the characteristic phase difference of the reference voltage vector V ref calculated in step S1 under the condition that each parameter is accurate in the experiment
Figure BDA0003143310430000071
Schematic diagram of the changes;

图7为实验中各参数准确情况下，通过步骤S2绘制的函数式曲线W1和函数式W2曲线，并计算得出的3D-SVPWM调制策略最大线性调制度Mmax1及最大压缩调制度Mmax2示意图；Fig. 7 is the functional curve W 1 and the functional formula W 2 curve drawn by step S2 under the condition that each parameter is accurate in the experiment, and the maximum linear modulation degree M max1 and the maximum compression modulation degree M of the 3D-SVPWM modulation strategy are calculated. max2 schematic diagram;

图8为实验中各参数准确情况下，从调制度M＝0.6到调制度M＝0.8时使用3D-SVPWM策略调制时共中线开绕组电驱动系统总输出的基波电压幅值变化情况示意图；Figure 8 is a schematic diagram of the change of the fundamental voltage amplitude of the total output of the common neutral open-winding electric drive system when the modulation degree M=0.6 to the modulation degree M=0.8 when the parameters are accurate in the experiment when the 3D-SVPWM strategy is used for modulation;

图9为本发明的技术方案的原理和特点描述图；Fig. 9 is the principle and characteristic description diagram of the technical solution of the present invention;

图10为实验中测得调制体判断中第四变量N的值变化趋势图。FIG. 10 is a graph showing the change trend of the value of the fourth variable N in the modulation body judgment measured in the experiment.

具体实施方式Detailed ways

为使本发明实施例的目的、技术方案和优点更加清楚，下面将结合本发明实施例，对本发明实施例中的技术方案进行清楚、完整地描述，显然，所描述的实施例是本发明一部分实施例，而不是全部的实施例。基于本发明中的实施例，本领域普通技术人员在没有作出创造性劳动前提下所获得的所有其他实施例，都属于本发明保护的范围。In order to make the purposes, technical solutions and advantages of the embodiments of the present invention clearer, the technical solutions in the embodiments of the present invention will be clearly and completely described below in conjunction with the embodiments of the present invention. Obviously, the described embodiments are part of the present invention. examples, but not all examples. Based on the embodiments of the present invention, all other embodiments obtained by those of ordinary skill in the art without creative efforts shall fall within the protection scope of the present invention.

下面结合说明书附图以及具体的实施例对本发明的技术方案作进一步描述：The technical solutions of the present invention are further described below in conjunction with the accompanying drawings and specific embodiments:

实施例一Example 1

图1为本发明中涉及的三相两电平电压型逆变器拓扑结构，由该图可见，本策略涉及的共中线开绕组电驱动系统拓扑结构包括第一直流源Udc1、第二直流源Udc2、第一三相两电平逆变器VSI1、第二三相两电平逆变器VSI2、三相定子绕组OEWIM、中线I、电容C1、电容C2、电容C3和电容C4；FIG. 1 is a topology structure of a three-phase two-level voltage inverter involved in the present invention. It can be seen from the figure that the topology structure of a common-neutral open-winding electric drive system involved in this strategy includes a first DC source U dc1 , a second DC source U dc1 , a second DC source U dc2 , first three-phase two-level inverter VSI1, second three-phase two-level inverter VSI2, three-phase stator winding OEWIM, neutral line I, capacitor C1, capacitor C2, capacitor C3 and capacitor C4;

所述电容C1和电容C2串联后连接在第一直流源Udc1的直流正母线P与直流负母线N之间，电容C1、电容C2的公共节点记为点O；所述电容C3和电容C4串联后连接在第二直流源Udc2的直流正母线P'与直流负母线N'之间，电容C3、电容C4的公共节点记为点O'，所述中线I连接点O与点O'，第一直流源Udc1和第二直流源Udc2直流电压均为Udc；The capacitor C1 and the capacitor C2 are connected in series between the DC positive bus P and the DC negative bus N of the first DC source U dc1 , and the common node of the capacitor C1 and the capacitor C2 is marked as point O; the capacitor C3 and the capacitor C4 is connected in series between the DC positive busbar P' and the DC negative busbar N' of the second DC source U dc2 , the common node of the capacitors C3 and C4 is marked as point O', and the neutral line I connects point O and point O ', the direct current voltages of the first direct current source U dc1 and the second direct current source U dc2 are both U dc ;

所述第一三相两电平逆变器VSI1的三相桥臂中，每相桥臂包括2个带反并联二极管的开关管，即第一三相两电平逆变器VSI1共包括6个带反并联二极管的开关管，6个开关管分别记为Sn1j，其中n表示相序，n＝a,b,c，j表示开关管的序号，j＝1,2；第一三相两电平逆变器VSI1的三相桥臂相互并联在直流正母线P与直流负母线N之间，即开关管Sa11、Sb11、Sc11的集电极并联后连接直流正母线P，开关管Sa12、Sb12、Sc12的发射极并联后连接直流负母线N；在第一三相两电平逆变器VSI1的三相桥臂中，开关管Sa11和开关管Sa12串联，开关管Sb11和开关管Sb12串联，开关管Sc11和开关管Sc12串联，其连接点分别记为第一三相两电平逆变器VSI1的三相桥臂中点a1、b1、c1；In the three-phase bridge arms of the first three-phase two-level inverter VSI1, each phase bridge arm includes two switch tubes with anti-parallel diodes, that is, the first three-phase two-level inverter VSI1 includes a total of six 6 switches with anti-parallel diodes, 6 switches are respectively denoted as S n1j , where n represents the phase sequence, n=a, b, c, j represents the serial number of the switches, j=1, 2; the first three-phase The three-phase bridge arms of the two-level inverter VSI1 are connected in parallel between the DC positive busbar P and the DC negative busbar N, that is, the collectors of the switch tubes S a11 , S b11 , and S c11 are connected in parallel and then connected to the DC positive bus bar P, the switch The emitters of the tubes S a12 , S b12 , and S c12 are connected in parallel and then connected to the DC negative busbar N; in the three-phase bridge arm of the first three-phase two-level inverter VSI1, the switch tube S a11 and the switch tube S a12 are connected in series, The switch tube S b11 and the switch tube S b12 are connected in series, and the switch tube S c11 and the switch tube S c12 are connected in series. 1 , c1 ;

所述第二三相两电平逆变器VSI2的三相桥臂中，每相桥臂包括2个带反并联二极管的开关管，即第二三相两电平逆变器VSI2共包括6个带反并联二极管的开关管，6个开关管分别记为Sn2j；第二三相两电平逆变器VSI2的三相桥臂相互并联在直流正母线P'与直流负母线N'之间，即开关管Sa21、Sb21、Sc21的集电极并联后连接直流正母线P'，开关管Sa22、Sb22、Sc22的发射极并联后连接直流负母线N'；在第二三相两电平逆变器VSI2的三相桥臂中，开关管Sa21和开关管Sa22串联,开关管Sb21和开关管Sb22串联，开关管Sc21和开关管Sc22串联，其连接点分别记为第二三相两电平逆变器VSI2的三相桥臂中点a2、b2、c2；In the three-phase bridge arms of the second three-phase two-level inverter VSI2, each phase bridge arm includes two switch tubes with anti-parallel diodes, that is, the second three-phase two-level inverter VSI2 includes a total of six 1 switch tubes with anti-parallel diodes, 6 switch tubes are respectively denoted as Sn2j ; the three-phase bridge arms of the second three-phase two-level inverter VSI2 are connected in parallel between the DC positive busbar P' and the DC negative busbar N'. between the collectors of the switches S a21 , S b21 , and S c21 are connected in parallel to the DC positive bus P', and the emitters of the switches S a22 , S b22 , and S c22 are connected in parallel and then connected to the DC negative bus N'; in the second In the three-phase bridge arm of the three-phase two-level inverter VSI2, the switch tube S a21 and the switch tube S a22 are connected in series, the switch tube S b21 and the switch tube S b22 are connected in series, and the switch tube S c21 and the switch tube S c22 are connected in series. The connection points are respectively recorded as midpoints a 2 , b 2 , and c 2 of the three-phase bridge arms of the second three-phase two-level inverter VSI2;

所述三相定子绕组OEWIM中包括三相绕组，A相绕组、B相绕组和C相绕组的左端口分别接第一三相两电平逆变器VSI1的三相桥臂中点a1、b1、c1，A相绕组、B相绕组和C相绕组的右端口分别接第二三相两电平逆变器VSI2的三相桥臂中点a2、b2、c2。The three-phase stator winding OEWIM includes three-phase windings, and the left ports of the A-phase winding, the B-phase winding and the C-phase winding are respectively connected to the midpoints a 1 of the three-phase bridge arms of the first three-phase two-level inverter VSI1, b 1 , c 1 , the right ports of the A-phase winding, the B-phase winding and the C-phase winding are respectively connected to the midpoints a 2 , b 2 and c 2 of the three-phase bridge arms of the second three-phase two-level inverter VSI2.

本发明包括下述步骤：The present invention includes the following steps:

图2为本发明实施例中任意一个调制体内的过调制运行流程图，对应步骤1-步骤3。FIG. 2 is a flow chart of the overmodulation operation in any modulation body in the embodiment of the present invention, corresponding to steps 1 to 3. FIG.

步骤1，设三相两电平逆变器需要调制的参考电压矢量为Vref，参考电压矢量为Vref对应两个逆变器VSI1和VSI2其中任意一个输出的参考电压矢量，将参考电压矢量Vref对三维空间坐标系中坐标轴α、β、γ轴的投影分量以直流电压Udc进行标幺化，分别记为参考电压矢量α轴分量Vα、参考电压矢量β轴分量Vβ、参考电压矢量γ轴分量Vγ，使用参考电压矢量α轴分量Vα、参考电压矢量β轴分量Vβ计算得出参考电压矢量Vref的α-β平面分量的幅值m1、参考电压矢量Vref的α-β平面分量的相位

Figure BDA0003143310430000091
和参考电压矢量Vref的α-β平面分量对应的调制度M1，计算式如下：Step 1, set the reference voltage vector to be modulated by the three-phase two-level inverter as V ref , and the reference voltage vector as V ref corresponding to the reference voltage vector output by any one of the two inverters VSI1 and VSI2, the reference voltage vector The projection components of the coordinate axes α, β, and γ in the three-dimensional space coordinate system by V ref are per-unitized by the DC voltage U dc , which are respectively recorded as the reference voltage vector α-axis component V α , the reference voltage vector β-axis component V β , The reference voltage vector γ-axis component V γ is calculated by using the reference voltage vector α-axis component V α and the reference voltage vector β-axis component V β to calculate the amplitude m 1 of the α-β plane component of the reference voltage vector V ref , the reference voltage vector Phase of the α-β plane component of Vref
Figure BDA0003143310430000091
The modulation degree M 1 corresponding to the α-β plane component of the reference voltage vector V ref is calculated as follows:

Figure BDA0003143310430000092
Figure BDA0003143310430000092

对参考电压矢量γ轴分量Vγ进行正交分解，得出两个相差90度的分量，分别记为参考电压矢量γ轴分量Vγ的第一正交分量Vγ，1和参考电压矢量γ轴分量Vγ的第二正交分量Vγ，2，计算得出参考电压矢量γ轴分量Vγ的幅值m3及参考电压矢量γ轴分量Vγ的相位

Figure BDA0003143310430000093
计算式如下：Orthogonal decomposition of the reference voltage vector γ-axis component V γ to obtain two components with a difference of 90 degrees, which are respectively recorded as the first quadrature component V γ, 1 of the reference voltage vector γ-axis component V γ and the reference voltage vector γ The second quadrature component V γ, 2 of the axis component V γ is calculated to obtain the amplitude m 3 of the reference voltage vector γ axis component V γ and the phase of the reference voltage vector γ axis component V γ
Figure BDA0003143310430000093
The calculation formula is as follows:

Figure BDA0003143310430000094
Figure BDA0003143310430000094

计算参考电压矢量Vref的特征相位差

Figure BDA0003143310430000101
计算式如下：Calculate the characteristic phase difference of the reference voltage vector Vref
Figure BDA0003143310430000101
The calculation formula is as follows:

Figure BDA0003143310430000102
Figure BDA0003143310430000102

步骤2，根据步骤1所得的参考电压矢量γ轴分量Vγ的幅值m3及参考电压矢量Vref的特征相位差

Figure BDA0003143310430000103
计算3D-SVPWM调制策略最大线性调制度Mmax1及最大压缩调制度Mmax2：Step 2, according to the amplitude m 3 of the reference voltage vector γ-axis component V γ and the characteristic phase difference of the reference voltage vector V ref obtained in step 1
Figure BDA0003143310430000103
Calculate the maximum linear modulation degree M max1 and the maximum compression modulation degree M max2 of the 3D-SVPWM modulation strategy:

定义函数式W1如下： The functional formula W1 is defined as follows:

Figure BDA0003143310430000104
Figure BDA0003143310430000104

定义函数式W2如下：The functional formula W 2 is defined as follows:

Figure BDA0003143310430000105
Figure BDA0003143310430000105

其中θ1的取值范围为

Figure BDA0003143310430000106
在θ1的取值范围内计算函数式W1最小值为W1min，计算函数式W2最小值为W2min，当W1min≤W2min时，Mmax1＝W1min，当W1min>W2min时，Mmax1＝W2min，计算函数式曲线W1和函数式W2曲线交点的函数值即为Mmax2。The value range of θ1 is
Figure BDA0003143310430000106
Within the value range of θ 1 , the minimum value of the calculation function formula W 1 is W 1min , and the minimum value of the calculation function formula W 2 is W 2min . When W 1min ≤W 2min , M max1 =W 1min , and when W 1min >W 2min When M max1 =W 2min , the function value of the intersection of the curve W 1 of the functional formula and the curve of the functional formula W 2 is calculated as M max2 .

步骤3，根据步骤1及步骤2所得参考电压矢量Vref的α-β平面分量对应的调制度M1和3D-SVPWM调制策略最大线性调制度Mmax1及最大压缩调制度Mmax2，进行过调制判断；Step 3: Perform overmodulation according to the modulation degree M 1 corresponding to the α-β plane component of the reference voltage vector V ref obtained in step 1 and step 2 and the maximum linear modulation degree M max1 and the maximum compression modulation degree M max2 of the 3D-SVPWM modulation strategy. judge;

当计算M1<Mmax1时，为线性调制区域，进入步骤3.1；When M 1 <M max1 is calculated, it is a linear modulation area, and go to step 3.1;

当计算Mmax1≤M1≤Mmax2时，为过调制区域，进入步骤3.2；When calculating M max1 ≤M 1 ≤M max2 , it is the overmodulation area, and go to step 3.2;

步骤3.1，计算M1<Mmax1时的线性调制区域，根据参考电压矢量α轴分量Vα、参考电压矢量β轴分量Vβ和参考电压矢量γ轴分量Vγ，使用3D-SVPWM调制策略计算基础电压矢量作用时间t0、基础电压矢量作用时间t1、基础电压矢量作用时间t2和基础电压矢量作用时间t7进行发波控制；时间t0、t1、t2、t7的具体计算过程参见公开日期为2018年11月5日的文献《共直流母线开绕组永磁同步电机的弱磁控制策略》(年珩等，中国电机工程学报，2018年第38卷第21期)的6461-6469页。Step 3.1, calculate the linear modulation area when M 1 <M max1 , according to the reference voltage vector α axis component V α , the reference voltage vector β axis component V β and the reference voltage vector γ axis component V γ , use the 3D-SVPWM modulation strategy to calculate The basic voltage vector action time t 0 , the basic voltage vector action time t 1 , the basic voltage vector action time t 2 and the basic voltage vector action time t 7 are used for wave generation control ; For the calculation process, please refer to the document "Field Weakening Control Strategy for Open-winding Permanent Magnet Synchronous Motors with Common DC Bus" published on November 5, 2018 (Nian Heng et al., Chinese Journal of Electrical Engineering, Vol. 38, No. 21, 2018). 6461-6469 pages.

步骤3.2，计算Mmax1≤M1≤Mmax2时的过调制区域；Step 3.2, calculate the overmodulation region when M max1 ≤ M 1 ≤ M max2 ;

步骤3.21，根据参考电压矢量α轴分量Vα、参考电压矢量β轴分量Vβ和参考电压矢量γ轴分量Vγ，使用3D-SVPWM调制策略计算基础电压矢量作用时间t0、基础电压矢量作用时间t1、基础电压矢量作用时间t2和基础电压矢量作用时间t7；Step 3.21, according to the reference voltage vector α-axis component V α , the reference voltage vector β-axis component V β and the reference voltage vector γ-axis component V γ , use the 3D-SVPWM modulation strategy to calculate the basic voltage vector action time t 0 , the basic voltage vector action time t 0 , and the basic voltage vector action time t 0 . time t 1 , basic voltage vector action time t 2 and basic voltage vector action time t 7 ;

当t0≥0且t7≥0时，为过调制区域的圆弧区，进入步骤3.22；When t 0 ≥ 0 and t 7 ≥ 0, it is the arc area of the overmodulation area, and go to step 3.22;

当t0<0或t7<0时，为过调制区域的边界区，进入步骤3.23；When t 0 <0 or t 7 <0, it is the boundary region of the overmodulation region, and go to step 3.23;

步骤3.22，由计算得出的基础电压矢量作用时间t0、基础电压矢量作用时间t1、基础电压矢量作用时间t2和基础电压矢量作用时间t7进行发波控制；Step 3.22, the wave generation control is performed based on the calculated basic voltage vector action time t 0 , the basic voltage vector action time t 1 , the basic voltage vector action time t 2 and the basic voltage vector action time t 7 ;

步骤3.23，对参考电压矢量Vref的α-β平面分量进行修改，首先根据参考电压矢量α轴分量Vα、参考电压矢量β轴分量Vβ和参考电压矢量γ轴分量Vγ对参考电压矢量Vref所在的调制体进行调制体序号判断，由判断的调制体序号选择对应的压缩平面约束方程，然后与瞬时误差最小压缩方案约束方程联立计算得出修改后参考电压矢量α轴分量

Figure BDA0003143310430000111
参考电压矢量β轴分量
Figure BDA0003143310430000112
根据修改后参考电压矢量α轴分量
Figure BDA0003143310430000113
参考电压矢量β轴分量
Figure BDA0003143310430000114
和参考电压矢量γ轴分量Vγ，使用3D-SVPWM调制策略计算基础电压矢量作用时间
Figure BDA0003143310430000115
基础电压矢量作用时间
Figure BDA0003143310430000116
基础电压矢量作用时间
Figure BDA0003143310430000117
和基础电压矢量作用时间
Figure BDA0003143310430000118
进行发波控制；时间
Figure BDA0003143310430000119
的具体计算过程参见参见公开日期为2018年11月5日的文献《共直流母线开绕组永磁同步电机的弱磁控制策略》(年珩等，中国电机工程学报，2018年第38卷第21期)的6461-6469页。Step 3.23, modify the α-β plane component of the reference voltage vector V ref , first, according to the reference voltage vector α-axis component V α , the reference voltage vector β-axis component V β and the reference voltage vector γ-axis component V γ , the reference voltage vector The modulation body where V ref is located is determined by the modulation body serial number, and the corresponding compression plane constraint equation is selected from the judged modulation body serial number, and then the α-axis component of the modified reference voltage vector is calculated simultaneously with the constraint equation of the minimum instantaneous error compression scheme.
Figure BDA0003143310430000111
Reference voltage vector β-axis component
Figure BDA0003143310430000112
According to the α-axis component of the modified reference voltage vector
Figure BDA0003143310430000113
Reference voltage vector β-axis component
Figure BDA0003143310430000114
and the reference voltage vector γ-axis component V γ , use the 3D-SVPWM modulation strategy to calculate the basic voltage vector action time
Figure BDA0003143310430000115
Basic voltage vector action time
Figure BDA0003143310430000116
Basic voltage vector action time
Figure BDA0003143310430000117
and base voltage vector action time
Figure BDA0003143310430000118
Carry out wave control; time
Figure BDA0003143310430000119
For the specific calculation process, please refer to the document "Field Weakening Control Strategy of Open-winding Permanent Magnet Synchronous Motor with Common DC Bus" published on November 5, 2018 (Nian Heng et al., Chinese Journal of Electrical Engineering, Vol. 38, No. 21, 2018) Issue) pp. 6461-6469.

调制体序号判断具体方式为：定义调制体序号判断的中间变量为第一变量A、第二变量B、第三变量C、第四变量N、第五变量A1、第六变量B1、第七变量C1、第八变量N1，定义函数式F1，

Figure BDA00031433104300001110
定义函数式F2，F2＝2Vγ-Vα，定义函数式F3，
Figure BDA00031433104300001111
定义函数式F4，F4＝Vβ，定义函数式F5，
Figure BDA00031433104300001112
定义函数式F6，
Figure BDA0003143310430000121
则：The specific way of judging the serial number of the modulating body is: define the intermediate variables for the judgment of the serial number of the modulating body as the first variable A, the second variable B, the third variable C, the fourth variable N, the fifth variable A 1 , the sixth variable B 1 , the first variable A 1 , the sixth variable B 1 , the The seven variables C 1 and the eighth variable N 1 define the functional formula F 1 ,
Figure BDA00031433104300001110
Define the functional formula F 2 , F 2 =2V γ -V α , define the functional formula F 3 ,
Figure BDA00031433104300001111
Define functional formula F 4 , F 4 =V β , define functional formula F 5 ,
Figure BDA00031433104300001112
Define the functional formula F 6 ,
Figure BDA0003143310430000121
but:

当F1≥0时，A＝1,When F 1 ≥ 0, A=1,

当F1<0时，A＝0，When F 1 <0, A=0,

当F2≥0时，B＝1,When F 2 ≥ 0, B=1,

当F2<0时，B＝0，When F 2 <0, B=0,

当F3≥0时，C＝1,When F 3 ≥ 0, C=1,

当F3<0时，C＝0，When F 3 <0, C=0,

N＝A+2B+4C，N=A+2B+4C,

当F4≥0时，A1＝1，When F 4 ≥ 0, A 1 =1,

当F4<0时，A1＝0，When F 4 <0, A 1 =0,

当F5≥0时，B1＝1，When F 5 ≥ 0, B 1 =1,

当F5<0时，B1＝0，When F 5 <0, B 1 =0,

当F6≥0时，C1＝1，When F 6 ≥ 0, C 1 =1,

当F6<0时，C1＝0，When F 6 <0, C 1 =0,

N1＝A1+2B1+4C1，N 1 =A 1 +2B 1 +4C 1 ,

第四变量N的每一个值对应一个调制体序号，具体如下：Each value of the fourth variable N corresponds to a modulation body serial number, as follows:

N＝5对应调制体1；N＝1对应调制体2；N＝3对应调制体3；N＝2对应调制体4；N＝6对应调制体5；N＝4对应调制体6；N＝0时需要结合第八变量N1值做进一步判断，其中当N1＝1或N1＝3时对应调制体2，当N1＝4或N1＝5时对应调制体4，当N1＝2或N1＝6时对应调制体6；N＝7时需要结合第八变量N1值做进一步判断，其中当N1＝2或N1＝3时对应调制体1，当N1＝1或N1＝5时对应调制体3，当N1＝4或N1＝6时对应调制体5。N=5 corresponds to modulator 1; N=1 corresponds to modulator 2; N=3 corresponds to modulator 3; N=2 corresponds to modulator 4; N=6 corresponds to modulator 5; N=4 corresponds to modulator 6; N= When it is 0, it needs to be further judged in combination with the value of the eighth variable N 1 . When N 1 =1 or N 1 =3, it corresponds to modulator 2, when N 1 =4 or N 1 =5, it corresponds to modulator 4, and when N 1 = 2 or N 1 =6, corresponding to modulating body 6; when N = 7, it is necessary to make further judgment in combination with the value of the eighth variable N 1 , wherein when N 1 =2 or N 1 =3, it corresponds to modulating body 1, and when N 1 = When 1 or N 1 =5, it corresponds to the modulator 3, and when N 1 =4 or N 1 =6, it corresponds to the modulator 5 .

第四变量N不同值与调制体序号的对应关系见下表：The corresponding relationship between the different values of the fourth variable N and the serial number of the modulation body is shown in the following table:

Figure BDA0003143310430000131
Figure BDA0003143310430000131

图3为本发明实施例中3D-SVPWM调制策略总调制体说明图，为3D-SVPWM调制策略在α-β-γ三维空间上的总调制体。FIG. 3 is an explanatory diagram of the overall modulation volume of the 3D-SVPWM modulation strategy in the embodiment of the present invention, which is the overall modulation volume of the 3D-SVPWM modulation strategy in the α-β-γ three-dimensional space.

图4为本发明实施例中3D-SVPWM调制策略调制体分开说明图，对图3中的总调制体分为六个调制体进行标注序号。FIG. 4 is a diagram illustrating the separation of modulation bodies of a 3D-SVPWM modulation strategy in an embodiment of the present invention, and the total modulation body in FIG. 3 is divided into six modulation bodies to be labeled with serial numbers.

由判断的调制体序号选择对应的压缩平面约束方程具体方式为：The specific method of selecting the corresponding compression plane constraint equation according to the judged modulation volume serial number is:

调制体1的压缩平面约束方程为：

Figure BDA0003143310430000132
The compression plane constraint equation of modulating body 1 is:
Figure BDA0003143310430000132

调制体2的压缩平面约束方程为：

Figure BDA0003143310430000133
The compression plane constraint equation of modulation volume 2 is:
Figure BDA0003143310430000133

调制体3的压缩平面约束方程为：

Figure BDA0003143310430000134
The compression plane constraint equation of modulation volume 3 is:
Figure BDA0003143310430000134

调制体4的压缩平面约束方程为：

Figure BDA0003143310430000135
The compression plane constraint equation of modulation volume 4 is:
Figure BDA0003143310430000135

调制体5的压缩平面约束方程为：

Figure BDA0003143310430000136
The compression plane constraint equation of the modulation body 5 is:
Figure BDA0003143310430000136

调制体6的压缩平面约束方程为：

Figure BDA0003143310430000137
The compression plane constraint equation of modulating body 6 is:
Figure BDA0003143310430000137

瞬时误差最小压缩方案约束方程如下：The constraint equation of the minimum instantaneous error compression scheme is as follows:

Figure BDA0003143310430000138
Figure BDA0003143310430000138

其中，P1、P2、P3分别为所选择的压缩平面约束方程中

Figure BDA0003143310430000139
前的系数及常数项；Among them, P 1 , P 2 , and P 3 are respectively in the selected compression plane constraint equation
Figure BDA0003143310430000139
The previous coefficients and constant terms;

即实现含过调制的3D-SVPWM调制策略发波控制。That is, the 3D-SVPWM modulation strategy with overmodulation can be realized.

为了验证本发明的有效性，对本发明进行了实验验证。共中线开绕组电驱动系统拓扑结构第一直流源Udc1和第二直流源Udc2的直流电压Udc均为280V，第一三相两电平逆变器VSI1和第二三相两电平逆变器VSI2主电路由三菱智能IGBT功率模块PM100CLA120构成，开关频率fs＝9600Hz，死区设定3μs。使用三相异步电机作为负载，异步电机参数：额定功率pn＝3kW，额定相电压UN＝220V，定子电阻Rs＝1.93Ω，互感Lm＝0.19H，定子电感Ls＝0.21H，极对数P＝2，运行频率fe＝50Hz。将共中线开绕组电驱动系统需要调制的参考电压矢量180度解耦平均分配给第一三相两电平逆变器VSI1和第二三相两电平逆变器VSI2进行调制，即两个三相两电平逆变器需要调制的参考电压矢量大小相等，方向相反。In order to verify the effectiveness of the present invention, the present invention has been experimentally verified. Common neutral open-winding electric drive system topology The DC voltages U dc of the first DC source U dc1 and the second DC source U dc2 are both 280V, the first three-phase two-level inverter VSI1 and the second three-phase two-power inverter The main circuit of the flat inverter VSI2 is composed of the Mitsubishi intelligent IGBT power module PM100CLA120, the switching frequency f s =9600Hz, and the dead zone is set to 3μs. Using a three-phase asynchronous motor as the load, the parameters of the asynchronous motor: rated power p n =3kW, rated phase voltage U N =220V, stator resistance R s =1.93Ω, mutual inductance L m =0.19H, stator inductance L s =0.21H, The number of pole pairs P=2, and the operating frequency f e =50Hz. The 180-degree decoupling of the reference voltage vector that needs to be modulated in the common-neutral open-winding electric drive system is evenly distributed to the first three-phase two-level inverter VSI1 and the second three-phase two-level inverter VSI2 for modulation, that is, two The three-phase two-level inverter needs to modulate the reference voltage vector with equal magnitude and opposite direction.

图5给出了对应第一三相两电平逆变器VSI1通过步骤1计算得出的参考电压矢量γ轴分量Vγ的幅值m3约为0.212，对应第一三相两电平逆变器VSI1的共模电压需求为59.4V,对应共中线开绕组电驱动系统总的共模电压需求为118.72V。Fig. 5 shows that the amplitude m 3 of the reference voltage vector γ-axis component V γ calculated in step 1 corresponding to the first three-phase two-level inverter VSI1 is about 0.212, corresponding to the first three-phase two-level inverse The common-mode voltage requirement of the inverter VSI1 is 59.4V, and the total common-mode voltage requirement corresponding to the common-neutral open-winding electric drive system is 118.72V.

图6给出了通过步骤1计算得出第一三相两电平逆变器VSI1的参考电压矢量Vref特征相位差

Figure BDA0003143310430000141
约为2.4。Figure 6 shows the characteristic phase difference of the reference voltage vector V ref of the first three-phase two-level inverter VSI1 calculated through step 1
Figure BDA0003143310430000141
about 2.4.

图7给出了在参考电压矢量γ轴分量Vγ的幅值m3约为0.212，参考电压矢量Vref的特征相位差

Figure BDA0003143310430000147
约为2.4条件下通过步骤2绘制的函数式曲线W1和函数式W2曲线，计算得出的对应第一三相两电平逆变器VSI1使用3D-SVPWM调制策略最大线性调制度Mmax1为0.6096，即对应第一三相两电平逆变器VSI1使用3D-SVPWM调制策略线性调制最大输出108.4V，计算得出最大压缩调制度Mmax2为1.04。Fig. 7 shows the characteristic phase difference of the reference voltage vector V ref when the amplitude m of the γ-axis component V γ of the reference voltage vector is about 0.212
Figure BDA0003143310430000147
Under the condition of about 2.4, through the functional curve W 1 and the functional formula W 2 drawn in step 2, the calculated maximum linear modulation degree M max1 corresponding to the first three-phase two-level inverter VSI1 using the 3D-SVPWM modulation strategy is 0.6096, that is, corresponding to the first three-phase two-level inverter VSI1, the 3D-SVPWM modulation strategy is used to linearly modulate the maximum output of 108.4V, and it is calculated that the maximum compression modulation degree M max2 is 1.04.

图8给出了第一三相两电平逆变器VSI1参考电压矢量Vref的α-β平面分量对应的调制度M1从0.6上升到0.8时，使用3D-SVPWM调制策略调制时共中线开绕组电驱动系统总输出的基波电压幅值变化情况示意图。可见使用本过调制策略能够有效地将总输出的基波电压幅值突破传统线性调制最大约束216.8V，提升到265V左右，有效提升3D-SVPWM调制策略调制范围。Figure 8 shows that the modulation factor M1 corresponding to the α-β plane component of the reference voltage vector V ref of the first three-phase two-level inverter VSI1 rises from 0.6 to 0.8, when the 3D-SVPWM modulation strategy is used to modulate the common neutral line Schematic diagram of the fundamental voltage amplitude change of the total output of the open-winding electric drive system. It can be seen that the use of this overmodulation strategy can effectively break the total output fundamental voltage amplitude of 216.8V, which is the maximum constraint of traditional linear modulation, and increase it to about 265V, effectively increasing the modulation range of the 3D-SVPWM modulation strategy.

如图9所示，Vref为参考电压矢量，V*为经过本发明技术方案步骤1～3后，由计算所得的修改后参考电压矢量α轴分量

Figure BDA0003143310430000142
参考电压矢量β轴分量
Figure BDA0003143310430000143
和参考电压矢量γ轴分量Vγ为坐标组成的修改后参考电压矢量。修改后参考电压矢量V*顶点位于调制体外表面上的空间直线
Figure BDA0003143310430000144
空间直线
Figure BDA0003143310430000145
与参考电压矢量Vref等高，因此保证了本发明技术方案方案的共模分量输出能够跟随指令。本发明技术方案的压缩方案约束方程使得参考电压矢量Vref往空间直线
Figure BDA0003143310430000146
做垂线，其垂足即为修改后参考电压矢量V*顶点。参考电压矢量Vref、修改后参考电压矢量V*的顶点和空间直线
Figure BDA0003143310430000151
在αβ平面的投影分别记为点D、G和直线
Figure BDA0003143310430000152
矢量
Figure BDA0003143310430000153
为本发明技术方案方案的修改后参考电压矢量V*与参考电压矢量Vref之间的差模瞬时误差矢量，由
Figure BDA0003143310430000154
垂直于
Figure BDA0003143310430000155
可知本发明技术方案方案的瞬时误差矢量最小。As shown in FIG. 9 , Vref is the reference voltage vector, and V * is the α-axis component of the modified reference voltage vector obtained by calculation after going through steps 1 to 3 of the technical solution of the present invention
Figure BDA0003143310430000142
Reference voltage vector β-axis component
Figure BDA0003143310430000143
and the reference voltage vector γ-axis component V γ is the modified reference voltage vector composed of coordinates. The modified reference voltage vector V * is the space line whose vertex lies on the outer surface of the modulating body
Figure BDA0003143310430000144
space line
Figure BDA0003143310430000145
It is the same height as the reference voltage vector V ref , thus ensuring that the output of the common mode component of the technical solution of the present invention can follow the command. The compression scheme constraint equation of the technical scheme of the present invention makes the reference voltage vector V ref go to the space straight line
Figure BDA0003143310430000146
Make a vertical line, and its vertical foot is the vertex of the modified reference voltage vector V * . Reference voltage vector V ref , vertex and space line of modified reference voltage vector V *
Figure BDA0003143310430000151
The projections on the αβ plane are denoted as points D, G and lines, respectively
Figure BDA0003143310430000152
vector
Figure BDA0003143310430000153
is the differential mode instantaneous error vector between the modified reference voltage vector V * and the reference voltage vector Vref according to the technical solution of the present invention, and is given by
Figure BDA0003143310430000154
perpendicular to
Figure BDA0003143310430000155
It can be seen that the instantaneous error vector of the technical solution of the present invention is the smallest.

在实验中，还采用以下方式对调制体序号判断进行了验证。In the experiment, the judgment of the serial number of the modulation body is also verified by the following methods.

由图10可见，在一个基波周期内第四变量N值按顺序变化，对应参考电压矢量Vref从调制体1到调制体6连续旋转一周，可见调制体序号判断准确有效。It can be seen from Fig. 10 that the value of the fourth variable N changes sequentially in one fundamental wave period, and the corresponding reference voltage vector V ref rotates continuously from the modulator 1 to the modulator 6 for one cycle. It can be seen that the judgment of the modulator serial number is accurate and effective.

以上实施例仅用以说明本发明的技术方案，而非对其限制；尽管参照前述实施例对本发明进行了详细的说明，本领域的普通技术人员应当理解：其依然可以对前述各实施例所记载的技术方案进行修改，或者对其中部分技术特征进行等同替换；而这些修改或者替换，并不使相应技术方案的本质脱离本发明各实施例技术方案的精神和范围。The above embodiments are only used to illustrate the technical solutions of the present invention, but not to limit them; although the present invention has been described in detail with reference to the foregoing embodiments, those of ordinary skill in the art should understand that: The recorded technical solutions are modified, or some technical features thereof are equivalently replaced; and these modifications or replacements do not make the essence of the corresponding technical solutions deviate from the spirit and scope of the technical solutions of the embodiments of the present invention.

Claims (8)

1.一种瞬时误差最小的3D-SVPWM调制策略过调制方法，其特征在于，包括以下步骤：1. a minimum 3D-SVPWM modulation strategy overmodulation method of instantaneous error, is characterized in that, comprises the following steps: 步骤S1，计算参考电压矢量Vref的α-β平面分量的幅值m1、相位
Figure FDA0003143310420000011
和调制度M1，计算参考电压矢量Vref的γ轴分量Vγ的幅值m3及相位
Figure FDA0003143310420000012
计算参考电压矢量Vref的特征相位差
Figure FDA0003143310420000013
Step S1, calculate the amplitude m 1 and phase of the α-β plane component of the reference voltage vector V ref
Figure FDA0003143310420000011
and the modulation degree M 1 , calculate the amplitude m 3 and phase of the γ-axis component V γ of the reference voltage vector V ref
Figure FDA0003143310420000012
Calculate the characteristic phase difference of the reference voltage vector Vref
Figure FDA0003143310420000013
 步骤S2，根据步骤S1中的幅值m3及特征相位差
Figure FDA0003143310420000017
计算3D-SVPWM调制策略最大线性调制度Mmax1及最大压缩调制度Mmax2；Step S2, according to the amplitude m 3 and the characteristic phase difference in step S1
Figure FDA0003143310420000017
Calculate the maximum linear modulation degree M max1 and the maximum compression modulation degree M max2 of the 3D-SVPWM modulation strategy; 步骤S3，根据调制度M1、最大线性调制度Mmax1及最大压缩调制度Mmax2，进行过调制判断：Step S3, according to the modulation degree M 1 , the maximum linear modulation degree M max1 and the maximum compression modulation degree M max2 , perform overmodulation judgment: 当计算M1<Mmax1时，为线性调制区域，采用线性调制区域发波控制，方法为：根据Vα、Vβ和Vγ，使用3D-SVPWM调制策略计算基础电压矢量作用时间t0、t1、t2和t7进行发波控制；When M 1 < M max1 is calculated , it is a linear modulation region, and the linear modulation region is used for wave control. t 1 , t 2 and t 7 perform wave emission control; 当计算Mmax1≤M1≤Mmax2时，为过调制区域，采用过调制区域发波控制，方法为：When M max1 ≤M 1 ≤M max2 is calculated, it is the over-modulation region, and the over-modulation region is used for wave control. The method is as follows: 当t0≥0且t7≥0时，为过调制区域的圆弧区，根据Vα、Vβ和Vγ，使用3D-SVPWM调制策略计算基础电压矢量作用时间t0、t1、t2和t7进行发波控制；When t 0 ≥ 0 and t 7 ≥ 0, it is the arc area of the overmodulation area. According to V α , V β and V γ , the 3D-SVPWM modulation strategy is used to calculate the basic voltage vector action time t 0 , t 1 , t 2 and t 7 for wave control; 当t0<0或t7<0时，为过调制区域的边界区，对参考电压矢量Vref的α-β平面分量进行修改：When t 0 <0 or t 7 <0, it is the boundary region of the overmodulation region, and the α-β plane component of the reference voltage vector Vref is modified: 首先根据Vα、Vβ和Vγ对参考电压矢量Vref所在的调制体进行调制体序号判断，由判断的调制体序号选择对应的压缩平面约束方程；Firstly, according to V α , V β and V γ , the modulation body serial number is judged for the modulation body where the reference voltage vector V ref is located, and the corresponding compression plane constraint equation is selected according to the judged modulation body serial number; 然后与瞬时误差最小压缩方案约束方程联立计算得出修改后参考电压矢量α轴分量
Figure FDA0003143310420000014
参考电压矢量β轴分量
Figure FDA0003143310420000015
所述的瞬时误差最小压缩方案约束方程如下：Then, the α-axis component of the modified reference voltage vector is calculated simultaneously with the constraint equation of the minimum compression scheme of the instantaneous error.
Figure FDA0003143310420000014
Reference voltage vector β-axis component
Figure FDA0003143310420000015
The constraint equation of the minimum instantaneous error compression scheme described is as follows:
Figure FDA0003143310420000016
Figure FDA0003143310420000016
 其中，P1、P2、P3分别为所选择的压缩平面约束方程中
Figure FDA0003143310420000021
前的系数及常数项；Among them, P 1 , P 2 , and P 3 are respectively in the selected compression plane constraint equation
Figure FDA0003143310420000021
The previous coefficients and constant terms; 最后根据修改后参考电压矢量α轴分量
Figure FDA0003143310420000022
修改后参考电压矢量β轴分量
Figure FDA0003143310420000023
和Vγ，使用3D-SVPWM调制策略计算修改后基础电压矢量作用时间
Figure FDA0003143310420000024
和
Figure FDA0003143310420000025
进行发波控制。Finally, according to the α-axis component of the modified reference voltage vector
Figure FDA0003143310420000022
Modified reference voltage vector β-axis component
Figure FDA0003143310420000023
and V γ , use the 3D-SVPWM modulation strategy to calculate the modified base voltage vector action time
Figure FDA0003143310420000024
and
Figure FDA0003143310420000025
Perform wave control. 2.根据权利要求1所述的一种瞬时误差最小的3D-SVPWM调制策略过调制方法，其特征在于，步骤S1中计算参考电压矢量Vref的α-β平面分量的幅值m1、相位
Figure FDA0003143310420000026
和调制度M1的公式为：2. The 3D-SVPWM modulation strategy overmodulation method with minimum instantaneous error according to claim 1, wherein in step S1, the amplitude m 1 , the phase of the α-β plane component of the reference voltage vector V ref are calculated
Figure FDA0003143310420000026
The formula for the sum modulation degree M 1 is:
Figure FDA0003143310420000027
Figure FDA0003143310420000027
 3.根据权利要求2所述的一种瞬时误差最小的3D-SVPWM调制策略过调制方法，其特征在于，步骤S1中计算参考电压矢量Vref的γ轴分量Vγ的幅值m3及相位
Figure FDA0003143310420000028
的公式为：3. a kind of 3D-SVPWM modulation strategy overmodulation method with minimum instantaneous error according to claim 2, is characterized in that, in step S1, calculate the amplitude m 3 and the phase of the γ-axis component V γ of the reference voltage vector V ref
Figure FDA0003143310420000028
The formula is:
Figure FDA0003143310420000029
Figure FDA0003143310420000029
 4.根据权利要求2所述的一种瞬时误差最小的3D-SVPWM调制策略过调制方法，其特征在于，步骤S1中计算参考电压矢量Vref的特征相位差
Figure FDA00031433104200000210
计算式如下：4. a kind of 3D-SVPWM modulation strategy overmodulation method with minimum instantaneous error according to claim 2, is characterized in that, in step S1, calculate the characteristic phase difference of reference voltage vector V ref
Figure FDA00031433104200000210
The calculation formula is as follows:
Figure FDA00031433104200000211
Figure FDA00031433104200000211
 5.根据权利要求2所述的一种瞬时误差最小的3D-SVPWM调制策略过调制方法，其特征在于，步骤S2中计算3D-SVPWM调制策略最大线性调制度Mmax1及最大压缩调制度Mmax2具体为：5. the minimum 3D-SVPWM modulation strategy overmodulation method of a kind of instantaneous error according to claim 2, is characterized in that, calculates 3D-SVPWM modulation strategy maximum linear modulation degree M max1 and maximum compression modulation degree M max2 in step S2 Specifically: 定义函数式W1，Define the functional formula W 1 ,
Figure FDA0003143310420000031
Figure FDA0003143310420000031
 定义函数式W2，Define the functional formula W 2 ,
Figure FDA0003143310420000032
Figure FDA0003143310420000032
 其中，θ1的取值范围为
Figure FDA0003143310420000033
在θ1的取值范围内计算函数式W1最小值为W1min，计算函数式W2最小值为W2min，当W1min≤W2min时，Mmax1＝W1min，当W1min>W2min时，Mmax1＝W2min，计算函数式曲线W1和函数式W2曲线交点的函数值即为Mmax2。Among them, the value range of θ1 is
Figure FDA0003143310420000033
Within the value range of θ 1 , the minimum value of the calculation function formula W 1 is W 1min , and the minimum value of the calculation function formula W 2 is W 2min . When W 1min ≤W 2min , M max1 =W 1min , and when W 1min >W 2min When M max1 =W 2min , the function value of the intersection of the curve W 1 of the functional formula and the curve of the functional formula W 2 is calculated as M max2 . 6.根据权利要求1所述的一种瞬时误差最小的3D-SVPWM调制策略过调制方法，其特征在于，所述的调制体序号判断的具体方式为：6. a kind of 3D-SVPWM modulation strategy overmodulation method with minimum instantaneous error according to claim 1, is characterized in that, the concrete mode that described modulation body serial number judges is: 定义调制体序号判断的中间变量为第一变量A、第二变量B、第三变量C、第四变量N、第五变量A1、第六变量B1、第七变量C1、第八变量N1，定义函数式F1，
Figure FDA0003143310420000034
定义函数式F2，F2＝2Vγ-Vα，定义函数式F3，
Figure FDA0003143310420000035
定义函数式F4，F4＝Vβ，定义函数式F5，
Figure FDA0003143310420000036
定义函数式F6，
Figure FDA0003143310420000037
则：The intermediate variables that define the modulation body serial number judgment are the first variable A, the second variable B, the third variable C, the fourth variable N, the fifth variable A 1 , the sixth variable B 1 , the seventh variable C 1 , and the eighth variable N 1 , define the functional formula F 1 ,
Figure FDA0003143310420000034
Define the functional formula F 2 , F 2 =2V γ -V α , define the functional formula F 3 ,
Figure FDA0003143310420000035
Define functional formula F 4 , F 4 =V β , define functional formula F 5 ,
Figure FDA0003143310420000036
Define the functional formula F 6 ,
Figure FDA0003143310420000037
but: 当F1≥0时，A＝1；当F1<0时，A＝0；当F2≥0时，B＝1；当F2<0时，B＝0；当F3≥0时，C＝1；当F3<0时，C＝0；N＝A+2B+4C；When F 1 ≥ 0, A=1; when F 1 <0, A=0; when F 2 ≥ 0, B=1; when F 2 <0, B=0; when F 3 ≥ 0 , C=1; when F 3 <0, C=0; N=A+2B+4C; 当F4≥0时，A1＝1；当F4<0时，A1＝0；当F5≥0时，B1＝1；当F5<0时，B1＝0；当F6≥0时，C1＝1；当F6<0时，C1＝0；N1＝A1+2B1+4C1；When F 4 ≥ 0, A 1 =1; when F 4 <0, A 1 =0; when F 5 ≥ 0, B 1 =1; when F 5 <0, B 1 =0; When 6 ≥ 0, C 1 =1; when F 6 <0, C 1 =0; N 1 =A 1 +2B 1 +4C 1 ; 第四变量N的每一个值对应一个调制体序号，具体如下：N＝5对应调制体1；N＝1对应调制体2；N＝3对应调制体3；N＝2对应调制体4；N＝6对应调制体5；N＝4对应调制体6；N＝0时需要结合第八变量N1值做进一步判断，其中当N1＝1或N1＝3时对应调制体2，当N1＝4或N1＝5时对应调制体4，当N1＝2或N1＝6时对应调制体6；N＝7时需要结合第八变量N1值做进一步判断，其中当N1＝2或N1＝3时对应调制体1，当N1＝1或N1＝5时对应调制体3，当N1＝4或N1＝6时对应调制体5。Each value of the fourth variable N corresponds to a modulation body serial number, as follows: N=5 corresponds to modulation body 1; N=1 corresponds to modulation body 2; N=3 corresponds to modulation body 3; N=2 corresponds to modulation body 4; N =6 corresponds to modulating body 5; N=4 corresponds to modulating body 6; when N=0, further judgment needs to be made in conjunction with the value of the eighth variable N 1 , wherein when N 1 =1 or N 1 =3, it corresponds to modulating body 2, and when N When 1 = 4 or N 1 =5, it corresponds to modulator 4; when N 1 =2 or N 1 =6, it corresponds to modulator 6; when N = 7, it is necessary to make further judgments based on the value of the eighth variable N 1 , where when N 1 = 2 or N 1 =3, it corresponds to modulator 1, when N 1 =1 or N 1 =5, corresponds to modulator 3, and when N 1 =4 or N 1 =6, corresponds to modulator 5. 7.根据权利要求1所述的一种瞬时误差最小的3D-SVPWM调制策略过调制方法，其特征在于，所述的由判断的调制体序号选择对应的压缩平面约束方程的具体方式为：7. the minimum 3D-SVPWM modulation strategy overmodulation method of a kind of instantaneous error according to claim 1, is characterized in that, the described concrete mode of selecting corresponding compression plane constraint equation by the modulation body serial number of judgment is: 调制体1的压缩平面约束方程为：
Figure FDA0003143310420000041
The compression plane constraint equation of modulating body 1 is:
Figure FDA0003143310420000041
 调制体2的压缩平面约束方程为：
Figure FDA0003143310420000042
The compression plane constraint equation of modulation volume 2 is:
Figure FDA0003143310420000042
 调制体3的压缩平面约束方程为：
Figure FDA0003143310420000043
The compression plane constraint equation of modulation volume 3 is:
Figure FDA0003143310420000043
 调制体4的压缩平面约束方程为：
Figure FDA0003143310420000044
The compression plane constraint equation of modulation volume 4 is:
Figure FDA0003143310420000044
 调制体5的压缩平面约束方程为：
Figure FDA0003143310420000045
The compression plane constraint equation of the modulation body 5 is:
Figure FDA0003143310420000045
 调制体6的压缩平面约束方程为：
Figure FDA0003143310420000046
The compression plane constraint equation of modulating body 6 is:
Figure FDA0003143310420000046
 8.一种应用于权利要求1-7任一项所述的瞬时误差最小的3D-SVPWM调制策略过调制方法的系统，其特征在于，包括：第一直流源Udc1、第二直流源Udc2、第一三相两电平逆变器VSI1、第二三相两电平逆变器VSI2、三相定子绕组OEWIM、中线I、电容C1、电容C2、电容C3和电容C4；8. A system applied to the 3D-SVPWM modulation strategy overmodulation method with minimum instantaneous error according to any one of claims 1-7, characterized in that, comprising: a first DC source U dc1 , a second DC source U dc2 , the first three-phase two-level inverter VSI1, the second three-phase two-level inverter VSI2, the three-phase stator winding OEWIM, the neutral line I, the capacitor C1, the capacitor C2, the capacitor C3 and the capacitor C4; 所述电容C1和电容C2串联后连接在第一直流源Udc1的直流正母线P与直流负母线N之间，电容C1、电容C2的公共节点记为点O；所述电容C3和电容C4串联后连接在第二直流源Udc2的直流正母线P'与直流负母线N'之间，电容C3、电容C4的公共节点记为点O'，所述中线I连接点O与点O'，第一直流源Udc1和第二直流源Udc2直流电压均为Udc；The capacitor C1 and the capacitor C2 are connected in series between the DC positive bus P and the DC negative bus N of the first DC source U dc1 , and the common node of the capacitor C1 and the capacitor C2 is marked as point O; the capacitor C3 and the capacitor C4 is connected in series between the DC positive busbar P' and the DC negative busbar N' of the second DC source U dc2 , the common node of the capacitors C3 and C4 is marked as point O', and the neutral line I connects point O and point O ', the direct current voltages of the first direct current source U dc1 and the second direct current source U dc2 are both U dc ; 所述第一三相两电平逆变器VSI1的三相桥臂中，每相桥臂包括2个带反并联二极管的开关管，即第一三相两电平逆变器VSI1共包括6个带反并联二极管的开关管，6个开关管分别记为Sn1j，其中n表示相序，n＝a,b,c，j表示开关管的序号，j＝1,2；第一三相两电平逆变器VSI1的三相桥臂相互并联在直流正母线P与直流负母线N之间，即开关管Sa11、Sb11、Sc11的集电极并联后连接直流正母线P，开关管Sa12、Sb12、Sc12的发射极并联后连接直流负母线N；在第一三相两电平逆变器VSI1的三相桥臂中，开关管Sa11和开关管Sa12串联，开关管Sb11和开关管Sb12串联，开关管Sc11和开关管Sc12串联，其连接点分别记为第一三相两电平逆变器VSI1的三相桥臂中点a1、b1、c1；In the three-phase bridge arms of the first three-phase two-level inverter VSI1, each phase bridge arm includes two switch tubes with anti-parallel diodes, that is, the first three-phase two-level inverter VSI1 includes a total of six 6 switches with anti-parallel diodes, 6 switches are respectively denoted as S n1j , where n represents the phase sequence, n=a, b, c, j represents the serial number of the switches, j=1, 2; the first three-phase The three-phase bridge arms of the two-level inverter VSI1 are connected in parallel between the DC positive busbar P and the DC negative busbar N, that is, the collectors of the switch tubes S a11 , S b11 , and S c11 are connected in parallel and then connected to the DC positive bus bar P, the switch The emitters of the tubes S a12 , S b12 , and S c12 are connected in parallel and then connected to the DC negative busbar N; in the three-phase bridge arm of the first three-phase two-level inverter VSI1, the switch tube S a11 and the switch tube S a12 are connected in series, The switch tube S b11 and the switch tube S b12 are connected in series, and the switch tube S c11 and the switch tube S c12 are connected in series. 1 , c1 ; 所述第二三相两电平逆变器VSI2的三相桥臂中，每相桥臂包括2个带反并联二极管的开关管，即第二三相两电平逆变器VSI2共包括6个带反并联二极管的开关管，6个开关管分别记为Sn2j；第二三相两电平逆变器VSI2的三相桥臂相互并联在直流正母线P'与直流负母线N'之间，即开关管Sa21、Sb21、Sc21的集电极并联后连接直流正母线P'，开关管Sa22、Sb22、Sc22的发射极并联后连接直流负母线N'；在第二三相两电平逆变器VSI2的三相桥臂中，开关管Sa21和开关管Sa22串联，开关管Sb21和开关管Sb22串联，开关管Sc21和开关管Sc22串联，其连接点分别记为第二三相两电平逆变器VSI2的三相桥臂中点a2、b2、c2；In the three-phase bridge arms of the second three-phase two-level inverter VSI2, each phase bridge arm includes two switch tubes with anti-parallel diodes, that is, the second three-phase two-level inverter VSI2 includes a total of six 1 switch tubes with anti-parallel diodes, 6 switch tubes are respectively denoted as Sn2j ; the three-phase bridge arms of the second three-phase two-level inverter VSI2 are connected in parallel between the DC positive busbar P' and the DC negative busbar N'. between the collectors of the switches S a21 , S b21 , and S c21 are connected in parallel to the DC positive bus P', and the emitters of the switches S a22 , S b22 , and S c22 are connected in parallel and then connected to the DC negative bus N'; in the second In the three-phase bridge arm of the three-phase two-level inverter VSI2, the switch tube S a21 and the switch tube S a22 are connected in series, the switch tube S b21 and the switch tube S b22 are connected in series, and the switch tube S c21 and the switch tube S c22 are connected in series. The connection points are respectively recorded as midpoints a 2 , b 2 , and c 2 of the three-phase bridge arms of the second three-phase two-level inverter VSI2; 所述三相定子绕组OEWIM中包括三相绕组，A相绕组、B相绕组和C相绕组的左端口分别接第一三相两电平逆变器VSI1的三相桥臂中点a1、b1、c1，A相绕组、B相绕组和C相绕组的右端口分别接第二三相两电平逆变器VSI2的三相桥臂中点a2、b2、c2。The three-phase stator winding OEWIM includes three-phase windings, and the left ports of the A-phase winding, the B-phase winding and the C-phase winding are respectively connected to the midpoints a 1 of the three-phase bridge arms of the first three-phase two-level inverter VSI1, b 1 , c 1 , the right ports of the A-phase winding, the B-phase winding and the C-phase winding are respectively connected to the midpoints a 2 , b 2 and c 2 of the three-phase bridge arms of the second three-phase two-level inverter VSI2.
CN202110746997.5A 2021-07-01 2021-07-01 Overmodulation method and system for 3D-SVPWM modulation strategy with minimum instantaneous error Active CN113364326B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN202110746997.5A CN113364326B (en) 2021-07-01 2021-07-01 Overmodulation method and system for 3D-SVPWM modulation strategy with minimum instantaneous error

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202110746997.5A CN113364326B (en) 2021-07-01 2021-07-01 Overmodulation method and system for 3D-SVPWM modulation strategy with minimum instantaneous error

Publications (2)

Publication Number Publication Date
CN113364326A true CN113364326A (en) 2021-09-07
CN113364326B CN113364326B (en) 2022-09-16

Family

ID=77537950

Family Applications (1)

Application Number Title Priority Date Filing Date
CN202110746997.5A Active CN113364326B (en) 2021-07-01 2021-07-01 Overmodulation method and system for 3D-SVPWM modulation strategy with minimum instantaneous error

Country Status (1)

Country Link
CN (1) CN113364326B (en)

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103107761A (en) * 2013-01-11 2013-05-15 哈尔滨工业大学 Three-dimensional space vector pulse width modulation (SVPWM) method based on four-phrase five-wire topology
US20150311818A1 (en) * 2014-04-23 2015-10-29 National Tsing Hua University Load impedance estimation and repetitive control method capable of allowing inductance variation for inverter
CN107196543A (en) * 2017-07-05 2017-09-22 合肥工业大学 Zero-sequence circulating current suppression method for open-winding asynchronous motor system with common DC bus
CN110995115A (en) * 2019-12-23 2020-04-10 深圳市凌康技术有限公司 Improved three-dimensional space vector modulation method and system

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN103107761A (en) * 2013-01-11 2013-05-15 哈尔滨工业大学 Three-dimensional space vector pulse width modulation (SVPWM) method based on four-phrase five-wire topology
US20150311818A1 (en) * 2014-04-23 2015-10-29 National Tsing Hua University Load impedance estimation and repetitive control method capable of allowing inductance variation for inverter
CN107196543A (en) * 2017-07-05 2017-09-22 合肥工业大学 Zero-sequence circulating current suppression method for open-winding asynchronous motor system with common DC bus
CN110995115A (en) * 2019-12-23 2020-04-10 深圳市凌康技术有限公司 Improved three-dimensional space vector modulation method and system

Non-Patent Citations (4)

* Cited by examiner, † Cited by third party
Title
JOSÉ LUIS MONROY MORALES ET AL.: "A digital control for a Three-Dimensional SV-PWM multilevel converter", 《2014 IEEE INTERNATIONAL AUTUMN MEETING ON POWER, ELECTRONICS AND COMPUTING (ROPEC)》 *
LIN ZHOU ET AL.: "Application of a four-leg ASVG based on", 《PROCEEDINGS. INTERNATIONAL CONFERENCE ON POWER SYSTEM TECHNOLOGY》 *
卢远宏等: "基于空间直角坐标系的逆变器调制波研究", 《电工技术学报》 *
胡慧慧等: "抑制三相四桥臂逆变器共模电压的三维SVPWM控制策略", 《电力系统自动化》 *

Also Published As

Publication number Publication date
CN113364326B (en) 2022-09-16

Similar Documents

Publication Publication Date Title
CN103986357B (en) Method for restraining circulating current in modular multilevel converter for high-voltage direct current transmission
JP4429338B2 (en) Motor control device, current detection unit
CN110855165B (en) Discontinuous Pulse Width Modulation Method for Control Circuit of Three-Phase Vienna Rectifier
CN108418489B (en) Vector control method of open-winding permanent magnet synchronous motor for suppressing zero-sequence current
CN109039207B (en) An N-phase N+1 bridge arm inverter and its modulation method
JP2010068653A (en) Inverter control apparatus and motor drive system
CN104242775A (en) Zero-sequence current suppression method of open type permanent magnet synchronous motor with double-inverter power supply
CN107872167B (en) Virtual space vector modulation method for voltage type three-level neutral point clamped converter
CN1732618A (en) Motor drive unit for air conditioner
CN110247568B (en) A three-phase diode-clamped three-level dual-output inverter topology
CN112436752B (en) Inverter 12-sector virtual vector overmodulation strategy
CN111654225A (en) A Model Predictive Current Control Method for Open Winding Permanent Magnet Vernier Linear Motors
CN109728756B (en) Dual reference voltage single vector open-winding permanent magnet motor predictive control method and device
Wu et al. Equivalent three-vector-based model predictive control with duty-cycle reconstruction for pmsm
CN109861622B (en) Low switching frequency control strategy of common direct current bus open winding permanent magnet synchronous motor system
CN113364327B (en) Output harmonic minimization 3D-AZSPWM modulation strategy overmodulation method and system
CN113364326B (en) Overmodulation method and system for 3D-SVPWM modulation strategy with minimum instantaneous error
CN113364328B (en) Overmodulation output maximization method and system of 3D-SVPWM (three-dimensional-space vector pulse width modulation) strategy
CN113364330B (en) Output harmonic wave minimized 3D-SVPWM modulation strategy overmodulation method and system
CN113364325B (en) 3D-SVPWM modulation strategy rapid overmodulation method and system
CN105958525B (en) A PWM grid-connected inverter control method for a permanent magnet wind power generation system
CN117526792A (en) Common-mode voltage suppression method for permanent magnet synchronous motor
CN113364331B (en) Overmodulation method and system for 3D-AZSPWM modulation strategy with minimum instantaneous error
CN113364329B (en) Overmodulation output maximization method and system of 3D-AZSPWM modulation strategy
CN117394725A (en) Zero sequence component injection DPWM modulation method for driving double Y-shift 30-degree six-phase permanent magnet synchronous motor

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant