CN112821747B - Three-phase staggered parallel PFC circuit based on coupling inductor and control system - Google Patents
Three-phase staggered parallel PFC circuit based on coupling inductor and control system Download PDFInfo
- Publication number
- CN112821747B CN112821747B CN202011550360.0A CN202011550360A CN112821747B CN 112821747 B CN112821747 B CN 112821747B CN 202011550360 A CN202011550360 A CN 202011550360A CN 112821747 B CN112821747 B CN 112821747B
- Authority
- CN
- China
- Prior art keywords
- inductor
- circuit
- coupling
- phase
- pfc
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
Images
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4233—Arrangements for improving power factor of AC input using a bridge converter comprising active switches
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M7/2176—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only comprising a passive stage to generate a rectified sinusoidal voltage and a controlled switching element in series between such stage and the output
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The invention provides a three-phase interleaved parallel PFC circuit based on coupling inductance and a control system, wherein the three-phase interleaved parallel PFC circuit comprises: the three-phase commercial power input end, the three-level PFC conversion circuit and the bus capacitor circuit, wherein the three-level PFC conversion circuit comprises three groups of two-way PFC conversion circuits, each phase input of the three-phase commercial power input end is connected to the one group of two-way PFC conversion circuit, and one end, far away from the three-phase commercial power input section, of each group of PFC conversion circuit is connected to the midpoint of the bus capacitor circuit; each group of PFC conversion circuits comprises a coupling inductor, two switching circuits and two diode circuits, one end of the coupling inductor is connected to the three-phase mains supply input end, and the other end of the coupling inductor is connected with the switching circuits and the diode circuits respectively. The invention can greatly reduce input current ripple and output current ripple, effectively reduce the volume and quantity of the inductor and increase the power density.
Description
Technical Field
The invention relates to a PFC (power factor correction) conversion circuit, in particular to a three-phase interleaved parallel PFC circuit based on coupling inductance and a control system comprising the three-phase interleaved parallel PFC circuit based on the coupling inductance.
Background
A Vienna three-phase active power factor correction circuit (PFC for short) adopted by a high-power AC-DC power supply is a relatively mature technology, but with the continuous increase of power requirements, the existing traditional Vienna three-phase PFC circuit has the problems of large inductive current ripple, large volume, large semiconductor current stress, difficulty in heat dissipation and the like.
The existing traditional solutions for increasing output power are: by adopting a device parallel connection mode, the problem of overlarge current stress can be solved, but the problems of overlarge inductor volume, excessively concentrated heating, unfavorable heat dissipation, incapability of completely ensuring current balance of parallel tubes and the like still exist; the parallel connection of the independent inductors is adopted, but the problems of increased inductor number, increased cost, increased volume and the like are also brought.
Disclosure of Invention
The invention aims to solve the technical problem of providing a three-phase interleaving PFC circuit based on coupling inductance, which can reduce the ripple current of the circuit and reduce the volume and the quantity of the inductance, and further providing a control system comprising the three-phase interleaving PFC circuit based on the coupling inductance.
In contrast, the present invention provides a three-phase interleaved parallel PFC circuit based on a coupled inductor, comprising: the three-level PFC conversion circuit comprises three groups of two-way PFC conversion circuits, each phase input of the three-phase mains supply input end is connected to one group of two-way PFC conversion circuits, and one end, far away from the three-phase mains supply input end, of each group of two-way PFC conversion circuits is connected to the middle point of the bus capacitance circuit; the group of two-way PFC conversion circuits comprises a coupling inductor, two-way switching circuits and two-way diode circuits, wherein one end of the coupling inductor is connected to the three-phase mains supply input end, the other end of the coupling inductor is respectively connected with the switching circuits and the diode circuits, and the switching circuits and the diode circuits are respectively connected with the bus capacitor circuit; the cycle start time and the cycle end time of two switching circuits in the same PFC conversion circuit group are different.
The invention has the further improvement that the two PFC conversion circuits of each group have the same structure, and the control time sequence difference between the switching circuits of the two adjacent groups of PFC conversion circuits is one third of the period or 120 degrees of phase difference.
The invention is further improved in that the starting time and the ending time of the period of the second path of switching circuit are different from the starting time and the ending time of the period of the first path of switching circuit by half a period in a group of two paths of PFC conversion circuits connected to the same phase input.
The further improvement of the present invention lies in that the switch circuit includes a bidirectional switch, the diode circuit includes a first diode and a second diode, one end of the coupling inductor, which is far away from the three-phase mains input end, is respectively connected with one end of the bidirectional switch, an anode of the first diode and a cathode of the second diode, the other end of the bidirectional switch is connected to a midpoint of the bus capacitor circuit, and a cathode of the first diode and an anode of the second diode are respectively connected to two ends of the bus capacitor circuit.
The invention is further improved in that the coupling inductor is an inductor which is wound on a common magnetic core through two inductor coils, and the value range of the coupling coefficient M of the two inductor coils is 0-1 by adjusting the coil distance of the inductor and the structure of the magnetic core.
The further improvement of the invention is that the winding turns of the two inductance coils of the coupling inductance are the same, and the inductance is the same; and the different-name ends of one side of the two inductance coils are connected and are connected with an input alternating current phase line of the three-phase commercial power input end.
A further improvement of the present invention is that the coupling inductance comprises two or more coupling inductances connected in series.
The invention is further improved in that the coupling inductor comprises a first coupling inductor L1 and a second coupling inductor L2 which are connected in series, the first coupling inductor L1 and the second coupling inductor L2 have the same structure, and the coil turn ratios are all N1: n2; a coil N1 dotted terminal of the first coupling inductor L1 is connected to the three-phase mains supply input terminal, a coil N1 dotted terminal of the first coupling inductor L1 is connected to a coil N2 dotted terminal of the second coupling inductor L2, and a coil N2 dotted terminal of the second coupling inductor L2 is connected to the switch circuit of the first path and the diode circuit of the first path; a coil N2 synonym terminal of the first coupling inductor L1 is connected to the three-phase mains supply input terminal, a coil N2 synonym terminal of the first coupling inductor L1 is connected to a coil N1 synonym terminal of the second coupling inductor L2, and a coil N1 synonym terminal of the second coupling inductor L2 is connected to the switch circuit of the second path and the diode circuit of the second path.
The further improvement of the present invention lies in that the coupling inductor includes a first coupling inductor L1 and a second coupling inductor L2 connected in series, the first coupling inductor L1 and the second coupling inductor L2 have the same structure, and the coil turns ratio is N1: n2; after the coil N1 of the first coupling inductor L1 is completed, the coil N2 is continuously wound on the magnetic ring of the second coupling inductor L2, and after the coil N1 of the second coupling inductor L2 is completed, the coil N2 is continuously wound on the magnetic ring of the first coupling inductor L1.
The invention is further improved in that, for the magnetic core with a fixed structure, by adjusting the coil turn ratio N1 of the first coupling inductor L1 and the second coupling inductor L2: n2, the coupling coefficient M can be adjusted equivalently, the coupling coefficient M is close to 1 when N1 equals N2, the coupling coefficient M is close to 0 when N1 equals 0 or N2 equals 0, and the coil ratio N1 equals N2 is adjusted so that 0< M < 1.
The invention also provides a three-phase interleaved parallel PFC circuit control system based on the coupling inductor, which comprises the three-phase interleaved parallel PFC circuit based on the coupling inductor.
Compared with the prior art, the invention has the beneficial effects that: the coupling inductor is adopted to replace an independent inductor, the structural design and the time sequence control of the circuit are optimized, and each winding of the coupling inductor is respectively connected to the three-level PFC conversion circuits which are connected in parallel in a staggered mode, so that the input current ripple and the output current ripple can be greatly reduced, the volume and the number of the inductor can be effectively reduced, the volume of an input EMC filter is reduced, the EMC interference is reduced, the number of output filter capacitors can be reduced, and the power density is increased; on the basis, the coupling inductor can be further optimized to reduce the height and the volume of the inductor device, improve the power density and reduce the cost.
Drawings
FIG. 1 is a circuit schematic of one embodiment of the present invention;
FIG. 2 is a schematic diagram illustrating a simulation of the relationship between the inductor current waveform and the input total current according to an embodiment of the present invention;
FIG. 3 is a schematic diagram of the equivalent circuit of the PFC converter circuit in working condition and the waveform of the coupled inductor current;
FIG. 4 is a schematic diagram of an optimization circuit according to an embodiment of the present invention;
FIG. 5 is a schematic diagram of a re-optimization circuit of one embodiment of the present invention;
fig. 6 is a schematic top view of an optimized coupling inductor according to an embodiment of the present invention;
fig. 7 is a schematic front view of an optimized coupling inductor according to an embodiment of the present invention;
fig. 8 is a schematic bottom view of a coupling inductor according to an embodiment of the invention.
Detailed Description
Preferred embodiments of the present invention will be described in further detail below with reference to the accompanying drawings.
As shown in fig. 1, this example provides a three-phase interleaved parallel PFC circuit based on coupled inductors, including: the three-phase commercial power input end 1, the three-level PFC conversion circuit 2 and the bus capacitor circuit 3, wherein the three-level PFC conversion circuit 2 comprises three groups of two-way PFC conversion circuits, each phase input of the three-phase commercial power input end 1 is connected to one group of two-way PFC conversion circuits, and one end, far away from the three-phase commercial power input end 1, of each group of two-way PFC conversion circuits is connected to the midpoint of the bus capacitor circuit 3; the group of two-way PFC conversion circuit comprises a coupling inductor 201, two-way switch circuits 202 and two-way diode circuits 203, one end of the coupling inductor 201 is connected to the three-phase mains supply input end 1, the other end of the coupling inductor 201 is respectively connected with the switch circuits 202 and the diode circuits 203, and the switch circuits 202 and the diode circuits 203 are respectively connected with the bus capacitor circuit 3; the PFC conversion circuit is also called a PFC converter; the single-phase coupling inductor 201 may be one or more.
The three-phase mains supply input end 1 comprises three-phase input of VA, VB and VC, each phase input is connected to two paths of PFC conversion circuits with the same structure, three groups of PFC converters are counted, and the three-level PFC conversion circuit 2 is realized; the bus capacitor circuit 3 refers to a bus circuit where a bus capacitor C01 and a bus capacitor C02 are located; the circuit can reduce the ripple current of the circuit and the volume and the number of inductors; on the basis, the current stress of the power device can be reduced, and the power density is improved; after the structural design and the time sequence control of the circuit are optimized, the three-phase power factor correction circuit can overcome the defects of the existing three-phase power factor correction circuit, effectively reduces the volume and the number of inductors, improves the power density and reduces the cost.
That is, the two PFC converter circuits in each group have the same structure, and each PFC converter circuit includes a switch circuit 202 and a diode circuit 203, where the switch circuit 202 preferably uses a bidirectional switch, such as a switch tube S1 and a switch tube S2 or a switch tube S3 and a switch tube S4, and the diode circuit 203 preferably uses two diodes, such as a diode D1 and a diode D2 or a diode D3 and a diode D4, and is a group of two PFC converter circuits; the other two groups of PFC converter circuits have the same structure as shown in fig. 1.
That is, in this example, the switch circuit 202 includes a bidirectional switch (e.g., a switch tube S1 and a switch tube S2), the diode circuit 203 includes a first diode (e.g., a diode D1) and a second diode (e.g., a diode D2), one end of the coupling inductor 201, which is away from the three-phase mains input terminal 1, is respectively connected to one end of the bidirectional switch (e.g., a switch tube S1 and a switch tube S2), an anode of the first diode (e.g., a diode D1), and a cathode of the second diode (e.g., a diode D2), the other ends of the bidirectional switch (e.g., a switch tube S1 and a switch tube S2) are connected to a midpoint of the bus capacitor circuit 3, and a cathode of the first diode (e.g., a diode D1) and an anode of the second diode (e.g., a diode D2) are respectively connected to two ends of the bus capacitor circuit 3; the other PFC conversion circuits adopt the same mechanism.
Each group of PFC conversion circuits (one group of PFC conversion circuits comprises two paths of PFC conversion circuits) comprises a coupling inductor 201, which is different from a common discrete inductor, the coupling inductor 201 is an inductor formed by winding two inductor coils on a common magnetic core, the two inductor coils reach different coupling coefficients M by adjusting the coil distance and the magnetic core structure of the inductor, and the coupling coefficients M can be adjusted according to actual needs or circuits, and the value range of the coupling coefficients M is 0-1.
Preferably, in this embodiment, the two inductance coils of the coupling inductance 201 have the same winding number and the same inductance; and the different-name ends of one side of the two inductance coils are connected and are connected with an input alternating current phase line of the three-phase commercial power input end 1.
In this embodiment, the period start time and the period end time of the two switching circuits in the same PFC converter circuit group are different, and preferably, the period start time and the period end time of the switching circuit 202 in the second switching circuit group are different from the period start time and the period end time of the switching circuit 202 in the first switching circuit group by half a period when the switching circuits 202 in the second switching circuit group are connected to the PFC converter circuit group of the same input phase. For example, the two paths of PFC converter circuits of the first group of two paths of PFC converter circuits are switched on and off under the control of the inductor current, wherein the start and end times of the period of the second/second path of PFC converter circuits 202 are advanced or delayed by half the period time of the first/first path of PFC converter circuits 202, that is, the two paths of PFC converter circuits are divided into two paths of circuits controlled by 180 degrees in an interlaced manner in a single-phase PFC converter circuit, so as to optimize the control process of the three-phase PFC converter circuits connected in parallel in an interlaced manner based on the coupled inductor. The switching circuit 202 in this example is preferably a bi-directional switch.
The control timing difference between the switch circuits 202 of two adjacent groups of PFC conversion circuits in this example is one third of a cycle or 120 ° in phase.
Referring to fig. 1, the specific control timing sequence of the bidirectional switch 202 of the six-path PFC converter circuit is as follows: assuming that the control period of the bidirectional switch 202 is T, at a time T equal to 0, the switching tube S1 and the switching tube S2 in the bidirectional switch (the switching circuit 202) of the first path are controlled to be turned on, and at a time T equal to 1/2T, the switching tube S3 and the switching tube S4 in the bidirectional switch (the switching circuit 202) of the second path are controlled to be turned on; at time T of 1/3T, the switching tube S5 and the switching tube S6 of the bidirectional switch (the switching circuit 202) in the third path are controlled to be turned on; when T is 5/6T, the switching tube S7 and the switching tube S8 of the bidirectional switch (the switching circuit 202) in the fourth path are controlled to be turned on; when T is 2/3T, the switching tube S9 and the switching tube S10 of the bidirectional switch (the switching circuit 202) in the fifth path are controlled to be turned on; when T is 7/6T, that is, at the time of the next cycle 1/6T, the switching tube S11 and the switching tube S12 of the bidirectional switch (the switching circuit 202) in the sixth path are controlled to be turned on; the closing time of each two-way switch is controlled by hardware or software according to the working state of the circuit.
In the first set of two-way PFC converter circuits described in this example, the two switching circuits 202 are controlled to be turned on and off by the inductor current, wherein the start and end times of the cycle of the second/second switching circuit 202 are advanced or delayed by half the cycle time of the first switching circuit 202. The waveforms of the inductive current of the two PFC conversion circuits and the total current of the first input are shown in fig. 2, so that the current ripples are offset after the two PFC conversion circuits are connected in parallel in a staggered manner, and the total current ripple is greatly smaller than the single current ripple.
The three-level PFC converter circuit 2 of the present embodiment may be divided into three-phase interleaved 120-degree phase-controlled coupled inductor interleaved PFC circuits, and each phase coupled inductor interleaved PFC circuit may be equivalent to a single-phase coupled inductor PFC circuit in the positive half cycle and the negative half cycle of the input alternating current, as shown in fig. 3. The switching tube S1 and the switching tube S2 are turned on, the pulse phase difference is Ts/2(Ts is the switching period), the on pulse width is equal, and the self inductance of the coupling inductor 201 is equal (L1 is equal to L2 is equal to L). The PFC conversion circuit has 4 working states in total. The equivalent circuit of half a switching cycle, two operating modes, and one switching cycle coupled inductor current waveform are shown in fig. 3.
When the device is in the first working mode t 0-t 1: before the time t0, the switching tube S2 is cut off, and the inductor L2 discharges through the diode D2; at time t0, switching tube S1 is turned on, and current i1 rises linearly, so that there is a possibility that current i2 rises due to the coupling effect of inductance. According to analysis, whether the current i2 rises or not depends on the magnitude of the coupling coefficient M of the inductor L1 and the inductor L2 and the magnitude of the on-duty ratio D.
When the working mode is the second working mode t 1-t 2: the switch tube S1 is turned off, the switch tube S2 is turned off, the switch tube S1 is turned off, the current i1 flows through the diode D1, the current i2 flows through the diode D2, and the current i1 and the current i2 both decrease linearly.
After time t3, the coupling inductor 201 alternates the parallel PFC converter into the next half of the switching cycle, and the two operating modes in this half of the switching cycle are similar to the two operating modes in the first half of the switching cycle, except that the two channels are switched.
Setting the duty cycle to D, the voltage gain can be calculated as:
(ii) a The coupling inductor 201 is only related to the conduction duty ratio of the output voltage of the interleaved parallel PFC conversion circuit, and is not related to other factors such as the coupling coefficient and the load. Therefore, a control scheme which is reliable and mature before can be adopted on the circuit control, namely:
. The above equation shows that the coupling inductance staggers and connects the current ripples of each channel of the PFC converter in parallel, and the ripples are related to the coupling coefficient. The coupling coefficient M can be adjusted according to the actual circuit requirement, so that the control system and the control process of the three-phase interleaved parallel PFC circuit based on the coupling inductor are more flexible, and the adaptability is stronger.
The size of the coupling inductor 201 shown in fig. 1 is reduced compared to the conventional circuit, but the optimized design shown in fig. 4 can be adopted to achieve the objectives of smaller size, thinner thickness and higher power density, for which the coupling inductor 201 in this embodiment includes two or more coupling inductors connected in series. The design can further solve the problems of height, volume, heat dissipation and the like, and one coupling inductor 201 is divided into two or more coupling inductors connected in series, so that the height and the volume are further reduced, and the heat dissipation is optimized. The series-connected coupling inductors 201 can be made of traditional annular magnetic rings, the equivalent coupling coefficient M can be controlled by adjusting the proportion of coils, the height and the size of an inductor device can be reduced, heat is dispersed, and the power density is improved.
In this embodiment, two or more coupling inductors 201 are adopted, and the number of turns of the coupling coils may be different, that is, the coupling inductor 201 includes a first coupling inductor L1 and a second coupling inductor L2 connected in series, the first coupling inductor L1 and the second coupling inductor L2 have the same structure, in fact, the first coupling inductor L1 to the sixth coupling inductor L6 are the same type of inductor, and the coil number ratio is N1: n2, such a design facilitates manufacturing and fabrication; the connection method comprises the following steps: a coil N1 of the first coupling inductor L1 is connected with an input A-phase voltage in a homonymous mode, a coil N1 of the first coupling inductor L1 is connected with a coil N2 of the second coupling inductor L2 in a synonym mode, and a coil N2 of the second coupling inductor L2 is connected with a switch tube S1, a diode D1 and a diode D2 in a synonym mode; a coil N2 of the first coupling inductor L1 is connected with an input A-phase voltage in a different name mode, a coil N2 of the first coupling inductor L1 is connected with a coil N1 different name end of the second coupling inductor L2 in a same name mode, and a coil N1 of the second coupling inductor L2 is connected with a switch tube S2, a diode D3 and a diode D4 in a same name mode.
In other words, in this embodiment, the dotted terminal of the coil N1 of the first coupling inductor L1 is connected to the three-phase mains input terminal 1, the dotted terminal of the coil N1 of the first coupling inductor L1 is connected to the dotted terminal of the coil N2 of the second coupling inductor L2, and the dotted terminal of the coil N2 of the second coupling inductor L2 is connected to the switch circuit 202 of the first path and the diode circuit 203 of the first path; a coil N2 synonym terminal of the first coupling inductor L1 is connected to the three-phase mains input terminal 1, a coil N2 synonym terminal of the first coupling inductor L1 is connected to a coil N1 synonym terminal of the second coupling inductor L2, and a coil N1 synonym terminal of the second coupling inductor L2 is connected to the switch circuit 202 of the second path and the diode circuit 203 of the second path.
Preferably, for a magnetic core with a fixed structure, by adjusting the coil turn ratio N1 of each of the first coupling inductor L1 and the second coupling inductor L2: n2, the coupling coefficient M can be adjusted equivalently, the coupling coefficient M is close to 1 when N1 equals N2, the coupling coefficient M is close to 0 when N1 equals 0 or N2 equals 0, and 0< M <1 by adjusting the coil ratio N1 equals N2.
The other two corresponding PFC conversion circuits are connected similarly.
Therefore, the preferred circuit topology using two coupling inductors in this embodiment has the advantage that, in some conventional inductors, such as inductors wound by a toroidal magnetic ring, the magnetic core of the conventional inductor is circular and cannot change the magnetic circuit, and when the conventional inductor is used for manufacturing the coupling inductor, the coupling coefficient of the conventional inductor cannot be adjusted, so that the parameter performance of the conventional inductor cannot be optimized by adjusting the coupling coefficient. By adopting 2 or more coupled inductors, the inductor can be manufactured by winding a traditional annular magnetic ring, and the ratio of the coupled turns is adjusted to be N1: n2 adjusts the equivalent coupling coefficient. Assuming N1> N2, then N1: the larger the proportion of N2, the smaller the equivalent coupling coefficient.
In a specific embodiment, for example, for a toroidal inductor, two separate coupling inductors may be further combined, as shown in fig. 5, the coupling inductor 201 includes a first coupling inductor L1 and a second coupling inductor L2 connected in series, the first coupling inductor L1 and the second coupling inductor L2 have the same structure, and the coil turn ratio is N1: n2; after the coil N1 of the first coupling inductor L1 is completed, the coil N2 is continuously wound on the magnetic ring of the second coupling inductor L2, and after the coil N1 of the second coupling inductor L2 is completed, the coil N2 is continuously wound on the magnetic ring of the first coupling inductor L1, so that 4 outgoing pins can be reduced, the size is further reduced, the PCB layout is facilitated, and specific structural drawings are shown in fig. 6 to 8.
The present example also provides a three-phase interleaved parallel PFC circuit control system based on the coupling inductor 201, which includes the three-phase interleaved parallel PFC circuit based on the coupling inductor 201 as described above.
In summary, the coupling inductor 201 is adopted to replace an independent inductor, the structural design and the time sequence control of the circuit are optimized, each winding of the coupling inductor 201 is connected to the three-level PFC conversion circuit 2 in a staggered and parallel connection mode, so that the input current ripple and the output current ripple can be greatly reduced, the volume and the number of inductors can be effectively reduced, the volume of an input EMC filter can be reduced, the EMC interference can be reduced, the number of output filter capacitors can be reduced, and the power density can be increased; on the basis, the coupling inductor 201 can be further optimized to reduce the height and volume of the inductor device, disperse heat and improve power density.
The foregoing is a more detailed description of the invention in connection with specific preferred embodiments and it is not intended that the invention be limited to these specific details. For those skilled in the art to which the invention pertains, numerous simple deductions or substitutions may be made without departing from the spirit of the invention, which shall be deemed to belong to the scope of the invention.
Claims (9)
1. A three-phase interleaved parallel PFC circuit based on a coupled inductor is characterized by comprising: the three-phase commercial power input end, the three-level PFC conversion circuit and the bus capacitor circuit, wherein the three-level PFC conversion circuit comprises three groups of two-way PFC conversion circuits, each phase input of the three-phase commercial power input end is connected to one group of two-way PFC conversion circuit, and one end, far away from the three-phase commercial power input end, of each group of two-way PFC conversion circuit is connected to the midpoint of the bus capacitor circuit; the PFC conversion circuit with the two circuits comprises a coupling inductor, two switching circuits and two diode circuits, one end of the coupling inductor is connected to the three-phase mains supply input end, the other end of the coupling inductor is respectively connected with the switching circuit and the diode circuits, and the switching circuit and the diode circuits are respectively connected with the bus capacitor circuit; the cycle start time and the cycle end time of two switching circuits in the same group of PFC conversion circuits are different;
the coupling inductors comprise two or more coupling inductors connected in series; the coupling inductor comprises a first coupling inductor L1 and a second coupling inductor L2 which are connected in series, the first coupling inductor L1 and the second coupling inductor L2 have the same structure, and the coil number ratio is N1: n2; a coil N1 dotted terminal of the first coupling inductor L1 is connected to the three-phase mains supply input terminal, a coil N1 dotted terminal of the first coupling inductor L1 is connected to a coil N2 dotted terminal of the second coupling inductor L2, and a coil N2 dotted terminal of the second coupling inductor L2 is connected to the switch circuit of the first path and the diode circuit of the first path; a coil N2 synonym terminal of the first coupling inductor L1 is connected to the three-phase mains supply input terminal, a coil N2 synonym terminal of the first coupling inductor L1 is connected to a coil N1 synonym terminal of the second coupling inductor L2, and a coil N1 synonym terminal of the second coupling inductor L2 is connected to the switch circuit of the second path and the diode circuit of the second path.
2. The three-phase interleaved PFC circuit according to claim 1, wherein the two PFC converter circuits in each group have the same structure, and the control timing difference between the switching circuits of two adjacent PFC converter circuits is one-third of a cycle or 120 ° out of phase.
3. The three-phase interleaved parallel PFC circuit according to claim 1, wherein the starting and ending times of the cycle of the second switching circuit are different from the starting and ending times of the cycle of the first switching circuit by half a cycle when the two switching circuits are connected to a group of two-way PFC conversion circuits of the same phase input.
4. The three-phase interleaved PFC circuit of any one of claims 1 to 3, wherein the switching circuit comprises a bidirectional switch, the diode circuit comprises a first diode and a second diode, one end of the coupling inductor, which is away from the three-phase mains input end, is connected to one end of the bidirectional switch, an anode of the first diode and a cathode of the second diode, respectively, the other end of the bidirectional switch is connected to a middle point of the bus capacitor circuit, and a cathode of the first diode and an anode of the second diode are connected to two ends of the bus capacitor circuit, respectively.
5. The three-phase interleaved PFC circuit according to any one of claims 1 to 3, wherein the coupling inductor is an inductor wound on a common magnetic core through two inductor coils, and the coil distance and the magnetic core structure of the inductor are adjusted so that the coupling coefficient M of the two inductor coils ranges from 0 to 1.
6. The three-phase interleaved parallel PFC circuit according to claim 5, wherein the two inductor coils of the coupling inductor have the same winding number and the same inductance; and the different-name ends of one side of the two inductance coils are connected and are connected with an input alternating current phase line of the three-phase commercial power input end.
7. The coupled inductor-based three-phase interleaved parallel PFC circuit according to any one of claims 1 to 3, wherein the coupled inductor comprises a first coupled inductor L1 and a second coupled inductor L2 which are connected in series, the first coupled inductor L1 and the second coupled inductor L2 are identical in structure, and the coil number ratio of the coupled inductors is N1: n2; after the coil N1 of the first coupling inductor L1 is completed, the coil N2 is continuously wound on the magnetic ring of the second coupling inductor L2, and after the coil N1 of the second coupling inductor L2 is completed, the coil N2 is continuously wound on the magnetic ring of the first coupling inductor L1.
8. The coupled inductor based three-phase interleaved PFC circuit of any one of claims 1 to 3, wherein for a fixed structure core, by adjusting a coil turn ratio N1 of each of the first coupled inductor L1 and the second coupled inductor L2: n2, the coupling coefficient M can be adjusted equivalently, the coupling coefficient M is close to 1 when N1= N2, and the coupling coefficient M is close to 0 when N1=0 or N2=0, by adjusting the coil ratio N1: N2 so that 0< M < 1.
9. A three-phase interleaved PFC circuit control system based on a coupled inductor is characterized by comprising the three-phase interleaved PFC circuit based on the coupled inductor, which is disclosed by any one of claims 1 to 8.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202011550360.0A CN112821747B (en) | 2020-12-24 | 2020-12-24 | Three-phase staggered parallel PFC circuit based on coupling inductor and control system |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202011550360.0A CN112821747B (en) | 2020-12-24 | 2020-12-24 | Three-phase staggered parallel PFC circuit based on coupling inductor and control system |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN112821747A CN112821747A (en) | 2021-05-18 |
| CN112821747B true CN112821747B (en) | 2022-06-21 |
Family
ID=75853753
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202011550360.0A Active CN112821747B (en) | 2020-12-24 | 2020-12-24 | Three-phase staggered parallel PFC circuit based on coupling inductor and control system |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN112821747B (en) |
Families Citing this family (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN117439429B (en) * | 2023-12-21 | 2024-04-12 | 广东省洛仑兹技术股份有限公司 | Control method of soft switch Vienna rectifying circuit and storage medium |
Citations (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102739033A (en) * | 2012-06-23 | 2012-10-17 | 杭州中恒电气股份有限公司 | Interleaved parallel three-phase power factor correction circuit |
| CN106385171A (en) * | 2016-09-30 | 2017-02-08 | 深圳市奥耐电气技术有限公司 | Interleaved parallel three-phase PFC circuit |
| CN107222115A (en) * | 2017-06-02 | 2017-09-29 | 杭州中恒电气股份有限公司 | A kind of Three phase power factor correcting converter |
| CN206620047U (en) * | 2017-02-17 | 2017-11-07 | 先控捷联电气股份有限公司 | Interleaving PFC power conversion circuit |
| CN107623436A (en) * | 2017-10-17 | 2018-01-23 | 西安麦格米特电气有限公司 | A kind of PFC supply units |
| CN110383660A (en) * | 2017-03-23 | 2019-10-25 | 华为技术有限公司 | The power supply of high efficiency and low ripple |
| CN110504849A (en) * | 2019-09-16 | 2019-11-26 | 连云港杰瑞电子有限公司 | A kind of no differential mode inductance staggered-parallel-type Vienna rectifier and its control circuit |
| WO2020061905A1 (en) * | 2018-09-27 | 2020-04-02 | Abb Schweiz Ag | Apparatus for conversion between ac power and dc power |
Family Cites Families (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103700473B (en) * | 2013-12-12 | 2017-11-28 | 华为技术有限公司 | Coupling inductance and power inverter |
| CN116798757A (en) * | 2020-03-11 | 2023-09-22 | 杭州禾迈电力电子股份有限公司 | Coupling inductance element and micro-inversion system inversion topological structure |
-
2020
- 2020-12-24 CN CN202011550360.0A patent/CN112821747B/en active Active
Patent Citations (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102739033A (en) * | 2012-06-23 | 2012-10-17 | 杭州中恒电气股份有限公司 | Interleaved parallel three-phase power factor correction circuit |
| CN106385171A (en) * | 2016-09-30 | 2017-02-08 | 深圳市奥耐电气技术有限公司 | Interleaved parallel three-phase PFC circuit |
| CN206620047U (en) * | 2017-02-17 | 2017-11-07 | 先控捷联电气股份有限公司 | Interleaving PFC power conversion circuit |
| CN110383660A (en) * | 2017-03-23 | 2019-10-25 | 华为技术有限公司 | The power supply of high efficiency and low ripple |
| CN107222115A (en) * | 2017-06-02 | 2017-09-29 | 杭州中恒电气股份有限公司 | A kind of Three phase power factor correcting converter |
| CN107623436A (en) * | 2017-10-17 | 2018-01-23 | 西安麦格米特电气有限公司 | A kind of PFC supply units |
| WO2020061905A1 (en) * | 2018-09-27 | 2020-04-02 | Abb Schweiz Ag | Apparatus for conversion between ac power and dc power |
| CN110504849A (en) * | 2019-09-16 | 2019-11-26 | 连云港杰瑞电子有限公司 | A kind of no differential mode inductance staggered-parallel-type Vienna rectifier and its control circuit |
Also Published As
| Publication number | Publication date |
|---|---|
| CN112821747A (en) | 2021-05-18 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| US9923476B2 (en) | Switching power supply and method for controlling switching power supply | |
| CN108028605A (en) | With the converter for keeping operation | |
| CN210380663U (en) | Bidirectional multipath parallel full-bridge LLC resonant converter | |
| KR102009351B1 (en) | High Efficiency LLC Resonant Converter with Balanced Secondary Currents using the Two Transformer Structure | |
| CN111355378A (en) | LLC resonant DC/DC converter | |
| CN112821747B (en) | Three-phase staggered parallel PFC circuit based on coupling inductor and control system | |
| CN104135154A (en) | Isolated four-element resonance circuit and control method | |
| Alaql et al. | Review and comparison of resonant DC-DC converters for wide-input voltage range applications | |
| CN109818494B (en) | High-gain voltage type quasi-Y source direct current-direct current converter | |
| CN214674879U (en) | Three-phase staggered parallel PFC circuit based on coupling inductor and control system | |
| CN101697456A (en) | Rectifying circuit capable of realizing voltage clamping of rectifier tube by using two power transformers | |
| CN112350583A (en) | Current type push-pull bridge type soft switching bidirectional direct current converter | |
| Jia et al. | Analysis and implementation of LC series resonant converter with secondary Side clamp diodes under DCM operation for high step-up applications | |
| CN114884363B (en) | Double LLC resonant converter with six-time gain ratio and control method thereof | |
| CN103515071A (en) | High-voltage coarse and fine regulation on-load voltage regulation power transformer | |
| CN217693114U (en) | Single-stage rectification circuit based on magnetic control | |
| CN110299849A (en) | A kind of interleaving shunt-wound two-transistor forward power converter of phase shifting control | |
| CN109194144A (en) | A kind of double positive activation type booster circuits of crisscross parallel | |
| CN211701855U (en) | Input stage boost two-stage converter for ultrathin high-power-density module power supply | |
| CN110729913B (en) | Single-stage high-gain five-switch Boost type inverter | |
| CN113315381A (en) | Novel LCLCL resonant converter and high-efficiency resonant driving method thereof | |
| CN113014087A (en) | Coupling inductance type switch quasi-Z-source bidirectional direct current converter | |
| EP3504783B1 (en) | Sandwich wound inductance | |
| CN201418031Y (en) | Power source supply device with current sharing function | |
| CN112421962B (en) | Two-stage DC-DC converter with partial power regulation function |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant | ||
| TR01 | Transfer of patent right |
Effective date of registration: 20230831 Address after: Floor 9, Keshida Industrial Park R&D Building, No.7 Road, Gaoxinyuan West District, Guangming New District, Shenzhen, Guangdong 518000 Patentee after: SHENZHEN KSTAR NEW ENERGY Co.,Ltd. Address before: 518000 rooms 401 and 402, 4th floor, building 1, software park, kejizhong 2nd Road, Gaoxin North District, Nanshan District, Shenzhen City, Guangdong Province Patentee before: SHENZHEN KSTAR SCIENCE AND TECHNOLOGY Co.,Ltd. Patentee before: Guangdong Youdian New Energy Technology Co.,Ltd. |
|
| TR01 | Transfer of patent right |