CN214674879U - Three-phase staggered parallel PFC circuit based on coupling inductor and control system - Google Patents
Three-phase staggered parallel PFC circuit based on coupling inductor and control system Download PDFInfo
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- CN214674879U CN214674879U CN202023155701.2U CN202023155701U CN214674879U CN 214674879 U CN214674879 U CN 214674879U CN 202023155701 U CN202023155701 U CN 202023155701U CN 214674879 U CN214674879 U CN 214674879U
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Abstract
The utility model provides a crisscross parallelly connected PFC circuit of three-phase and control system based on coupling inductance, the crisscross parallelly connected PFC circuit of three-phase includes: the three-phase commercial power input end, the three-level PFC conversion circuit and the bus capacitor circuit, wherein the three-level PFC conversion circuit comprises three groups of two-way PFC conversion circuits, each phase input of the three-phase commercial power input end is connected to the one group of two-way PFC conversion circuit, and one end, far away from the three-phase commercial power input section, of each group of PFC conversion circuit is connected to the midpoint of the bus capacitor circuit; each group of PFC conversion circuits comprises a coupling inductor, two switching circuits and two diode circuits, one end of the coupling inductor is connected to the three-phase mains supply input end, and the other end of the coupling inductor is connected with the switching circuits and the diode circuits respectively. The utility model discloses can enough reduce input current ripple and output current ripple, can effectively reduce inductance volume and quantity again, increase power density.
Description
Technical Field
The utility model relates to a PFC converting circuit especially relates to a crisscross parallelly connected PFC circuit of three-phase based on coupling inductance to the control system who includes this crisscross parallelly connected PFC circuit of three-phase based on coupling inductance has been related to.
Background
A Vienna three-phase active power factor correction circuit (PFC for short) adopted by a high-power AC-DC power supply is a relatively mature technology, but with the continuous increase of power requirements, the existing traditional Vienna three-phase PFC circuit has the problems of large inductive current ripple, large volume, large semiconductor current stress, difficulty in heat dissipation and the like.
The existing traditional solutions for increasing output power are: by adopting the mode of parallel connection of devices, the problem of overlarge current stress can be solved, but the problems of overlarge inductor volume, over-concentrated heating, unfavorable heat dissipation, incapability of completely ensuring current balance of parallel tubes and the like still exist; the parallel connection of the independent inductors is adopted, but the problems of increased inductor number, increased cost, increased volume and the like are also brought.
Disclosure of Invention
The utility model aims to solve the technical problem that a need provide one kind can reduce circuit ripple current, can reduce the crisscross parallel PFC circuit of three-phase based on coupling inductance of inductance volume and quantity again, on this basis, still further provided including this crisscross parallel PFC circuit's of three-phase based on coupling inductance control system.
To this, the utility model provides a crisscross parallelly connected PFC circuit of three-phase based on coupling inductance, include: the three-phase commercial power input end, the three-level PFC conversion circuit and the bus capacitor circuit, wherein the three-level PFC conversion circuit comprises three groups of two-way PFC conversion circuits, each phase input of the three-phase commercial power input end is connected to one group of two-way PFC conversion circuit, and one end, far away from the three-phase commercial power input end, of each group of two-way PFC conversion circuit is connected to the midpoint of the bus capacitor circuit; the PFC conversion circuit with the two paths comprises a coupling inductor, two switching circuits and two diode circuits, one end of the coupling inductor is connected to the three-phase commercial power input end, the other end of the coupling inductor is respectively connected with the switching circuits and the diode circuits, and the switching circuits and the diode circuits are respectively connected with the bus capacitor circuit.
The utility model discloses a further improvement lies in, switch circuit includes two way switch, diode circuit includes first diode and second diode, the coupling inductance is kept away from three-phase mains input end's one end respectively with two way switch's one end, the positive pole of first diode and the negative pole of second diode are connected, two way switch's the other end is connected to bus-bar capacitance circuit's mid point, the negative pole of first diode and the positive pole of second diode are connected to respectively bus-bar capacitance circuit's both ends.
The utility model discloses a further improvement lies in, coupling inductance is for winding the inductance on a public magnetic core through two inductance coils.
The utility model discloses a further improvement lies in, two inductance coils's of coupling inductance the winding number of turns is the same, and the inductance value is the same.
The utility model discloses a further improvement lies in, two inductance coils's one side synonym end is connected, and with three-phase mains input end's input alternating current phase line is connected.
The present invention is further improved in that the coupling inductor includes two or more coupling inductors connected in series.
The utility model discloses a further improvement lies in, the coupling inductance includes first coupling inductance L1 and second coupling inductance L2 of series connection, first coupling inductance L1 is the same with second coupling inductance L2 structure, and its coil number ratio is N1: n2; a coil N1 dotted terminal of the first coupling inductor L1 is connected to the three-phase mains input terminal, a coil N1 dotted terminal of the first coupling inductor L1 is connected to a coil N2 dotted terminal of the second coupling inductor L2, and a coil N2 dotted terminal of the second coupling inductor L2 is connected to the switch circuit of the first path and the diode circuit of the first path; a coil N2 synonym terminal of the first coupling inductor L1 is connected to the three-phase mains supply input terminal, a coil N2 synonym terminal of the first coupling inductor L1 is connected to a coil N1 synonym terminal of the second coupling inductor L2, and a coil N1 synonym terminal of the second coupling inductor L2 is connected to the switch circuit of the second path and the diode circuit of the second path.
The utility model discloses a further improvement lies in, the coupling inductance includes first coupling inductance L1 and second coupling inductance L2 of series connection, first coupling inductance L1 is the same with second coupling inductance L2 structure, and its coil number ratio is N1: n2; after the coil N1 of the first coupling inductor L1 is completed, the coil N2 is continuously wound on the magnetic ring of the second coupling inductor L2, and after the coil N1 of the second coupling inductor L2 is completed, the coil N2 is continuously wound on the magnetic ring of the first coupling inductor L1.
The utility model also provides a crisscross parallelly connected PFC circuit control system of three-phase based on coupling inductance, included as above the crisscross parallelly connected PFC circuit of three-phase based on coupling inductance.
Compared with the prior art, the beneficial effects of the utility model reside in that: the coupling inductor is adopted to replace an independent inductor, the structural design and the time sequence control of the circuit are optimized, and each winding of the coupling inductor is respectively connected to the three-level PFC conversion circuits which are connected in parallel in a staggered mode, so that the input current ripple and the output current ripple can be greatly reduced, the volume and the number of the inductor can be effectively reduced, the volume of an input EMC filter is reduced, the EMC interference is reduced, the number of output filter capacitors can be reduced, and the power density is increased; on the basis, the coupling inductor can be further optimized to reduce the height and the volume of the inductor device, improve the power density and reduce the cost.
Drawings
Fig. 1 is a schematic circuit diagram of an embodiment of the present invention;
fig. 2 is a schematic diagram illustrating simulation of the relationship between the inductor current waveform and the input total current according to an embodiment of the present invention;
FIG. 3 is a schematic diagram of the equivalent circuit of the PFC converter circuit in working condition and the waveform of the coupled inductor current;
fig. 4 is a schematic diagram of an optimization circuit according to an embodiment of the present invention;
fig. 5 is a schematic diagram of a re-optimization circuit according to an embodiment of the present invention;
fig. 6 is a schematic top view of an optimized coupling inductor according to an embodiment of the present invention;
fig. 7 is a schematic structural diagram of a coupling inductor according to an embodiment of the present invention after optimization;
fig. 8 is a schematic bottom view of an embodiment of an optimized coupling inductor according to the present invention.
Detailed Description
Preferred embodiments of the present invention will be described in further detail with reference to the accompanying drawings.
As shown in fig. 1, this example provides a three-phase interleaved parallel PFC circuit based on coupled inductors, including: the three-phase commercial power input end 1, the three-level PFC conversion circuit 2 and the bus capacitor circuit 3, wherein the three-level PFC conversion circuit 2 comprises three groups of two-way PFC conversion circuits, each phase input of the three-phase commercial power input end 1 is connected to one group of two-way PFC conversion circuits, and one end, far away from the three-phase commercial power input end 1, of each group of two-way PFC conversion circuits is connected to the midpoint of the bus capacitor circuit 3; the group of two-way PFC conversion circuit comprises a coupling inductor 201, two-way switch circuits 202 and two-way diode circuits 203, one end of the coupling inductor 201 is connected to the three-phase mains supply input end 1, the other end of the coupling inductor 201 is respectively connected with the switch circuits 202 and the diode circuits 203, and the switch circuits 202 and the diode circuits 203 are respectively connected with the bus capacitor circuit 3; the PFC conversion circuit is also called a PFC converter; the single-phase coupling inductor 201 may be one or more.
The three-phase mains supply input end 1 comprises three-phase input of VA, VB and VC, each phase input is connected to two paths of PFC conversion circuits with the same structure, three groups of PFC converters are counted, and the three-level PFC conversion circuit 2 is realized; the bus capacitor circuit 3 refers to a bus circuit where a bus capacitor C01 and a bus capacitor C02 are located; the circuit can reduce the ripple current of the circuit and the volume and the number of inductors; on the basis, the current stress of the power device can be reduced, and the power density is improved; after the structural design and the time sequence control of the circuit are optimized, the three-phase power factor correction circuit can overcome the defects of the existing three-phase power factor correction circuit, effectively reduces the volume and the number of inductors, improves the power density and reduces the cost.
That is, the two PFC converter circuits in each group have the same structure, and each PFC converter circuit includes a switch circuit 202 and a diode circuit 203, where the switch circuit 202 preferably uses a bidirectional switch, such as a switch tube S1 and a switch tube S2 or a switch tube S3 and a switch tube S4, and the diode circuit 203 preferably uses two diodes, such as a diode D1 and a diode D2 or a diode D3 and a diode D4, which are a group of two PFC converter circuits; the other two groups of PFC converter circuits have the same structure as shown in fig. 1.
That is, in this example, the switch circuit 202 includes a bidirectional switch (e.g., a switch tube S1 and a switch tube S2), the diode circuit 203 includes a first diode (e.g., a diode D1) and a second diode (e.g., a diode D2), one end of the coupling inductor 201, which is away from the three-phase mains input terminal 1, is respectively connected to one end of the bidirectional switch (e.g., a switch tube S1 and a switch tube S2), an anode of the first diode (e.g., a diode D1), and a cathode of the second diode (e.g., a diode D2), the other ends of the bidirectional switch (e.g., a switch tube S1 and a switch tube S2) are connected to a midpoint of the bus capacitor circuit 3, and a cathode of the first diode (e.g., a diode D1) and an anode of the second diode (e.g., a diode D2) are respectively connected to two ends of the bus capacitor circuit 3; the other PFC conversion circuits adopt the same mechanism.
Each group of PFC conversion circuits (one group of PFC conversion circuits comprises two paths of PFC conversion circuits) comprises a coupling inductor 201, which is different from a common discrete inductor, the coupling inductor 201 is an inductor formed by winding two inductor coils on a common magnetic core, the two inductor coils reach different coupling coefficients M by adjusting the coil distance and the magnetic core structure of the inductor, and the coupling coefficients M can be adjusted according to actual needs or circuits, and the value range of the coupling coefficients M is 0-1.
Preferably, in this embodiment, the two inductance coils of the coupling inductor 201 have the same winding number and the same inductance; and the different-name ends of one side of the two inductance coils are connected and are connected with an input alternating current phase line of the three-phase commercial power input end 1.
In the embodiment, in a group of two paths of PFC conversion circuits connected to the same phase input, the period start and end times of the switching circuit 202 of the second path are different from the period start and end times of the switching circuit 202 of the first path by half a period. For example, the first group of two-way PFC converter circuits are switched on and off by the two-way switching circuits 202 controlled by the inductor current, wherein the start and end times of the second/second-way switching circuits 202 are advanced or delayed by half the cycle time of the first/first-way switching circuits 202, i.e., the single-phase PFC converter circuits are divided into two-way circuits controlled by 180 degrees in an interlaced manner. The switching circuit 202 in this example is preferably a bi-directional switch.
The control timing difference between the switch circuits 202 of two adjacent groups of PFC conversion circuits in this example is one third of a cycle or 120 ° in phase.
Referring to fig. 1, the specific control timing sequence of the bidirectional switch 202 of the six-path PFC converter circuit is as follows: assuming that the control period of the bidirectional switch 202 is T, at a time T equal to 0, the switching tube S1 and the switching tube S2 in the bidirectional switch (the switching circuit 202) of the first path are controlled to be turned on, and at a time T equal to 1/2T, the switching tube S3 and the switching tube S4 of the bidirectional switch (the switching circuit 202) of the second path are controlled to be turned on; at time T of 1/3T, the switching tube S5 and the switching tube S6 of the bidirectional switch (the switching circuit 202) in the third path are controlled to be turned on; when T is 5/6T, the switching tube S7 and the switching tube S8 of the bidirectional switch (the switching circuit 202) in the fourth path are controlled to be turned on; at time T2/3T, the switching tube S9 and the switching tube S10 of the bidirectional switch (the switching circuit 202) in the fifth path are controlled to be turned on; when T is 7/6T, that is, at the time of the next cycle 1/6T, the switching tube S11 and the switching tube S12 of the bidirectional switch (the switching circuit 202) in the sixth path are controlled to be turned on; the closing time of each two-way switch is controlled by hardware or software according to the working state of the circuit.
In the first set of two-way PFC converter circuits described in this example, the two switching circuits 202 are controlled to be turned on and off by the inductor current, wherein the start and end times of the cycle of the second/second switching circuit 202 are advanced or delayed by half the cycle time of the first switching circuit 202. The waveforms of the inductive current of the two PFC conversion circuits and the total current of the first input are shown in fig. 2, so that the current ripples are offset after the two PFC conversion circuits are connected in parallel in a staggered manner, and the total current ripple is greatly smaller than the single current ripple.
The three-level PFC converter circuit 2 of the present embodiment may be divided into three-phase interleaved 120-degree phase-controlled coupled inductor interleaved PFC circuits, and each phase coupled inductor interleaved PFC circuit may be equivalent to a single-phase coupled inductor PFC circuit in the positive half cycle and the negative half cycle of the input alternating current, as shown in fig. 3. The switching tube S1 and the switching tube S2 are turned on, the pulse phase difference is Ts/2(Ts is the switching period), the on pulse width is equal, and the self-inductance of the coupling inductor 201 is equal (L1 is equal to L2 is equal to L). The PFC conversion circuit has 4 working states in total. The equivalent circuit of half a switching period, two operating modes, and one switching period coupled inductor current waveform are shown in fig. 3.
When the system is in the first working state t 0-t 1: before the time t0, the switching tube S2 is cut off, and the inductor L2 discharges through the diode D2; at time t0, switching tube S1 is turned on, and current i1 rises linearly, so that there is a possibility that current i2 rises due to the coupling effect of the inductor. Analysis shows that whether the current i2 rises or not depends on the magnitude of the coupling coefficient M of the inductor L1 and the inductor L2 and the magnitude of the on-duty D.
When the working state is in a second working state t 1-t 2: switch tube S1 is turned off, switch tube S2 is turned off, switch tube S1 is turned off, current i1 flows through diode D1, current i2 flows through diode D2, and current i1 and current i2 both decrease linearly.
After time t3, the coupling inductor 201 alternates the parallel PFC converter into the next half of the switching cycle, and the two operating modes in this half of the switching cycle are similar to the two operating modes in the first half of the switching cycle, except that the two channels are switched.
Setting the duty cycle to D, the voltage gain can be calculated as:
the coupling inductor 201 is only related to the conduction duty ratio of the output voltage of the interleaved parallel PFC conversion circuit, and is not related to other factors such as the coupling coefficient and the load. Therefore, a control scheme which is reliable and mature before can be adopted on the circuit control, namely:
the above equation shows that the coupling inductance staggers and connects the current ripples of each channel of the PFC converter in parallel, and the ripples are related to the coupling coefficient. The coupling coefficient M can be adjusted according to the actual circuit requirement, so that the control system and the control process of the three-phase interleaved parallel PFC circuit based on the coupling inductor are more flexible, and the adaptability is stronger. Of course, the above description of the timing control and the operation state is to supplement the advantages brought by the circuit design of the present embodiment, and what is claimed in the present application is the hardware structure design, not the control process.
The size of the coupling inductor 201 shown in fig. 1 is reduced compared to the conventional circuit, but the optimized design shown in fig. 4 can be adopted to achieve the objectives of smaller size, thinner thickness and higher power density, for which the coupling inductor 201 in this embodiment includes two or more coupling inductors connected in series. The design can further solve the problems of height, volume, heat dissipation and the like, and one coupling inductor 201 is divided into two or more coupling inductors connected in series, so that the height and the volume are further reduced, and the heat dissipation is optimized. The series-connected coupling inductors 201 can be made of traditional annular magnetic rings, the equivalent coupling coefficient M can be controlled by adjusting the proportion of coils, the height and the size of an inductor device can be reduced, heat is dispersed, and the power density is improved.
In this embodiment, two or more coupling inductors 201 are adopted, and the number of turns of the coupling coils may be different, that is, the coupling inductor 201 includes a first coupling inductor L1 and a second coupling inductor L2 connected in series, the first coupling inductor L1 and the second coupling inductor L2 have the same structure, in fact, the first coupling inductor L1 to the sixth coupling inductor L6 are the same type of inductor, and the coil-to-coil ratio is N1: n2, such a design facilitates manufacturing and fabrication; the connection method comprises the following steps: a coil N1 of the first coupling inductor L1 is connected with an input A-phase voltage in a homonymous mode, a coil N1 of the first coupling inductor L1 is connected with a coil N2 of the second coupling inductor L2 in a different mode, and a coil N2 of the second coupling inductor L2 is connected with a switch tube S1, a diode D1 and a diode D2 in a different mode; a coil N2 of the first coupling inductor L1 is connected with an input A-phase voltage in a different name mode, a coil N2 of the first coupling inductor L1 is connected with a coil N1 of the second coupling inductor L2 in a same name mode, and a coil N1 of the second coupling inductor L2 is connected with a switch tube S2, a diode D3 and a diode D4 in a same name mode.
In other words, in this embodiment, the dotted terminal of the coil N1 of the first coupling inductor L1 is connected to the three-phase mains input terminal 1, the dotted terminal of the coil N1 of the first coupling inductor L1 is connected to the dotted terminal of the coil N2 of the second coupling inductor L2, and the dotted terminal of the coil N2 of the second coupling inductor L2 is connected to the switch circuit 202 of the first path and the diode circuit 203 of the first path; a coil N2 synonym terminal of the first coupling inductor L1 is connected to the three-phase mains input terminal 1, a coil N2 synonym terminal of the first coupling inductor L1 is connected to a coil N1 synonym terminal of the second coupling inductor L2, and a coil N1 synonym terminal of the second coupling inductor L2 is connected to the switch circuit 202 of the second path and the diode circuit 203 of the second path.
Preferably, for a magnetic core with a fixed structure, by adjusting the coil turn ratio N1 of each of the first coupling inductor L1 and the second coupling inductor L2: n2, the coupling coefficient M can be adjusted equivalently, the coupling coefficient M is close to 1 when N1 is equal to N2, the coupling coefficient M is close to 0 when N1 is equal to 0 or N2 is equal to 0, and 0< M <1 by adjusting the coil ratio N1 to N2.
The other two corresponding PFC conversion circuits are connected similarly.
Therefore, the preferred circuit topology using two coupling inductors in this embodiment has the advantage that, in some conventional inductors, such as inductors wound by annular magnetic rings, the magnetic cores of the conventional inductors are circular and cannot change the magnetic circuits, and when the conventional inductors are used for manufacturing the coupling inductors, the coupling coefficients of the conventional inductors cannot be adjusted, so that the parameter performance of the conventional inductors cannot be optimized by adjusting the coupling coefficients. By adopting 2 or more coupled inductors, the inductor can be manufactured by winding a traditional annular magnetic ring, and the ratio of the coupled turns is adjusted to be N1: n2 adjusts the equivalent coupling coefficient. Assuming N1> N2, N1: the larger the proportion of N2, the smaller the equivalent coupling coefficient.
In a specific embodiment, for example, for a toroidal inductor, two separate coupling inductors may be further combined, as shown in fig. 5, the coupling inductor 201 includes a first coupling inductor L1 and a second coupling inductor L2 connected in series, the first coupling inductor L1 and the second coupling inductor L2 have the same structure, and the coil number ratio is N1: n2; after the coil N1 of the first coupling inductor L1 is completed, the coil N2 is continuously wound on the magnetic ring of the second coupling inductor L2, and after the coil N1 of the second coupling inductor L2 is completed, the coil N2 is continuously wound on the magnetic ring of the first coupling inductor L1, so that 4 outgoing pins can be reduced, the size is further reduced, the PCB layout is facilitated, and specific structural drawings are shown in fig. 6 to 8.
The present example also provides a three-phase interleaved parallel PFC circuit control system based on the coupling inductor 201, which includes the three-phase interleaved parallel PFC circuit based on the coupling inductor 201 as described above.
In summary, the coupling inductor 201 is adopted to replace an independent inductor, the structural design and the time sequence control of the circuit are optimized, each winding of the coupling inductor 201 is connected to the three-level PFC conversion circuit 2 in a staggered and parallel connection mode, so that the input current ripple and the output current ripple can be greatly reduced, the volume and the number of inductors can be effectively reduced, the volume of an input EMC filter can be reduced, the EMC interference can be reduced, the number of output filter capacitors can be reduced, and the power density can be increased; on the basis, the coupling inductor 201 can be further optimized to reduce the height and volume of the inductor device, disperse heat and improve power density.
The above-mentioned embodiments are the preferred embodiments of the present invention, and the scope of the present invention is not limited to the above-mentioned embodiments, and the scope of the present invention includes and is not limited to the above-mentioned embodiments, and all equivalent changes made according to the shape and structure of the present invention are within the protection scope of the present invention.
Claims (9)
1. A three-phase interleaved parallel PFC circuit based on a coupled inductor is characterized by comprising: the three-phase commercial power input end, the three-level PFC conversion circuit and the bus capacitor circuit, wherein the three-level PFC conversion circuit comprises three groups of two-way PFC conversion circuits, each phase input of the three-phase commercial power input end is connected to one group of two-way PFC conversion circuit, and one end, far away from the three-phase commercial power input end, of each group of two-way PFC conversion circuit is connected to the midpoint of the bus capacitor circuit; the PFC conversion circuit with the two paths comprises a coupling inductor, two switching circuits and two diode circuits, one end of the coupling inductor is connected to the three-phase commercial power input end, the other end of the coupling inductor is respectively connected with the switching circuits and the diode circuits, and the switching circuits and the diode circuits are respectively connected with the bus capacitor circuit.
2. The three-phase interleaved PFC circuit of claim 1, wherein the switch circuit comprises a bidirectional switch, the diode circuit comprises a first diode and a second diode, one end of the coupling inductor, which is far away from the three-phase mains input end, is connected to one end of the bidirectional switch, an anode of the first diode and a cathode of the second diode, respectively, the other end of the bidirectional switch is connected to a middle point of the bus capacitor circuit, and a cathode of the first diode and an anode of the second diode are connected to two ends of the bus capacitor circuit, respectively.
3. The coupled inductor-based three-phase interleaved PFC circuit of claim 1 or 2 wherein the coupled inductor is an inductor wound around a common core by two inductor coils.
4. The coupled inductor-based three-phase interleaved PFC circuit of claim 3, wherein two inductor coils of the coupled inductor have the same number of winding turns.
5. The coupled-inductor-based three-phase interleaved PFC circuit of claim 3, wherein the two inductor coils are connected to each other at different ends of one side and are connected to an input ac phase line of the three-phase mains input terminal.
6. The coupled inductor-based three-phase interleaved PFC circuit of claim 1 or claim 2, wherein the coupled inductor comprises two or more coupled inductors connected in series.
7. The coupled inductor-based three-phase interleaved parallel PFC circuit of claim 6, wherein the coupled inductor comprises a first coupled inductor L1 and a second coupled inductor L2 connected in series, the first coupled inductor L1 and the second coupled inductor L2 are identical in structure, and the coil turn ratio is N1: n2; a coil N1 dotted terminal of the first coupling inductor L1 is connected to the three-phase mains input terminal, a coil N1 dotted terminal of the first coupling inductor L1 is connected to a coil N2 dotted terminal of the second coupling inductor L2, and a coil N2 dotted terminal of the second coupling inductor L2 is connected to the switch circuit of the first path and the diode circuit of the first path; a coil N2 synonym terminal of the first coupling inductor L1 is connected to the three-phase mains supply input terminal, a coil N2 synonym terminal of the first coupling inductor L1 is connected to a coil N1 synonym terminal of the second coupling inductor L2, and a coil N1 synonym terminal of the second coupling inductor L2 is connected to the switch circuit of the second path and the diode circuit of the second path.
8. The coupled inductor-based three-phase interleaved parallel PFC circuit of claim 6, wherein the coupled inductor comprises a first coupled inductor L1 and a second coupled inductor L2 connected in series, the first coupled inductor L1 and the second coupled inductor L2 are identical in structure, and the coil turn ratio is N1: n2; after the coil N1 of the first coupling inductor L1 is completed, the coil N2 is continuously wound on the magnetic ring of the second coupling inductor L2, and after the coil N1 of the second coupling inductor L2 is completed, the coil N2 is continuously wound on the magnetic ring of the first coupling inductor L1.
9. A three-phase interleaved PFC circuit control system based on a coupled inductor is characterized by comprising the three-phase interleaved PFC circuit based on the coupled inductor, which is disclosed by any one of claims 1 to 8.
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| CN202023155701.2U CN214674879U (en) | 2020-12-24 | 2020-12-24 | Three-phase staggered parallel PFC circuit based on coupling inductor and control system |
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| CN202023155701.2U CN214674879U (en) | 2020-12-24 | 2020-12-24 | Three-phase staggered parallel PFC circuit based on coupling inductor and control system |
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