CN112350598B - Resonance zero current circuit - Google Patents
Resonance zero current circuit Download PDFInfo
- Publication number
- CN112350598B CN112350598B CN202011051625.2A CN202011051625A CN112350598B CN 112350598 B CN112350598 B CN 112350598B CN 202011051625 A CN202011051625 A CN 202011051625A CN 112350598 B CN112350598 B CN 112350598B
- Authority
- CN
- China
- Prior art keywords
- mode
- current
- transformer
- diode
- circuit
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
- 239000003990 capacitor Substances 0.000 claims abstract description 17
- 238000004804 winding Methods 0.000 claims abstract description 12
- 238000001914 filtration Methods 0.000 claims abstract description 8
- 230000007423 decrease Effects 0.000 claims description 4
- 239000007983 Tris buffer Substances 0.000 claims description 3
- 230000000903 blocking effect Effects 0.000 claims description 2
- 238000000034 method Methods 0.000 claims description 2
- 238000007599 discharging Methods 0.000 claims 1
- 238000010586 diagram Methods 0.000 description 11
- 238000005516 engineering process Methods 0.000 description 6
- 238000006243 chemical reaction Methods 0.000 description 2
- 230000000694 effects Effects 0.000 description 2
- 238000012986 modification Methods 0.000 description 2
- 230000004048 modification Effects 0.000 description 2
- 230000009286 beneficial effect Effects 0.000 description 1
- 230000005669 field effect Effects 0.000 description 1
- 230000001939 inductive effect Effects 0.000 description 1
- 238000002955 isolation Methods 0.000 description 1
- 229910044991 metal oxide Inorganic materials 0.000 description 1
- 150000004706 metal oxides Chemical class 0.000 description 1
- 230000000630 rising effect Effects 0.000 description 1
- 239000004065 semiconductor Substances 0.000 description 1
- 239000000758 substrate Substances 0.000 description 1
Images
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/4815—Resonant converters
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The invention discloses a resonant zero-current circuit which comprises a full-bridge inverter, a transformer and an output rectifying and filtering circuit. A resonant inductor is arranged between the primary winding of the transformer and the output end of the full-bridge inverter, and an auxiliary circuit is arranged between the secondary winding and the input end of the output rectifying and filtering circuit; the auxiliary circuit is a circuit formed by connecting two auxiliary switching tubes which are connected in parallel with the secondary winding of the transformer and a resonance capacitor in series. The invention can realize the soft switching function of all the switching tubes including the auxiliary switching tube through the added auxiliary circuit, thereby improving the efficiency of the whole direct current converter.
Description
Technical Field
The invention belongs to the technical field of power electronics, and particularly relates to a resonant zero-current circuit.
Background
There are various types of DC-DC converters, including inductive type converters, capacitive type converters, resonant type converters, transformer type converters, and the like. Electrical isolation and voltage class conversion are easily achieved by using a transformer, and therefore, the development of a DC-DC converter has been the focus. The full-bridge converter is a widely-used transformer-type DC-DC converter, and if a hard switching mode is adopted, the loss of a power switch is large, the heat is serious, and the electromagnetic interference is serious. This requires soft switching to change the switching mode of the device, so that the power switch can achieve improved efficiency and reduced loss in principle. For most medium power applications employing Metal Oxide Semiconductor Field Effect Transistors (MOSFETs), the ZVS technique is attractive because it can reduce switching losses due to the inherent capacitance of the MOSFET. ZVZCS technology has been developed because ZVS technology has had limited effect on reducing the turn-off loss of IGBTs. The ZVZCS full-bridge converter can achieve zero-voltage switching of the leading leg and zero-current switching of the lagging leg by resetting the primary side current during freewheeling, thereby reducing turn-off loss of the lagging leg and improving efficiency. The turn-off loss caused by the current tailing phenomenon of the insulated gate bipolar transistor during zero-voltage turn-off is avoided in both the ZVS (zero voltage switching) technology and the ZVZCS (zero voltage switching) technology, but the ZVZCS technology reduces the turn-off loss of a lagging bridge arm compared with the ZVS technology.
Disclosure of Invention
In order to solve the problems in the prior art, the invention provides a resonant zero-current circuit which can realize zero-current turn-off of an auxiliary circuit in a full-bridge conversion circuit.
The technical problem to be solved by the invention is realized by the following technical scheme:
a resonant zero-current circuit comprises a full-bridge inverter, a transformer and an output rectifying filter circuit,
a resonant inductor is arranged between the primary winding of the transformer and the output end of the full-bridge inverter, and an auxiliary circuit is arranged between the secondary winding and the input end of the output rectifying and filtering circuit;
the auxiliary circuit is a circuit formed by connecting two auxiliary switching tubes which are connected in parallel with the secondary winding of the transformer and a resonance capacitor in series.
Further, the full-bridge inverter comprises a first switch tube Q, a second switch tube Q, a third switch tube Q and a fourth switch tube Q1、Q2、Q3And Q4(ii) a First switch tube Q1And a second switching tube Q2The bridge arms are connected in series in the same direction and are connected with a direct-current power supply in parallel to form a first bridge arm; third switch tube Q3And a fourth switching tube Q4The bridge arms are connected in series in the same direction and are connected with a direct-current power supply in parallel to form a second bridge arm; midpoint and resonant inductance L of first bridge armrConnected with a transformer TrIs connected in series with the transformer T at the midpoint of the second bridge armrIs connected to the primary side of the transformer.
Further, the output rectifying and filtering circuit comprises a first diode D, a second diode D, a third diode D, a fourth diode D and a fourth diode DR1、DR2、DR3And DR4First diode DR1And a second diode DR2The three bridge arms are connected in series in the same direction and are third bridge arms; third diode DR3And a fourth diode DR4The fourth bridge arm, the third bridge arm, the fourth bridge arm and the filter inductor L are connected in series in the same direction0Filter capacitor C connected in parallel after series connection0。
Wherein, the first to fourth switch tubes Q as the main switch tube1、Q2、Q3、Q4And the two auxiliary switching tubes are all Insulated Gate Bipolar Transistors (IGBT).
Further, the filter capacitor C0Connected in parallel across the output load.
The invention has the beneficial effects that: the switching tubes of the first bridge arm and the second bridge arm can simultaneously realize zero current turn-off, so that the efficiency is improved; and the control mode is PWM, stability is good, and is fast, can work under the high frequency condition, and soft switching scope is relatively great, makes control relatively easy.
Drawings
FIG. 1 is a schematic structural view of the present invention;
FIG. 2 is a waveform diagram illustrating the principal operation of the circuit of the present invention;
FIG. 3 is a current path diagram of the full-bridge inverter circuit according to the present invention operating in mode one;
FIG. 4 is a current path diagram of the full-bridge inverter circuit according to the present invention operating in mode two;
FIG. 5 is a current path diagram of the full bridge inverter according to the present invention operating in mode three;
FIG. 6 is a current path diagram of the full-bridge inverter circuit according to the present invention operating in mode four;
FIG. 7 is a current path diagram of the full-bridge inverter circuit according to the present invention operating in mode five;
FIG. 8 is a current path diagram of the full bridge inverter circuit according to the present invention operating in mode six;
FIG. 9 is a current path diagram of the full-bridge inverter circuit according to the present invention operating in mode seven;
FIG. 10 is a current path diagram of the full-bridge inverter circuit according to the present invention operating in mode eight;
FIG. 11 is a current path diagram of the full-bridge inverter circuit according to the present invention operating in the ninth mode;
fig. 12 is a current path diagram of the full-bridge inverter circuit operating in the mode ten according to the present invention.
Detailed Description
To further describe the technical features and effects of the present invention, the present invention will be further described with reference to the accompanying drawings and detailed description.
The zero-current full-bridge inverter circuit with an auxiliary circuit is shown in figure 1, and an auxiliary switching tube Q is connected in series to a secondary side of the circuit on the basis of a traditional full-bridge inverter5、Q6And an auxiliary circuit composed of a resonance capacitor. The voltage value of the secondary side resonance capacitor is reasonably controlled, so that the voltage on the resonance inductor can be reversed, the current flowing through the switching tube at the turn-off moment of the switching tube flows through the parallel diode of the IGBT, and the zero current turn-off of the switching tube is realized.
The technical scheme adopted by the invention is as follows:
a resonant zero current circuit comprising:
the system comprises a full-bridge inverter, a transformer and an output rectifying and filtering circuit;
output end of full-bridge inverter and primary side of transformerA resonance inductor L is connected in series between the windingsrAn auxiliary circuit is arranged between the secondary winding of the transformer and the input end of the output rectifying filter circuit;
the auxiliary circuit comprises a resonance capacitor Cr connected in parallel with the secondary winding of the transformer, and two auxiliary switching tubes (a fifth switching tube and a sixth switching tube) Q are connected in series at two ends of the resonance capacitor in an anti-phase manner5、Q6；
Wherein, the full-bridge inverter comprises a first switch tube Q to a fourth switch tube Q1、Q2、Q3And Q4(ii) a First switch tube Q1And a second switching tube Q2The bridge arms are connected in series in the same direction and are connected with a direct-current power supply in parallel to form a first bridge arm; third switch tube Q3And a fourth switching tube Q4The bridge arms are connected in series in the same direction and are connected with a direct-current power supply in parallel to form a second bridge arm; midpoint of first bridge arm and resonant inductor LrConnected with a transformer TrIs connected in series with the transformer T at the midpoint of the second bridge armrIs connected to the primary side of the transformer.
The output rectifying and filtering circuit comprises a first diode D, a second diode D, a third diode D, a fourth diode D and a fourth diode DR1、DR2、DR3And DR4First diode DR1And a second diode DR2The third bridge arm is connected in series in the same direction; third diode DR3And a fourth diode DR4The filter inductor L is connected in series in the same direction and is a fourth bridge arm, a third bridge arm and a fourth bridge arm0(the inductance is large enough to be regarded as a constant current source) and then is connected in parallel with the filter capacitor C0The filter capacitor C0The output voltage is smoothed by connecting in parallel at both ends of the output load, and the load voltage fluctuates all the time.
Wherein, the first to the sixth switch tubes all adopt IGBT.
The following analysis is performed by switching between specific working modes
Modal-mode operation is illustrated in FIG. 3, corresponding to t in FIG. 20-t1And (5) stage. In this mode, at t0Time out Q1、Q4A turn-on signal when the voltage between AB is equal to the input voltage vAB＝VinPrimary voltage v of transformerpDue to DR1、DR2、DR3、DR4Is clamped to 0, primary side main current ipAnd linearly increasing from zero to realize zero current switching-on. With i beingpIncrease of (a) iDR1＝iDR4Current i rising and flowing through the diodeDR2＝iDR3And (4) descending. Until t1，ipIs raised to Io/N，iDR2＝iDR3And decreases to zero.
The mode two operation is shown in FIG. 4, corresponding to t in FIG. 21-t2And (5) stage. In this mode, LrAnd CrResonance, CrVoltage v acrossCrIncreasing from 0, vp＝Nvcr. At t2At the moment, flow through CrCurrent i ofcr(t2)＝0，vcr(t2)＝2Vin/N，icrThe current will be reversed and blocked.
The three-mode operation is shown in FIG. 5, which corresponds to t in FIG. 22-t3And (5) a stage. In this mode, Q5Has not been turned off, but is due to CrThe branch is blocked, the charge is accumulated on the capacitor Cr and cannot be discharged, vCrMaintained at 2VinV, and NpDue to CrThe blocking of the branch is again equal to the input voltage VinThe circuit enters a stable operating mode.
Modal four operating modes are shown in FIG. 6, corresponding to t in FIG. 23—t4And (5) stage. In this mode, t3Constantly sends off a turn-off Q5The fourth mode is a stable working mode, and compared with the third mode, the Q is divided5There is no difference outside the shut-down, in this mode, VinBy DR1，DR4And outputting power to the output side.
Modal five mode of operation is shown in FIG. 7, corresponding to t in FIG. 24—t5And (5) stage. In this mode, t4Time of day trigger Q6The conducting signal has a circuit equation in the second mode completely consistent with that in the second mode, so that the conducting signal can be regarded as the continuation of the resonance state of the second mode, vpAgain with NvcrAre equal. Modal five-hand machineGo on to ipWhen it falls to 0, icr(t5)＝IoWhen this is the case, modality five ends.
Modal six operating modes are shown in FIG. 8, corresponding to t in FIG. 25—t6And (5) stage. In this mode, ipIncrease in the reverse direction, i.e. iCrTo the output side and the input side simultaneously. CrThe discharge is continued. v. ofpIs still greater than vAB. At t6Time-out turn-off Q1、Q4Of the signal of (a). Because the current flows through the anti-parallel diode, the current flowing through the IGBT is zero at the moment, and therefore the current is the switch Q1、Q4The zero current of (c) is turned off.
The seven mode of operation is shown in FIG. 9, corresponding to t in FIG. 26—t7And (5) stage. In this mode, Q is divided compared with mode six1、Q4There is no other difference than off. At t7Time vpIs equal to vAB。
Modal eight operating modes are shown in FIG. 10, corresponding to t in FIG. 27—t8And (5) stage. In this mode, vpLess than vAB，LrVoltage v acrossLrFrom negative to positive, meaning ipThe reverse increasing trend of (1) ends, the reverse ipThe current begins to decrease. CrThe discharge continues sinusoidally. At t8Time reversal current ipReducing to zero.
The nine-mode operation is shown in FIG. 11, which corresponds to t in FIG. 28—t9And (5) stage. In this mode, Q is due to1、Q4Has been turned off, ipThe primary side enters an open circuit state after the current reaches zero, and Cr outputs a constant current Io，vCrAnd thus is transformed from a trigonometric drop to a linear drop. At t9Time vCr0, capacitance CrReleasing all of the stored energy.
Modal ten operating modes are shown in FIG. 12, corresponding to t in FIG. 29—t10And (5) stage. In this mode, a current flows through DR1、DR2、DR3、DR4Four diodes are arranged on the upper surface of the substrate,DR1、DR2branch and DR3、DR4The branch divides the current equally, soDR1＝iDR4Down to half mode nine. This mode is the last phase of a half duty cycle, and the beginning of the next half duty cycle marks the end of mode ten.
The above description is only a preferred embodiment of the present invention, and it should be noted that, for those skilled in the art, several modifications and variations can be made without departing from the technical principle of the present invention, and these modifications and variations should also be regarded as the protection scope of the present invention.
Claims (4)
1. The utility model provides a resonance zero current circuit, includes full-bridge inverter, transformer and output rectification filter circuit, its characterized in that:
a resonant inductor is connected in series between the output end of the full-bridge inverter and the primary winding of the transformer, and an auxiliary circuit is arranged between the secondary winding of the transformer and the input end of the output rectifying and filtering circuit;
the auxiliary circuit comprises a resonance capacitor Cr connected in parallel with the secondary winding of the transformer, and two auxiliary switch tubes Q are connected in series at two ends of the resonance capacitor Cr5、Q6；
The full-bridge inverter comprises a first switch tube Q, a second switch tube Q, a third switch tube Q and a fourth switch tube Q1、Q2、Q3And Q4(ii) a First switch tube Q1And a second switching tube Q2The bridge arms are connected in series in the same direction and are connected with a direct-current power supply in parallel to form a first bridge arm; third switch tube Q3And a fourth switching tube Q4The bridge arms are connected in series in the same direction and are connected with a direct-current power supply in parallel to form a second bridge arm; midpoint and resonant inductance L of first bridge armrConnected with a transformer TrIs connected in series with the transformer T at the midpoint of the second bridge armrThe primary side of the primary side is connected;
the output rectifying and filtering circuit comprises a first diode D, a second diode D, a third diode D, a fourth diode D and a fourth diode DR1、DR2、DR3And DR4First diode DR1And a second diode DR2The third bridge arm is connected in series in the same direction; third diode DR3And a fourth diode DR4The filter inductor L is connected in series in the same direction and is a fourth bridge arm, a third bridge arm and a fourth bridge arm0Filter capacitor C connected in parallel after series connection0；
In the mode one, t0-t1Segment at t0Time out Q1、Q4Conduction signal, voltage v between nodes ABABIs equal to the input voltage VinPrimary voltage v of transformerpDue to DR1、DR2、DR3、DR4Is clamped to 0, primary side main current ipLinearly increasing from zero to realize zero current switching-on; in the mode two, t1-t2Segment, resonant inductance LrAnd a resonance capacitor CrResonance, CrVoltage v acrossCrIncreasing from 0 at t2At the moment, flow through CrCurrent i ofcr(t2)＝0，vcr(t2)＝2Vin/N，icrThe current is about to reverse and is blocked; in mode III, t2-t3Segment, Q5Has not been turned off due to the resonant capacitance CrBranch is blocked, vCrMaintained at 2VinV, and NpDue to CrThe blocking of the branch is again equal to the input voltage VinThe circuit enters a stable working mode; mode four, t3—t4Segment at t3Constantly sends off a turn-off Q5The fourth mode is a stable working mode; in mode five t4—t5At t4Time of day trigger Q6Signal of conduction, vpAgain with NvcrEquality, modality five persists to ipWhen it falls to 0, icr(t5)＝IoThen the process is finished; in mode six, t5—t6Segment ipIncrease in the reverse direction, CrContinue discharging at t6Time-out turn-off Q1、Q4The signal of (a); in the mode seven, t6—t7Segment, hold Q1、Q4Closing; in the mode eight, t7—t8Primary voltage v of segment, transformerpIs less than vABResonant inductance LrVoltage v acrossLrFrom negative to positive and vice versaTo ipThe current begins to decrease and the resonant capacitance CrStill continues to discharge in a sinusoidal manner at t8Time reversal current ipReduced to zero; in the mode nine, t8—t9Segment ipThe primary side enters an open circuit state after the zero, and the resonant capacitor Cr outputs a constant current Io，vCrLinearly decreases at t9Time vCr0, resonant capacitance CrReleasing all stored energy; in the mode ten, t9—t10Segment, current flows through DR1、DR2、DR3、DR4Four diodes, DR1、DR2Branch and DR3、DR4The branches divide the current equally.
2. A resonant zero current circuit according to claim 1, wherein the auxiliary switching tube is an IGBT.
3. A resonant zero current circuit according to claim 1, wherein: the first to fourth switching tubes adopt IGBTs.
4. A resonant zero current circuit according to claim 1, wherein: the filter capacitor C0Connected in parallel across the output load.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202011051625.2A CN112350598B (en) | 2020-09-29 | 2020-09-29 | Resonance zero current circuit |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202011051625.2A CN112350598B (en) | 2020-09-29 | 2020-09-29 | Resonance zero current circuit |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN112350598A CN112350598A (en) | 2021-02-09 |
| CN112350598B true CN112350598B (en) | 2022-07-01 |
Family
ID=74361286
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN202011051625.2A Active CN112350598B (en) | 2020-09-29 | 2020-09-29 | Resonance zero current circuit |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN112350598B (en) |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103929064A (en) * | 2014-03-24 | 2014-07-16 | 江苏固德威电源科技有限公司 | Isolated two-way DC/DC converter and control method thereof |
| CN204696920U (en) * | 2015-06-12 | 2015-10-07 | 中山大学 | A kind of full-bridge DC-DC converter of Zero Current Switch |
| CN206117517U (en) * | 2016-10-18 | 2017-04-19 | 北京交通大学 | Do you be suitable for high -pressure high -power auxiliary converter 's preceding stage high frequency DC DC converter |
| US10020752B1 (en) * | 2017-09-26 | 2018-07-10 | Vlt, Inc. | Adaptive control of resonant power converters |
-
2020
- 2020-09-29 CN CN202011051625.2A patent/CN112350598B/en active Active
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103929064A (en) * | 2014-03-24 | 2014-07-16 | 江苏固德威电源科技有限公司 | Isolated two-way DC/DC converter and control method thereof |
| CN204696920U (en) * | 2015-06-12 | 2015-10-07 | 中山大学 | A kind of full-bridge DC-DC converter of Zero Current Switch |
| CN206117517U (en) * | 2016-10-18 | 2017-04-19 | 北京交通大学 | Do you be suitable for high -pressure high -power auxiliary converter 's preceding stage high frequency DC DC converter |
| US10020752B1 (en) * | 2017-09-26 | 2018-07-10 | Vlt, Inc. | Adaptive control of resonant power converters |
Also Published As
| Publication number | Publication date |
|---|---|
| CN112350598A (en) | 2021-02-09 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| WO2021103415A1 (en) | High-gain quasi-resonance dc-dc converter based on voltage doubling rectifier circuit | |
| Feng et al. | A novel zero-voltage and zero-current-switching full-bridge PWM converter | |
| US20200287461A1 (en) | Dc-dc converter | |
| CN111478611B (en) | Auxiliary resonance converter pole inverter capable of realizing bidirectional reset of phase-correlated magnetizing current | |
| WO2008020629A1 (en) | Insulation boost type push-pull soft-switching dc/dc converter | |
| CN110190752B (en) | Bidirectional CLLLC-DCX resonant converter and control method thereof | |
| CN111934567B (en) | Bridgeless double-Boost power factor correction rectifier for left-right alternate auxiliary commutation | |
| CN103904901A (en) | Phase-shift full-bridge converter circuit and control method | |
| CN201490890U (en) | Converter capable of working in phase-shift resonance and PWM modes | |
| Shi et al. | High power ZVZCS phase shift full bridge DC–DC converter with high current reset ability and no extra electrical stress | |
| CN110504835A (en) | A kind of switch converters and its control method | |
| CN114285286A (en) | Single-stage zero-current switch full-bridge boost direct current converter and control method thereof | |
| CN110224605B (en) | Full-bridge conversion circuit | |
| Chen et al. | Analysis and design of LLC converter based on SiC MOSFET | |
| CN112202351A (en) | Single-stage isolated three-phase AC/DC rectifier of wide-range soft switch | |
| CN112350598B (en) | Resonance zero current circuit | |
| CN111384858A (en) | Full-bridge circuit and full-bridge converter | |
| CN114301292A (en) | Soft switching type bidirectional BUCK-BOOST converter | |
| CN110112921B (en) | Zero-current soft-switching PWM full-bridge converter | |
| CN112953288A (en) | Modulation method for resonant direct-current link soft switching inverter | |
| WO2018210285A1 (en) | T-type converter circuit and corresponding three-phase converter circuit | |
| WO2018210301A1 (en) | T-type converter circuit and corresponding three-phase converter circuit | |
| Nayanasiri et al. | Soft-switching single inductor current-fed push-pull converter for PV applications | |
| CN112910260B (en) | Control method of DC-DC conversion device and switching power supply | |
| CN217643168U (en) | High-efficient resonance phase shift conversion circuit structure |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |