CN111900944A - Composite parallel connection type audio digital power amplifier without dead zone distortion - Google Patents
Composite parallel connection type audio digital power amplifier without dead zone distortion Download PDFInfo
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- CN111900944A CN111900944A CN202010728568.0A CN202010728568A CN111900944A CN 111900944 A CN111900944 A CN 111900944A CN 202010728568 A CN202010728568 A CN 202010728568A CN 111900944 A CN111900944 A CN 111900944A
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
- H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
- H03F3/21—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only
- H03F3/217—Class D power amplifiers; Switching amplifiers
- H03F3/2178—Class D power amplifiers; Switching amplifiers using more than one switch or switching amplifier in parallel or in series
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
- H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
- H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
- H03F1/0211—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers with control of the supply voltage or current
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Abstract
The invention belongs to the technical field of audio power amplification, and discloses a composite parallel audio digital power amplifier without dead zone distortion, which comprises a voltage control module, an LC circuit, a load element RL and a current supplement module, wherein the input end of the voltage control module is connected with a signal input end VIN, the output end of the voltage control module is connected with one end of an inductor L1 of the LC circuit, the voltage control module and the current control module are respectively connected with the LC circuit, the LC circuit works in a high-frequency band, the input end of the current supplement module is connected with the output current sampling of the voltage control module, the output end of the current supplement module is connected with the output end of the voltage control module through an inductor L2, the current supplement module is used for tracking the output current of the power amplifier and providing the current output of the power amplifier, so that the output current of the voltage. The invention can improve the switching frequency of the digital power amplifier by multiple times, correspondingly improve the response speed of output, eliminate the influence of the dead zone of the voltage control module and improve the tone quality.
Description
Technical Field
The invention relates to the technical field of audio power amplifiers, in particular to a composite parallel audio digital power amplifier without dead zone distortion.
Background
The current class D digital power amplifier is formed by a half-bridge MOS or a full-bridge MOS plus a control circuit, and the defects and difficulties of the traditional structure and the control mode have the following aspects:
in order to improve the sound quality, the higher the switching frequency of the circuit is, the better the switching frequency is, but the higher the frequency is, the larger the loss of the circuit is, generally, the circuit is taken to be between 400K and 1000K, and in fact, if the switching frequency is improved to a higher frequency, the better sound quality is obtained, but the power consumption of the circuit is also greatly increased, so that in practice, the existing product needs to make a balance between the power consumption and the sound quality.
Secondly, when the class D digital power amplifier outputs a small current, the output characteristic is a very small low-resistance characteristic, which is very good for tone quality, and the soft switching operation of the MOS tube can be realized, and the switching frequency operation has very low loss when reaching a very high frequency. However, once the current is greater than a certain value, the circuit characteristic changes suddenly, the dead zone of the MOS drive causes the output characteristic to become nonlinear high resistance, which seriously affects the tone quality, and meanwhile, the soft switching state of the MOS transistor becomes hard switching, the switching loss increases by one order of magnitude, which hinders the frequency improvement.
When the ordinary digital switching power supply circuit outputs a small current, the MOS switching tube current works in a positive and negative two-way mode, at the moment, the MOS switching tube works in a soft switch mode, the switching loss is very small, and the MOS switching tube can work at a very high frequency. However, once the output current exceeds one point, the current becomes unidirectional, the MOS operating state becomes hard switching, and the MOS parasitic diode characteristic greatly increases the loss, at which time the switching loss becomes several tens of times. In order to improve the sound quality, the higher the circuit switching frequency is, the better, but the switching loss is limited, and currently, the switching frequency is generally set to be about 400K to 1000K, and then, the problem of excessive heat generation exists.
Conventional digital power supplies operate with a need to cross over between soft and hard switching states. Soft switching output voltage = VCC (TON + dead time)/T, where dead time is always present, so the output varies linearly with the variation of TON. Although the output voltage = VCC (TON)/T is linearly changed in the hard switching, the transmission characteristics are not consistent when the soft switching and the hard switching are switched, and the dead time ratio is relatively large in the high frequency, so that a large voltage jump occurs in the hard switching, which is equivalent to cross distortion, and the sound quality is greatly influenced.
Disclosure of Invention
In order to solve the technical problems in the prior art, the invention provides a composite parallel audio digital power amplifier without dead zone distortion, which can increase the switching frequency of a digital power amplifier by multiple times, correspondingly increase the response speed of output, simultaneously eliminate dead zone distortion and improve the tone quality, and the specific technical scheme is as follows:
a composite parallel audio digital power amplifier without dead zone distortion comprises a voltage control module, an LC circuit, a load element RL and a current supplement module, wherein the input end of the voltage control module is connected with a signal input end VIN, the output end of the voltage control module is connected with one end of an inductor L1 of the LC circuit, the voltage control module works in a high frequency band and provides voltage control capability and dynamic control requirements, the LC circuit is respectively connected with the voltage control module through voltage sampling and current sampling, the current sampling of the input end of the current supplement module is connected with the output end of the voltage control module, the output end of the current supplement module is connected with the output end of the voltage control module through an inductor L2 and used for tracking the output current of the power amplifier and providing the current output of the power amplifier, so that the output current of the voltage control module fluctuates around 0, and the load.
Further, the current at the input end of the current supplement module is sampled to measure the current at the output end of the voltage control module as the feedback value of the current detection feedback signal or to measure the currents of the inductor L1 and the inductor L2, and the difference value of the two is used as the feedback value of the current detection feedback signal.
Further, the voltage control module uses a voltage outer loop circuit, a current self-excited inner loop circuit, a first driving unit and a first switch unit, a feedback unit voltage sample of the voltage outer loop circuit is connected with the other end of the inductor L1, the output end of the feedback unit voltage sample is connected with the current self-excited inner loop circuit, the current self-excited inner loop circuit current sample is connected with a filter capacitor C2 of the LC circuit, the current from the filter capacitor C2 is fed back to form self-excited oscillation to generate a PWM driving signal, and the first switch unit is driven by the first driving unit.
Further, the feedback unit includes an operational amplifier U1, a resistor R1, and a resistor R2, the signal input terminal VIN is connected to the negative terminal of the operational amplifier U1 through the resistor R1, the negative terminal of the operational amplifier U1 is connected to one end of an inductor L1 through a resistor R2, and the positive terminal of the operational amplifier U1 is grounded.
Further, the current of the filter capacitor C2 is a combination of the current of the inductor L1 and the current of the load element RL.
Furthermore, the current supplement module comprises a current module control and PWM generating circuit, a second driving unit and a second switching unit, wherein the current module control and PWM generating circuit generates a driving signal according to the sampling current and drives the second switching unit through the second driving unit.
Furthermore, the current module control and PWM generating circuit generates the driving signal by adopting a current feedback closed loop self-excited oscillation generation driving signal or a triangular wave signal comparison mode.
Furthermore, the composite parallel audio digital power amplifier without dead zone distortion comprises a double-frequency mode and a single-frequency mode, wherein the double-frequency mode is that the working frequency of the current supplement module is different from the working frequency of the voltage control module, and the single-frequency mode is that the working frequency of the current supplement module and the working frequency of the voltage control module are synchronous at the same frequency.
Further, in the dual-frequency mode, the current module control and PWM generation circuit includes an RC filter circuit, a hysteresis oscillation comparison circuit, and a dual-edge trigger, the output current of the voltage control module is filtered by the RC filter circuit and then connected to the input end of the hysteresis oscillation comparison circuit, the output end of the hysteresis oscillation comparison circuit is connected to the dual-edge trigger, and the CLK end of the dual-edge trigger is connected to the PWM driving signal of the voltage control module;
and in a single-frequency mode, the current module control and PWM generating circuit comprises an RC filter circuit, a delay circuit and a hysteresis comparison circuit, the output current of the voltage control module is connected to one end of a comparator of the hysteresis comparison circuit after being filtered by the RC filter circuit, the PWM driving signal of the voltage control module is connected to the other end of the comparator after being delayed by the delay circuit, and the output of the comparator is used as the output of the current module control and PWM generating circuit.
The invention provides main current for the output of the power amplifier through the current supplement module, the average current output by the voltage module approaches to about zero, only AC ripple waves of an output inductor are provided, the conduction loss is greatly reduced, a much smaller device can be used, even a gallium nitride or silicon carbide high-performance device is used, the cost ratio is not improved, namely the high performance is achieved with low cost, more importantly, the working state of the voltage control module is greatly optimized, the voltage control module completely works in a soft switching state, the influence of a parasitic diode does not exist, the switching loss approaches to zero, so that the voltage control module can work at much higher frequency, the theoretical performance can be improved by ten times, meanwhile, the influence of a switching dead zone which seriously influences the tone quality all the time does not exist, and the voltage control module can work in an optimal state.
This current supplement module can connect in parallel to any digital power amplifier circuit that exists at present, because the current injection point is voltage control module's switch tube node, this node work wave form is the PWM wave of on-off state, the impedance only is switch tube on-resistance, this impedance is minimum generally, so the current of injecting into can not change PWM ripples characteristic and range basically, so can not influence voltage control module's operating characteristic yet, this is that current supplement module can cooperate the reason of any form of voltage control module, this circuit voltage control module work is in soft on-off state, transmission characteristic is linear and low resistance, this has very big benefit to improving tone quality.
Drawings
FIG. 1 is a schematic diagram of the circuit of the present invention;
FIG. 2 is a schematic diagram of a dual-band circuit of the present invention;
FIG. 3 is a schematic diagram of a single frequency circuit of the present invention;
FIG. 4 is a waveform schematic of a dual frequency circuit of the present invention;
FIG. 5 is a waveform schematic of a single frequency circuit of the present invention;
in the figure: 1-a voltage control module; 2-a current supplement module; a 3-LC circuit; 4-a first drive unit; 5-a first switching unit; 6-current module control and PWM generating circuit; 7-a second drive unit; 8-second switching unit.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more clearly apparent, the technical solutions of the present invention are further described in detail below with reference to the accompanying drawings.
As shown in fig. 1-3, the composite parallel audio digital power amplifier without dead zone distortion of the present invention comprises a voltage control module 1, an LC circuit 3, a load element RL and a current supplement module 2, wherein an input end of the voltage control module 1 is connected to a signal input end VIN, an output end is connected to one end of an inductor L1 of the LC circuit 3, the LC circuit 3 operates in a high frequency band and provides voltage control capability and dynamic control requirements, the LC circuit 3 is connected to the voltage control module 1 through voltage sampling and current sampling, respectively, an input end of the current supplement module 2 is connected to an output end of the voltage control module 1, and an output end is connected to an output end of the voltage control module 1 through an inductor L2, and is configured to track an output current of the power amplifier and provide a current output of the power amplifier, so that the output current of the voltage control module 1 fluctuates around 0 without excessive power consumption, therefore, the voltage control module 1 can work at a higher working frequency, and the quality of the audio frequency is ensured; the load element RL is arranged at the output of the LC circuit 3.
The current of the input end of the current supplement module 2 is sampled to measure the current of the output end of the voltage control module 1 as the feedback value of the current detection feedback signal or to measure the currents of the inductor L1 and the inductor L2, and the difference value of the two is used as the feedback value of the current detection feedback signal.
The voltage control module 1 uses a voltage outer loop circuit, a current self-excited inner loop circuit, a first driving unit 4 and a first switch unit 5, a feedback unit voltage sample of the voltage outer loop circuit is connected with the other end of an inductor L1, the output end of the voltage outer loop circuit is connected with the current self-excited inner loop circuit, the current sample of the current self-excited inner loop circuit is connected with a filter capacitor C2 of an LC circuit 3, the current fed back from the filter capacitor C2 forms self-excited oscillation to generate a PWM driving signal, and the first switch unit 5 is driven by the first driving unit 4.
The feedback unit comprises an operational amplifier U1, a resistor R1 and a resistor R2, wherein a signal input end VIN is connected with the negative end of the operational amplifier U1 through the resistor R1, the negative end of the operational amplifier U1 is connected with one end of an inductor L1 through a resistor R2, and the positive end of the operational amplifier U1 is grounded.
The current of the filter capacitor C2 is a combination of the current of the inductor L1 and the current of the load element RL.
The current supplementing module 2 comprises a current module control and PWM generating circuit 6, a second driving unit 7 and a second switching unit 8, wherein the current module control and PWM generating circuit 6 generates a driving signal according to the sampling current and drives the second switching unit 8 through the second driving unit 7.
The current module control and PWM generating circuit 6 generates a driving signal by adopting a current feedback closed loop self-excited oscillation generation driving signal or a triangular wave signal comparison mode, and aims to enable the voltage control module to enter a soft switch and working state without dead zone distortion.
The composite parallel connection type no-dead-zone distortion audio digital power amplifier comprises a double-frequency mode and a single-frequency mode, wherein the double-frequency mode is that the working frequency of the current supplement module 2 is inconsistent with the working frequency of the voltage control module 1, and the single-frequency mode is that the working frequency of the current supplement module 2 and the working frequency of the voltage control module 1 are synchronous at the same frequency.
In a dual-frequency mode, the current module control and PWM generating circuit 6 comprises an RC filter circuit, a hysteresis oscillation comparison circuit and a dual-edge trigger, the output current of the voltage control module (1) is filtered by the RC filter circuit and then is connected to the input end of the hysteresis oscillation comparison circuit, the output end of the hysteresis oscillation comparison circuit is connected to the dual-edge trigger, and the CLK end of the dual-edge trigger is connected to the PWM driving signal of the voltage control module 1;
during the single-frequency mode, the current module control and PWM generation circuit 6 includes an RC filter circuit, a delay circuit and a hysteresis oscillation comparison circuit, the output current of the voltage control module 1 is filtered by the RC filter circuit and then is connected to one end of a comparator of the hysteresis oscillation comparison circuit, the PWM driving signal of the voltage control module 1 is delayed by the delay circuit and then is connected to the other end of the comparator, and the output of the comparator is used as the output of the current module control and PWM generation circuit 6. The principle is that the delay quantity of the upper edge and the lower edge of a PWM signal is respectively adjusted in a micro-scale mode through a current filtering value, so that a current supplementing module can track current.
And (3) double-frequency mode: the voltage control module 1 operates at a very high frequency, such as 1000KHz, and the current supplement module 2 may operate at 200 KHz. The switching losses of the current compensation module 2 are reduced at this time because of the low frequency. The voltage control module 1 has no switching loss because of being in a soft switching state, and simultaneously, the influence of a dead zone on distortion is eliminated, the inductance requirement of the inductor L2 is larger in the mode, but the frequency is low, and a powder core material can be used. The pulse signals of the current supplement module 2 are synchronized by the PWM rising or falling edge of the voltage module, and the influence of the switching of the power level on the interference of weak signals is avoided.
Single frequency mode: the voltage control module 1 and the current supplement module 2 are synchronous at the same frequency, the influence of dead zones on the distortion rate is eliminated, the switching loss of the current supplement module 2 is not reduced, the switching of the current supplement module 2 is obtained by the small delay of PWM of the voltage control module 1, the interference on signal processing is avoided, and the mode only needs small inductance L2 inductance and has small fluctuation.
As shown in fig. 4, taking an example that a power amplifier inputs a 10K sinusoidal signal, the signal is a 10KHz positive ripple, I (L1) is a current waveform of an output inductor L1, I (L2) is a current waveform of an output inductor L2 of the current supplement module 2, and I (L2) is within an envelope range of I (L1). I (L1) -I (L2) are the MOS circuit output currents of the voltage control module 1, and each ripple crosses the 0 point, i.e. the MOS switch of the voltage control module 1 is not affected by the dead zone and is in a soft switching state, and this current value is also much smaller than the circuit output current.
As shown in fig. 5, taking the 20KHz sine signal input by the power amplifier as an example, I (L1) is the current waveform of the output inductor L1, I (L2) is the current waveform of the output inductor L2 of the current supplement module 2, and it can be seen that I (L2) is within the envelope range of I (L1). I (L1) -I (L2) are the output currents of the MOS circuits of the voltage control module 1, and each ripple crosses the 0 point, that is, the MOS switches of the voltage control module 1 are not affected by the dead zone and are in a soft switching state, so that the distortion problem caused by the dead zone is solved, and the loss of the voltage control module 1 is very small. The difference between double frequency and single frequency is that the operating frequencies of the current supplementing modules 2 are different.
Although the current of the current supplement module is still the same as the current of the main output, the frequency is greatly reduced, the switching loss is very low, and in order to see the waveform clearly, the frequency difference is not increased in fig. 4 and 5, and the frequency of the actual voltage control module can be greatly increased.
Claims (9)
1. The composite parallel audio digital power amplifier without dead zone distortion comprises a voltage control module (1), an LC circuit (3) and a load element RL, and is characterized by further comprising a current supplement module (2), wherein the input end of the voltage control module (1) is connected with a signal input end VIN, the output end of the voltage control module (1) is connected with one end of an inductor L1 of the LC circuit (3), the current supplement module works in a high frequency band and provides voltage control capability and dynamic control requirements, the LC circuit (3) is respectively connected with the voltage control module (1) through voltage sampling and current sampling, the input end of the current supplement module (2) is connected with the output end of the voltage control module (1) through an inductor L2, the output end of the current supplement module is used for tracking the output current of the power amplifier and providing the current output of the power amplifier, so that the output current of the voltage control module (1) fluctuates around 0, the load element RL is arranged at the output of the LC circuit (3).
2. The composite parallel connection type no-dead-time distortion audio digital power amplifier according to claim 1, characterized in that the input current of the current supplement module (2) is sampled by measuring the current of the output of the voltage control module (1) as the feedback value of the current detection feedback signal or measuring the current of the inductor L1 and the inductor L2, and the difference of the two is used as the feedback value of the current detection feedback signal.
3. The composite parallel type no dead zone distortion audio digital power amplifier according to claim 1, wherein the voltage control module (1) uses a voltage outer loop circuit whose feedback unit voltage sample is connected to the other end of an inductor L1 and whose output end is connected to a current self-excited inner loop circuit whose current sample is connected to a filter capacitor C2 of an LC circuit (3), a first driving unit (4) and a first switching unit (5), feeds back a current from the filter capacitor C2 to form a self-excited oscillation generating PWM driving signal, and drives the first switching unit (5) by the first driving unit (4).
4. The composite parallel connection type no dead zone distortion audio digital power amplifier of claim 3, characterized in that the feedback unit comprises an operational amplifier U1, a resistor R1 and a resistor R2, the signal input end VIN is connected with the negative terminal of the operational amplifier U1 through the resistor R1, the negative terminal of the operational amplifier U1 is connected with one end of an inductor L1 through a resistor R2, and the positive terminal of the operational amplifier U1 is grounded.
5. The composite parallel connection type no dead zone distortion audio digital power amplifier according to claim 3, wherein the current of the filter capacitor C2 is a combination of the current of the inductor L1 and the current of the load element RL.
6. The composite parallel type no-dead-time-distortion audio digital power amplifier according to claim 1, wherein the current supplement module (2) comprises a current module control and PWM generating circuit (6), a second driving unit (7) and a second switching unit (8), the current module control and PWM generating circuit (6) generates a driving signal according to the sampling current to drive the second switching unit (8) through the second driving unit (7).
7. The composite parallel connection type no-dead-zone-distortion audio digital power amplifier according to claim 6, wherein the current module control and PWM generating circuit (6) generates the driving signal by using current feedback closed loop self-oscillation generation driving signal or triangular wave signal comparison.
8. The composite parallel connection type no-dead-zone-distortion audio digital power amplifier according to claims 1-7, comprising a dual-frequency mode and a single-frequency mode, wherein the dual-frequency mode is that the working frequency of the current supplement module (2) is different from the working frequency of the voltage control module (1), and the single-frequency mode is that the working frequency of the current supplement module (2) and the working frequency of the voltage control module (1) are synchronized at the same working frequency.
9. The composite parallel connection type no-dead-zone distortion audio digital power amplifier according to claim 8, wherein in a dual-frequency mode, the current module control and PWM generation circuit (6) comprises an RC filter circuit, a hysteresis oscillation comparison circuit and a dual-edge trigger, an output current of the voltage control module (1) is filtered by the RC filter circuit and then is connected to an input end of the hysteresis oscillation comparison circuit, an output end of the hysteresis oscillation comparison circuit is connected to the dual-edge trigger, and a CLK end of the dual-edge trigger is connected to a PWM driving signal of the voltage control module (1);
during a single-frequency mode, the current module control and PWM generating circuit (6) comprises an RC filter circuit, a delay circuit and a hysteresis comparison circuit, the output current of the voltage control module (1) is connected to one end of a comparator of the hysteresis comparison circuit after being filtered by the RC filter circuit, the PWM driving signal of the voltage control module (1) is connected to the other end of the comparator after being delayed by the delay circuit, and the output of the comparator is used as the output of the current module control and PWM generating circuit (6).
Priority Applications (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202010728568.0A CN111900944A (en) | 2020-07-27 | 2020-07-27 | Composite parallel connection type audio digital power amplifier without dead zone distortion |
| PCT/CN2020/110398 WO2022021504A1 (en) | 2020-07-27 | 2020-08-21 | Composite parallel type audio digital power amplifier without dead zone distortion |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
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| CN202010728568.0A CN111900944A (en) | 2020-07-27 | 2020-07-27 | Composite parallel connection type audio digital power amplifier without dead zone distortion |
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| CN111900944A true CN111900944A (en) | 2020-11-06 |
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| CN202010728568.0A Withdrawn CN111900944A (en) | 2020-07-27 | 2020-07-27 | Composite parallel connection type audio digital power amplifier without dead zone distortion |
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| CN (1) | CN111900944A (en) |
| WO (1) | WO2022021504A1 (en) |
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN112671353A (en) * | 2021-02-09 | 2021-04-16 | 张金路 | Low-distortion D-type power amplifier applied to high-power range |
| CN113690983A (en) * | 2021-08-26 | 2021-11-23 | 长春捷翼汽车零部件有限公司 | Dead time determination method, charging drive circuit, device, apparatus, and medium |
| CN116112087A (en) * | 2023-01-18 | 2023-05-12 | 华中科技大学 | Driving circuit based on multi-path current segmentation delay and merging output architecture |
Families Citing this family (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| NO347259B1 (en) * | 2022-06-15 | 2023-08-14 | Zenitel Norway As | An improved audio amplifier with a transformer-less output stage and a method for operating an improved audio amplifier |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP4161545B2 (en) * | 2001-06-07 | 2008-10-08 | サンケン電気株式会社 | Switching amplifier |
| CN1835393B (en) * | 2005-03-07 | 2010-10-13 | 美国芯源系统股份有限公司 | Audio amplifier with high power and high efficiency and its control method |
| US7446603B2 (en) * | 2006-08-17 | 2008-11-04 | Matsushita Electric Industrial Co., Ltd. | Differential input Class D amplifier |
| CN101369802B (en) * | 2007-08-16 | 2012-09-05 | 美国芯源系统股份有限公司 | Closed-loop D-class power amplifier and its control method |
| CN102832887B (en) * | 2012-09-11 | 2015-07-29 | 电子科技大学 | High-fidelity D type voice frequency amplifier |
| GB2519540B (en) * | 2013-10-23 | 2018-05-09 | Cirrus Logic Int Semiconductor Ltd | Class-D Amplifier Circuits |
| CN104811151B (en) * | 2014-01-28 | 2018-04-10 | 意法半导体研发(深圳)有限公司 | For reducing the apparatus and method of the slicing in amplifier |
| EP3402070B1 (en) * | 2017-05-11 | 2020-02-12 | Infineon Technologies Austria AG | Class d audio amplifier with adjustable gate drive |
-
2020
- 2020-07-27 CN CN202010728568.0A patent/CN111900944A/en not_active Withdrawn
- 2020-08-21 WO PCT/CN2020/110398 patent/WO2022021504A1/en active Application Filing
Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN112671353A (en) * | 2021-02-09 | 2021-04-16 | 张金路 | Low-distortion D-type power amplifier applied to high-power range |
| WO2022170645A1 (en) * | 2021-02-09 | 2022-08-18 | 张金路 | Low-distortion class d power amplifier applied to high-power range |
| CN112671353B (en) * | 2021-02-09 | 2024-02-13 | 张金路 | Low-distortion class-D power amplifier applied to high-power range |
| CN113690983A (en) * | 2021-08-26 | 2021-11-23 | 长春捷翼汽车零部件有限公司 | Dead time determination method, charging drive circuit, device, apparatus, and medium |
| CN113690983B (en) * | 2021-08-26 | 2024-01-23 | 长春捷翼汽车科技股份有限公司 | Dead time determining method, charging driving circuit, device, equipment and medium |
| CN116112087A (en) * | 2023-01-18 | 2023-05-12 | 华中科技大学 | Driving circuit based on multi-path current segmentation delay and merging output architecture |
| CN116112087B (en) * | 2023-01-18 | 2024-02-27 | 华中科技大学 | Driving circuit based on multi-path current segmentation delay and merging output architecture |
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| WO2022021504A1 (en) | 2022-02-03 |
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Application publication date: 20201106 |
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