CN110829854A - Capacitance clamping type three-level direct current converter adopting asymmetric bidirectional switch - Google Patents

Capacitance clamping type three-level direct current converter adopting asymmetric bidirectional switch Download PDF

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Publication number
CN110829854A
CN110829854A CN201911319125.XA CN201911319125A CN110829854A CN 110829854 A CN110829854 A CN 110829854A CN 201911319125 A CN201911319125 A CN 201911319125A CN 110829854 A CN110829854 A CN 110829854A
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CN
China
Prior art keywords
switching tube
voltage
current
tube
transformer
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Pending
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CN201911319125.XA
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Chinese (zh)
Inventor
石勇
李启凡
宋扬
冯浪浪
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Shaanxi University of Science and Technology
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Shaanxi University of Science and Technology
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Priority to CN201911319125.XA priority Critical patent/CN110829854A/en
Publication of CN110829854A publication Critical patent/CN110829854A/en
Pending legal-status Critical Current

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/487—Neutral point clamped inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

The invention discloses a capacitance clamp type three-level direct current converter adopting an asymmetric bidirectional switch, which comprises a voltage source VinAnd a voltage-dividing capacitor Cin1And a voltage-dividing capacitor Cin2A primary side inverter unit and a transformer T. The input high-voltage direct current is switched on and off by a control switch tube, an alternating-current square wave is obtained on the primary side of the transformer, and then the alternating-current square wave passes through the transformer T and is connected to a rectifier bridge on the secondary side of the transformer, and then the direct-current voltage is output by a filter circuit. The current unbalance problem of the existing three-level circuit is solved, the turn-off current of a switching device in the circuit is reduced, the current stress of a switching tube is reduced, zero-voltage zero-current turn-on and turn-off of the switching tube are realized, the loss of the whole circuit is reduced, and the reliability of the circuit is enhanced.

Description

Capacitance clamping type three-level direct current converter adopting asymmetric bidirectional switch
Technical Field
The invention belongs to the technical field of high-voltage direct-current converters, and particularly relates to a capacitance clamping type three-level direct-current converter adopting an asymmetric bidirectional switch.
Background
Three-level DC-DC converters are the subject of extensive research, since high performance high input power DC converters have great potential in market applications. Compared with the traditional two-level DC-DC converter, the three-level DC-DC converter has the advantages of large output capacity, high output voltage, small current harmonic content and the like.
However, the conventional three-level DC-DC converter has the problem of unbalanced current and unbalanced midpoint potential of the input capacitor, because the charging and discharging time of the upper and lower input capacitors is not equal under the condition that the charging and discharging time of the upper and lower switching tubes is not equal, the inherent disadvantage of unbalanced midpoint potential will be shown. Especially when the duty cycle is reduced, the current of the input capacitor and the switch tube may be in an extremely unbalanced state, which may result in a reduced reliability of the whole circuit and increased stress of the switch tube.
Disclosure of Invention
The invention provides a capacitance clamping type three-level direct current converter adopting an asymmetric bidirectional switch, which solves the problem of current imbalance of the existing three-level circuit, reduces the turn-off current of a switch device in the circuit, reduces the current stress of a switch tube, realizes the zero-voltage zero-current turn-on and turn-off of the switch tube, reduces the loss of the whole circuit and enhances the reliability of the circuit.
In order to achieve the above object, the capacitor clamp type three-level DC converter using asymmetric bidirectional switch according to the present invention comprises a voltage source VinAnd a voltage-dividing capacitor Cin1And a voltage-dividing capacitor Cin2The primary side inverter unit and the transformer T; the primary side inverter unit is a half-bridge inverter circuit and comprises a switching tube Q1And a switching tube Q2pAnd a switching tube Q2RAnd a switching tube Q3And a switching tube Q4pAnd a switching tube Q4RWherein the switching tube Q1And a switching tube Q2pAnd a switching tube Q2RForm an upper bridge arm and a switch tube Q3And a switching tube Q4pAnd a switching tube Q4RForming a lower bridge arm; the voltage source VinPositive electrode and voltage-dividing capacitor Cin1The first end of the switch tube Q1 and the drain electrode of the switch tube Q1 are connected, and a voltage dividing capacitor Cin1Second terminal and voltage-dividing capacitor Cin2The first end of the transformer T is connected with the synonym end of the primary winding of the transformer T; voltage dividing deviceContainer Cin2And a voltage source VinNegative electrode of (1) and switching tube Q4RIs connected with the drain electrode of the transistor; switch tube Q1Source electrode of and switching tube Q2pIs connected with the drain electrode of the switching tube Q2pSource electrode of (1) and switching tube Q2RSource electrode of (1) is connected with a switching tube Q2RDrain electrode of the transformer T, the same-name terminal of the primary winding of the transformer T and the switching tube Q3Is connected with the drain electrode of the switching tube Q3Source electrode of (1) and switching tube Q4PIs connected with the drain electrode of the switching tube Q4PSource electrode of (1) and switching tube Q4RIs connected to the source of (a);
and the secondary side of the transformer T is connected with a rectifying circuit and a filter circuit.
Further, a switch tube Q1Source and flying capacitor CSIs connected to the first end of the switching tube Q3Source and flying capacitor CSIs connected to the second end of the first housing.
Further, a switch tube Q1And a switching tube Q4PThe upper parasitic has junction capacitance.
Further, the filter circuit is an LC filter circuit.
Further, the rectifying circuit is a full bridge rectifying circuit.
Further, the full-bridge rectification circuit includes a diode Do1Diode Do2Diode Do3And a diode Do4。
Further, a switch tube Q1And a switching tube Q2pAnd a switching tube Q2RAnd a switching tube Q3And a switching tube Q4pAnd a switching tube Q4RAre all MOS tubes.
Compared with the prior art, the invention has at least the following beneficial technical effects:
1) because the traditional three-level converter realizes ZVS of the hysteresis tube through leakage inductance resonance, and the topology realizes ZCS of the hysteresis tube through resetting follow current, a wider load output range can be achieved, and compared with the traditional three-level DC converter, the zero-voltage zero-current three-level DC converter has a wider output load range;
2) in the circuitSurface on the capacitor C1Full charge and capacitance C4After p is discharged, a leakage inductance current follow current loop is arranged in the circuit, in the process, the current ip is continuously reduced to zero, so that when the hysteresis tube is switched off, the current is reduced to zero, the switching-off current of the switching tube is greatly reduced compared with that of the traditional three-level direct current converter, the loss of the switching tube is reduced, the efficiency of a power supply is improved, and the service life of a device is prolonged;
3) because the trigger pulse of the traditional circuit switch tube is asymmetric, the current stress of the current unbalanced switch tube is larger; the circuit topology is in a primary current follow current link, so that the primary current is reduced to zero, the time of the process is short, the current is reduced, and the time can be ignored, so that the current stress of the switching tube can be reduced, the on-off signals of the switching tube of the transformer primary current topology are asymmetric, the current imbalance problem of the switching tube is improved, the current stress of the switching tube is reduced, and the reliability of the whole circuit is improved.
Further, in the charging state, the capacitor Cin1And a capacitor Cin2The filter capacitor is used for filtering higher harmonics, so that the power supply of the direct-current power supply is smoother; switch tube Q1And a switching tube Q4PThe parasitic junction capacitor helps the switching tube to realize zero-voltage switching, and the switching tube Q2pAnd a switching tube Q3The anti-parallel diode on the diode is used for realizing the current freewheeling process.
Drawings
FIG. 1 is a schematic diagram of the circuit of the present invention;
FIG. 2 is a schematic diagram of key waveforms;
FIG. 3 is t0A front working state diagram;
FIG. 4 is t0～t1A working state diagram;
FIG. 5 is t1～t3A working state diagram;
FIG. 6 is t3～t4A working state diagram;
FIG. 7 is t4～t5A working state diagram;
FIG. 8 is t5～t6Working state diagram of (1);
FIG. 9 is SkThe voltammetric characteristics of (a);
fig. 10 is a conventional three-level converter circuit topology.
Detailed Description
In order to make the objects and technical solutions of the present invention clearer and easier to understand. The present invention will be described in further detail with reference to the following drawings and examples, wherein the specific examples are provided for illustrative purposes only and are not intended to limit the present invention.
In the description of the present invention, it is to be understood that the terms "first", "second" and the like are used for descriptive purposes only and are not to be construed as indicating or implying relative importance or implying any number of technical features indicated. Thus, a feature defined as "first" or "second" may explicitly or implicitly include one or more of that feature. In the description of the present invention, "a plurality" means two or more unless otherwise specified. In the description of the present invention, it should be noted that, unless otherwise explicitly specified or limited, the terms "mounted," "connected," and "connected" are to be construed broadly, e.g., as meaning either a fixed connection, a removable connection, or an integral connection; can be mechanically or electrically connected; they may be connected directly or indirectly through intervening media, or they may be interconnected between two elements. The specific meanings of the above terms in the present invention can be understood in specific cases to those skilled in the art.
Referring to fig. 1, a capacitance clamp type three-level direct current converter adopting an asymmetric bidirectional switch adds two anti-parallel switching tubes Q in the original three-level topology2RAnd Q4RThe defects in the traditional three-level direct current converter are overcome, and the problem of unbalanced midpoint potential of the input capacitor is solved through the flying capacitor Cs.
The complete principle of the circuit topology of the present invention is shown in FIG. 3, which includes a voltage source VinAn input voltage-dividing capacitor Cin1And is divided intoVoltage capacitor Cin2Flying capacitor CSThe primary side inverter unit, the transformer, the rectifying unit, the LC filter circuit and the load. And selecting the type of the power tube according to the voltage grade.
The input high-voltage direct current is switched on and off by a control switch tube, an alternating-current square wave is obtained on the primary side of the transformer, and then the alternating-current square wave passes through the transformer T and is connected to a rectifier bridge on the secondary side of the transformer, and then the direct-current voltage is output by a filter circuit. FIG. 9 is SkK is 2, 4. S2Comprising a switching tube Q2PAnd a switching tube Q2RSwitching tube Q2PDrain electrode of (1) and switching tube Q1Source electrode of (1) is connected with a switching tube Q2PSource electrode of (1) and switching tube Q2RSource electrode of (1) is connected with a switching tube Q2RDrain electrode of the transformer T, the same-name terminal of the primary winding of the transformer T and the switching tube Q3Is connected with the drain electrode of the transistor; s4Comprising a switching tube Q4PAnd a switching tube Q4RSwitching tube Q4PDrain electrode of (1) and switching tube Q3Source electrode of (1) is connected with a switching tube Q4PSource electrode of (1) and switching tube Q4RSource electrode of (1) is connected with a switching tube Q4RDrain electrode and voltage dividing capacitor Cin2Is connected to the second end of the first housing.
The primary side inverter unit is a half-bridge inverter circuit comprising a switching tube Q1And a switching tube Q2pAnd a switching tube Q2RAnd a switching tube Q3And a switching tube Q4pAnd a switching tube Q4RWherein the switching tube Q1And a switching tube Q2pAnd a switching tube Q2RForm an upper bridge arm and a switch tube Q3And a switching tube Q4pAnd a switching tube Q4RForming a lower bridge arm; in fig. 1 to 8, the parallel diode and the capacitor beside the switch tube are parasitic to the switch tube itself. The rectification unit on the secondary side of the transformer is a full-bridge rectification circuit comprising a diode Do1Diode Do2Diode Do3And a diode Do4(ii) a The filter circuit is an LC filter circuit including an inductor LoAnd a capacitor Co(ii) a The load is R.
The concrete connection mode is as follows: voltage source VinPositive electrode and voltage-dividing capacitor Cin1To (1) aOne end of the capacitor is connected with the drain electrode of the switching tube Q1, and the voltage dividing capacitor Cin1Second terminal and voltage-dividing capacitor Cin2The first end of the transformer T is connected with the synonym end of the primary winding of the transformer T; voltage dividing capacitor Cin2And a voltage source VinNegative electrode of (1) and switching tube Q4RIs connected with the drain electrode of the transistor; switch tube Q1Source and flying capacitor CSFirst terminal of (1) and switching tube Q2pIs connected with the drain electrode of the switching tube Q2pSource electrode of (1) and switching tube Q2RSource electrode of (1) is connected with a switching tube Q2RDrain electrode of the transformer T, the same-name terminal of the primary winding of the transformer T and the switching tube Q3Is connected with the drain electrode of the switching tube Q3Source and flying capacitor CSSecond terminal and switching tube Q4PIs connected with the drain electrode of the switching tube Q4PSource electrode of (1) and switching tube Q4RSource electrode of (1) is connected with a switching tube Q4RDrain electrode and voltage dividing capacitor Cin2Is connected to the second end of the first housing. Dotted terminal of secondary winding of transformer T and diode D01Cathode of (2), diode D03Cathode and inductor LoIs connected with the first end of the first connecting pipe; synonym terminal and diode D04Is connected to the anode of diode D01And diode D02Is connected to the cathode of a diode D03And diode D04Is connected to the cathode of a diode D04And diode D02Anode and capacitor CoIs connected with the second end of the first end; inductor LoSecond terminal of and a capacitor CoIs connected with the first end of the first connecting pipe; capacitor CoAre used for connecting loads R in parallelo。
The working mode is that high-voltage direct current is converted into high-voltage square wave alternating current through a half-bridge inverter circuit, the high-voltage square wave alternating current is converted into low-voltage square wave alternating voltage through a transformer T, then the low-voltage square wave alternating voltage is converted into direct current voltage through a rectifying circuit, and finally high-frequency components are eliminated through an LC filter circuit to obtain stable direct current voltage with small ripples.
FIG. 2 is a timing diagram of the conduction of each switch transistor, switch transistor Q2pAnd a switching tube Q3Conducting alternately; switching tube Q4pAnd a switching tube Q1Conducting alternately; switch tube Q2RAt the switching tube Q3Is conducted when conducted and is at the switch tube Q4pTurning off when the switch is turned on; closing tube Q4RAt the switching tube Q1Is conducted when conducted and is at the switch tube Q2pAnd is turned off when turned on.
FIG. 3 is a graph at t0Previous operating state diagram, at t0Switching tube Q of primary side of high-frequency transformer T before moment1And a switching tube Q2pAnd a switching tube Q2RAnd Q4RAre all in a conducting state, and secondary side diodes Do1And Do4Simultaneously conducted, primary side current of high frequency transformer T is from voltage source VinStarting from the positive pole, sequentially flows through the switching tube Q1And a switching tube Q2pAnd a switching tube Q2RAnd the primary side of the high-frequency transformer T; the secondary current of the high-frequency transformer T flows through the diode D from the secondary side of the T in sequence01Load ROAnd a diode Do4And finally flows back to the secondary side of the high-frequency transformer T and the capacitor Cin2The voltage at both ends will gradually rise, and Q is at the moment4RAlthough conducting, no current flows.
FIG. 4 is t0～t1At t, at0～t1In the time period: at time t0, the switch tube Q1Is turned off because of the capacitance C1So that the switching tube Q is1The voltage at two ends can not change suddenly and has a slow rising process, so that the switching tube Q is switched1Zero voltage turn-off can be achieved, then the capacitor C1Rise in voltage, capacitance C4pDischarge through flying capacitor Cs, switching tube Q3The voltage across the capacitor Cs continues to C1The voltage at both ends becoming V in2 and C4PThe voltage drops to 0, during which time the switch tube Q is switched1And a switching tube Q4PThe voltages at both ends are less than Vin/2。
FIG. 5 is t1～t3At t, at1～t3Within a time period of t1Time of day, diode D4pNaturally conducting, the current ip flowing through the primary side of the transformer is always reduced, and the secondary side of the high-frequency transformer T is caused by the filter inductance LoIs stored inAt, four diodes Do1、Do2、Do3And Do4Simultaneously conducting to provide load current; wherein at t2Time switch tube Q4PIs turned on by zero voltage and the switching tube Q2RIs turned off by a zero voltage.
FIG. 6 is t3～t4At t, at3～t4During the time period, at time t3, ipReduced to zero but due to diode D2RIs present so that ipThe direction can not be changed, and at the moment, the switch tube Q2PCan be turned off at zero current and has a secondary diode Do1Diode Do2Diode Do3And a diode Do4And meanwhile, the high-frequency transformer T is conducted, the primary side current is zero, and the secondary side is in a follow current state.
FIG. 7 is t4～t5At t, at4～t5In time period, secondary side diode Do1Diode Do2Diode Do3And a diode Do4Meanwhile, the primary side current of the high-frequency transformer T is still zero; since the primary current is zero, it flows through the switching tube Q2pIs also zero at t5Time-off switch tube Q2pI.e. to realize the switching tube Q2pThe zero current of (c) is turned off.
FIG. 8 is t5～t6At t, at5～t6Within a time period of t5At any moment, the switching tube Q is switched on3The current rises slowly due to the leakage inductance of the transformer, so that Q3Belongs to zero current switching-on, and can simultaneously switch on the switching tube Q2RZero current turn-on, because of the switching tube Q2PHas been turned off, and the switching tube Q4PHas been opened at t2At this time, the primary current starts to increase reversely, and the maximum primary current reaches-Io/kTAt this time, the diode Do2、Do3On and diode Do1、Do4Will shut off, the circuit enters the next stage; the above six processes are repeated at the next stage.
Switch with a switch bodyWhen the tube Q1 and the switch tube Q4p realize zero voltage turn-on, the capacitor C1And a capacitor C4pThe energy on the switch tube Q should be larger than that on the inductor2pAnd a switching tube Q3The zero current turn-on is determined by the leakage inductance LlkThe size of (d) and also the duty cycle loss of the whole process are also strongly related to leakage inductance.
The invention reduces the loss of the switch tube to a great extent and realizes soft switching.
By controlling the on-off of the switching tube, an alternating-current square wave can be obtained on the primary side of the high-frequency transformer after passing through the three-level inverter bridge, a square wave voltage is obtained on the secondary side of the high-frequency transformer after passing through the high-frequency transformer, and a stable direct-current pulse voltage is obtained on the load side after passing through the rectifier bridge.
In the charging state, the capacitor Cin1And a capacitor Cin2The filter capacitor is used for filtering higher harmonics, so that the power supply of the direct-current power supply is smoother; MOS tube Q1And MOS transistor Q4PThe parasitic junction capacitor helps the switching tube to realize zero-voltage switching, and the MOS tube Q2pAnd MOS transistor Q3The anti-parallel diode on the diode is used for realizing the current freewheeling process.
In the inverter circuit, MOS transistor Q2R、Q4RThe function of the clamping device is to clamp voltage and limit reverse current; when the current is not reversed, the switch tube Q is controlled2R、Q4RThe switching on and off of the primary side can clamp the primary side voltage at Vin/2; when the current is reversed, the switch tube Q is controlled2R、Q4RCan block reverse current from flowing back to Cin1And Cin2The loss of primary current is reduced, and C is also reducedin1、Cin2And an unbalanced condition of shut-off.
Compared with the traditional three-level direct current conversion circuit, the three-level direct current conversion circuit reduces the turn-off current of elements, improves the zero voltage load range of a lagging bridge arm, and integrally improves the reliability of circuit operation. The current unbalance problem of the existing three-level circuit is solved, the turn-off current of a switching device in the circuit is reduced, the current stress of a switching tube is reduced, the zero-voltage zero-current turn-on and turn-off of the switching tube are realized, the loss of the whole circuit is reduced, and the reliability of the circuit is enhanced.
The above-mentioned contents are only for illustrating the technical idea of the present invention, and the protection scope of the present invention is not limited thereby, and any modification made on the basis of the technical idea of the present invention falls within the protection scope of the claims of the present invention.

Claims (7)

1. The capacitor clamping type three-level direct current converter adopting the asymmetric bidirectional switch is characterized by comprising a voltage source VinAnd a voltage-dividing capacitor Cin1And a voltage-dividing capacitor Cin2The primary side inverter unit and the transformer T;
the primary side inverter unit is a half-bridge inverter circuit and comprises a switching tube Q1And a switching tube Q2pAnd a switching tube Q2RAnd a switching tube Q3And a switching tube Q4pAnd a switching tube Q4RWherein the switching tube Q1And a switching tube Q2pAnd a switching tube Q2RForm an upper bridge arm and a switch tube Q3And a switching tube Q4pAnd a switching tube Q4RForming a lower bridge arm;
the voltage source VinPositive electrode and voltage-dividing capacitor Cin1The first end of the switch tube Q1 and the drain electrode of the switch tube Q1 are connected, and a voltage dividing capacitor Cin1Second terminal and voltage-dividing capacitor Cin2The first end of the transformer T is connected with the synonym end of the primary winding of the transformer T; voltage dividing capacitor Cin2And a voltage source VinNegative electrode of (1) and switching tube Q4RIs connected with the drain electrode of the transistor; switch tube Q1Source electrode of and switching tube Q2pIs connected with the drain electrode of the switching tube Q2pSource electrode of (1) and switching tube Q2RSource electrode of (1) is connected with a switching tube Q2RDrain electrode of the transformer T, the same-name terminal of the primary winding of the transformer T and the switching tube Q3Is connected with the drain electrode of the switching tube Q3Source electrode of (1) and switching tube Q4PIs connected with the drain electrode of the switching tube Q4PSource electrode of (1) and switching tube Q4RIs connected to the source of (a);
and the secondary side of the transformer T is connected with a rectifying circuit and a filter circuit.
2. The capacitance-clamped three-level DC converter with asymmetric bidirectional switches according to claim 1, wherein the switch transistor Q1Source and flying capacitor CSIs connected to the first end of the switching tube Q3Source and flying capacitor CSIs connected to the second end of the first housing.
3. The capacitance-clamped three-level DC converter with asymmetric bidirectional switches according to claim 1, wherein the switch transistor Q1And a switching tube Q4PThe upper parasitic has junction capacitance.
4. The capacitance-clamped three-level direct current converter employing asymmetric bidirectional switches according to claim 1, wherein the filter circuit is an LC filter circuit.
5. The capacitance-clamped three-level direct current converter employing asymmetric bidirectional switches according to claim 1, wherein the rectification circuit is a full-bridge rectification circuit.
6. The capacitance-clamped three-level DC converter according to claim 5, wherein the full-bridge rectification circuit comprises a diode Do1Diode Do2Diode Do3And a diode Do4。
7. The capacitance-clamped three-level DC converter with asymmetric bidirectional switches according to claim 1, wherein the switch transistor Q1And a switching tube Q2pAnd a switching tube Q2RAnd a switching tube Q3And a switching tube Q4pAnd a switching tube Q4RAre all MOS tubes.
CN201911319125.XA 2019-12-19 2019-12-19 Capacitance clamping type three-level direct current converter adopting asymmetric bidirectional switch Pending CN110829854A (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN201911319125.XA CN110829854A (en) 2019-12-19 2019-12-19 Capacitance clamping type three-level direct current converter adopting asymmetric bidirectional switch

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN201911319125.XA CN110829854A (en) 2019-12-19 2019-12-19 Capacitance clamping type three-level direct current converter adopting asymmetric bidirectional switch

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Publication Number Publication Date
CN110829854A true CN110829854A (en) 2020-02-21

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