CN110460337A - A kind of high-speed sampling and reconstructing method - Google Patents
A kind of high-speed sampling and reconstructing method Download PDFInfo
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- CN110460337A CN110460337A CN201910744050.3A CN201910744050A CN110460337A CN 110460337 A CN110460337 A CN 110460337A CN 201910744050 A CN201910744050 A CN 201910744050A CN 110460337 A CN110460337 A CN 110460337A
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03M—CODING; DECODING; CODE CONVERSION IN GENERAL
- H03M1/00—Analogue/digital conversion; Digital/analogue conversion
- H03M1/004—Reconfigurable analogue/digital or digital/analogue converters
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03M—CODING; DECODING; CODE CONVERSION IN GENERAL
- H03M1/00—Analogue/digital conversion; Digital/analogue conversion
- H03M1/10—Calibration or testing
- H03M1/1009—Calibration
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03M—CODING; DECODING; CODE CONVERSION IN GENERAL
- H03M1/00—Analogue/digital conversion; Digital/analogue conversion
- H03M1/12—Analogue/digital converters
- H03M1/124—Sampling or signal conditioning arrangements specially adapted for A/D converters
- H03M1/1245—Details of sampling arrangements or methods
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/03—Shaping networks in transmitter or receiver, e.g. adaptive shaping networks
- H04L25/03006—Arrangements for removing intersymbol interference
- H04L25/03159—Arrangements for removing intersymbol interference operating in the frequency domain
Abstract
The invention discloses a kind of methods of high-speed sampling and reconstruct, by 0~fsFrequency range is divided into M frequency sub-band, and each frequency sub-band bandwidth is fs/ M, and center simulation resonance angular frequency is (2i+1) π fs/ (2M), by the frequency spectrum shift of the sub-band signals of each big bandwidth signal of input to base band, and it filters out with outer garbage signal, then analog-to-digital conversion, symmetrical Digital Up Convert processing are carried out simultaneously, it will be moved in the sub-band signal centre frequency for being each positioned at base band to original radio frequency position, finally, digital signal is summed up, obtained output signal.In this way, each simulation low-pass filter performance parameter is all the same, the tap coefficient and impulse response of the wave digital lowpass filter of design are all the same, significantly reduce design complexities；The sample rate and processing bandwidth of required each ADC, more common frequency alternative expression sampling further reduced half, it is meant that the requirement to each ADC is looser with for reconstructing method.
Description
Technical field
The invention belongs to signal samplings and reconfiguration technique field, more specifically, are related to a kind of high speed and big bandwidth letter
Number carry out high-speed sampling and reconstruct method.
Background technique
Analog signal is carried out sampling to must satisfy Shannon-being Qwest's Sampling Theorem, i.e., required sample rate is at least
It is twice of signal bandwidth.This means that the bandwidth of analog signal is bigger, and the requirement to sample rate is higher；And single mould
The sample rate of number converter ADC be it is extremely limited, this has resulted in becoming larger of signal bandwidth trend and ADC device performance status
Violent contradiction.
As application, the signal bandwidths of required processing such as current popular 5G communication, satellite radar communication, data-link transmission are equal
Reached several G hertz it is even higher, this is that existing single ADC can not be sampled directly.At present popular to utilize multi-disc
ADC carries out parallel sampling to break the bottleneck of single ADC, the sampling of main having time alternative expression and reconstruct and the frequency of more application
Two methods of alternative expression sampling and reconstruct.But the former can only be simple raising sample rate, and the signal bandwidth that can be handled is still etc.
It is same as the bandwidth of a device of each ADC, can not solve the problems, such as big bandwidth signal processing.Therefore, it for big bandwidth signal, often adopts
It is realized with the sampling of frequency alternative expression with reconstructing method, sampling side by side is carried out to realize overall sample rate for f with M ADCsFor,
Its realization principle is as shown in Figure 1.
For the sampling of existing frequency alternative expression and reconstructing method, as shown in Figure 1, the sample frequency of M ADC is reduced to fs/
M, and the maximum signal bandwidth that this method can be handled is fs/ 2, the acquisition for big bandwidth signal is effective, but needs
Frequency band sorting is carried out to input signal using a simulation low-pass filter and several analog bandpass filters, not only complicated journey
Degree is high, and the very high bandpass filter of order also tends to be difficult to realize.In addition, the institute in the digital signal processing device of the rear end ADC
The restructing algorithm that need to be designed is also considerably complicated, very big to the realization influential effect of this method.Therefore, generally speaking, existing frequency
Alternative expression sampling is difficult with the hardware realization of reconstructing method and ineffective, now also predominantly stays in theoretical research rank
Section.
Summary of the invention
It is an object of the invention to overcome the deficiencies of the prior art and provide a kind of methods of high-speed sampling and reconstruct, with more
Efficiently, analog-to-digital conversion process is carried out to big bandwidth signal with more can be achieved.
For achieving the above object, the method for high-speed sampling of the present invention and reconstruct, which is characterized in that including following step
It is rapid:
(1), M orthogonal local oscillation signal is subjected to Frequency mixing processing with the big bandwidth signal of input respectively, obtains the road M mixing letter
Number, wherein the simulation resonance angular frequency of the orthogonal local oscillation signal on the road m is Ωm, and it is equal to (2m+1) π fs/ (2M), m=0,
1 ..., M-1, fsTo carry out sample rate required for directly sampling to the big bandwidth signal of input；
(2), low-pass filtering is carried out to the road M mixed frequency signal respectively, obtains M roadbed band signal, wherein per low-pass filtering all the way
The performance parameter of the simulation low-pass filter of use is all the same, cutoff frequency fs/(2M)；
(3), M roadbed band signal is sampled respectively, obtains the road M baseband digital signal, wherein per what is sampled all the way
The sample clock frequency of ADC is all the same, and is fs/(2M)；
(4), interpolation processing is carried out to the road M baseband digital signal respectively, obtains the road M interpolation baseband digital signal, wherein is every
The interpolation factor of the interpolation arithmetic module of interpolation processing is 2M all the way；
(5), digital low-pass filtering operation is carried out to the road M interpolation baseband digital signal respectively, obtains the road M low frequency interpolation base band
Digital signal, wherein the wave digital lowpass filter that each railway digital low-pass filtering uses, required for the tap coefficient used and
Impulse response is all the same；
(6), for the road M low frequency interpolation baseband digital signal, it is with angular frequency by the i-th road low frequency interpolation baseband digital signal
ωiDigital signal carry out orthogonal mixing, obtain the road M mixing output digit signals, wherein ωi=(2i+1) π/(2M)；
(7), output digit signals are mixed for the road M, while carry out width phase imbalance correction, lost to because of I, Q sampling bring
Weighing apparatus influences to compensate, and obtains the road M calibration digital signal,
(8), the road M calibration digital signal is summed up, obtains the digital signal of high-speed sampling and reconstruct, and the number
The sample rate of word signal is fs。
Goal of the invention of the invention is achieved in that
The method of high-speed sampling of the present invention and reconstruct, by 0~fsFrequency range is divided into M frequency sub-band, each frequency sub-band bandwidth
It is fs/ M, and center simulation angular frequency is (2i+1) π fs/ (2M) will be each first with orthogonal local oscillation signal and frequency mixer
The frequency spectrum shifts of the sub-band signals of big bandwidth signal is inputted to base band, and is filtered out by simulation low-pass filter with outer useless letter
Number, then each roadbed band signal is moved to the sub-band signal of base band while carrying out analog-to-digital conversion, and then to modulus
The digital signal obtained after conversion carries out symmetrical Digital Up Convert processing (by interpolation arithmetic, digital low-pass filtering operation sum number
The orthogonal mixing operations of word are completed), the purpose of Digital Up Convert processing in addition to by data transfer rate from fs/ (2M) is promoted to fsIn addition, will also
It moves in the aforementioned sub-band signal centre frequency for being each positioned at base band to original radio frequency position.Finally, by each Digital Up Convert
Digital signal after reason sums up, and obtained output signal is to input the undistorted reproduction of big broadband signal.
With the sampling of existing frequency alternative expression with reconstructing method compared with, high-speed sampling of the present invention and reconstructing method also have with
Lower advantage:
(1), each simulation low-pass filter performance parameter of the front end ADC is all the same, and ADC back-end digital signal processing
The tap coefficient of the wave digital lowpass filter of required design and impulse response are all the same in device, and it is complicated to significantly reduce design
Degree；
(2), realize that in sample rate be fsUnder conditions for the treatment of process that a big bandwidth signal is sampled and reconstructed, institute
The sample rate and processing bandwidth of each ADC needed, for more common frequency alternative expression sampling and reconstructing method, further
Reduce half, it is meant that the requirement to each ADC is looser.
It can be seen that high-speed sampling of the present invention and reconstructing method, can carry out effective analog-to-digital conversion process, solution to big bandwidth signal
Common frequency alternative expression of having determined samples the limitation that the design with reconstructing method is complicated, is difficult to realize.In particular with signal band
Wide further promotion, existing frequency alternative expression sampling will gradually fail with reconstructing method, and high-speed sampling of the present invention and reconstruct
Method can also continue to be competent at, and be easier to Project Realization.
Detailed description of the invention
Fig. 1 is the functional block diagram of existing frequency alternative expression sampling and reconstructing method；
Fig. 2 is a kind of specific embodiment of method that high speed of the invention and big bandwidth signal carry out high-speed sampling and reconstruct
Flow chart；
Fig. 3 is a kind of particular hardware realization side of method that high speed of the invention and big bandwidth signal carry out high-speed sampling and reconstruct
The functional block diagram of formula.
Specific embodiment
A specific embodiment of the invention is described with reference to the accompanying drawing, preferably so as to those skilled in the art
Understand the present invention.Requiring particular attention is that in the following description, when known function and the detailed description of design perhaps
When can desalinate main contents of the invention, these descriptions will be ignored herein.
Fig. 2 is a kind of specific embodiment of method that high speed of the invention and big bandwidth signal carry out high-speed sampling and reconstruct
Flow chart, Fig. 3 are the functional block diagrams of its particular hardware implementation.
In the present embodiment, as shown in Figure 2,3, high-speed sampling of the present invention and the method for reconstruct the following steps are included:
Step S1: Frequency mixing processing
M orthogonal local oscillation signal is subjected to Frequency mixing processing with input analog signal, that is, big bandwidth signal respectively, it is mixed to obtain the road M
Frequency signal, wherein the simulation resonance angular frequency of the orthogonal local oscillation signal on the road m is Ωm, and it is equal to (2m+1) π fs/ (2M), m=
0,1 ..., M-1, fsIt is often very high or even high to carry out sample rate required for directly sampling to the big bandwidth signal of input,
Alternatively referred to as overall sample rate.
Specifically, M orthogonal local oscillation signal, simulation resonance angular frequency is respectively Ω0,Ω1,…ΩM-1, occurrence according to
It is secondary to be equal to π fs/(2M),3πfs/(2M),...,(2M-1)πfs/ (2M) is respectively input in corresponding frequency mixer and input
Big bandwidth signal carries out Frequency mixing processing, obtains the road M mixed frequency signal.
Inputting big bandwidth signal is the analog signal for needing to carry out high-speed sampling and reconstruct, is expressed as x (t), and M orthogonal
The mathematic(al) representation of local oscillator isWherein,So, mixed by M
After frequency device, M mixed frequency signal x is obtainedm(t), mixed frequency signal xm(t) frequency response indicates are as follows:
Xm(j Ω)=X (j Ω+j Ωm) (1)
Step S2: analogue low pass filtering
Low-pass filtering is carried out to the road M mixed frequency signal respectively, obtains M roadbed band signal, wherein is used per low-pass filtering all the way
Simulation low-pass filter performance parameter it is all the same, cutoff frequency fs/(2M)。
Each road mixed frequency signal obtained after mixing is filtered out via the simulation low-pass filter of same performance parameter with outer useless
Signal, if indicating the frequency response of low-pass filter, m roadbed band signal after being filtered with Φ (j Ω)Frequency domain characterization
Are as follows:
Step S3:ADC sampling
M roadbed band signal is sampled respectively, obtains the road M baseband digital signal, wherein per the ADC's sampled all the way
Sample clock frequency is all the same, and is fs/(2M)。
The road m base band signalThe road m baseband digital signal x is obtained after the ADC on road conversionm[n], frequency
Domain equation can be expressed as:
In formula (3), Ts=1/fsIndicate the overall sampling period.
Step S4: interpolation processing
Interpolation processing is carried out to the road M baseband digital signal respectively, obtains the road M interpolation baseband digital signal, wherein per all the way
The interpolation factor of the interpolation arithmetic module of interpolation processing is 2M.
Step S5: digital low-pass filtering operation
Digital low-pass filtering operation is carried out to the road M interpolation baseband digital signal respectively, obtains the road M low frequency interpolation base-band digital
Signal, wherein the wave digital lowpass filter that each railway digital low-pass filtering uses, required for the tap coefficient and impulse used
It responds all the same.
Step S6: orthogonal mixing
It is ω by the i-th tunnel and angular frequency for the road M low frequency interpolation baseband digital signaliDigital signal carry out it is orthogonal mixed
Frequently, the road M mixing output digit signals are obtained, wherein ωi=(2i+1) π/(2M).
To the road m baseband digital signal xm[n] carries out 2M times of interpolation processing, digital low-pass filtering operation and orthogonal mixing,
Obtain digital signal ym[n], frequency domain equation can be expressed as
Wherein, Ψ (ejω) be wave digital lowpass filter frequency-domain expression.
Step S7: width phase imbalance correction
Output digit signals are mixed for the road M, while carrying out width phase imbalance correction, sample the unbalance shadow of bring to because of I, Q
Sound compensates, and obtains the road M calibration digital signal；
Step S8: adduction
The road M calibration digital signal is summed up, the digital signal i.e. numeral output of high-speed sampling and reconstruct is obtained
Signal, and the sample rate of the digital signal is fs。
Digital output signal, that is, high-speed sampling of time domain and the digital signal of reconstruct are indicated with y [n], then its spectral response can
It indicates are as follows:
Wherein,
AndIt should meet,
In formula (7), A indicates the amplitude gain of signal sampling, the delay factor of τ representation signal processing.
In the present embodiment, as shown in figure 3, using high performance digital signal processing device, such as FPGA, DSP, ASIC
It is handled to complete the interpolation processing after ADC sampling, digital low-pass filtering operation, orthogonal mixing, width phase imbalance correction, adduction etc.,
The ADC road the M baseband digital signal exported in the road M is sent into the digital signal processing device and is handled.
Hardware programming design is carried out in digital signal processing device, designing one group of (M) interpolation factor first is 2M's
Interpolation arithmetic module carries out interpolation processing to the baseband digital signal of the ADC output on the road M respectively, then to the M roadbed after interpolation
Band digital signal carries out digital low-pass filtering operation respectively, per the tap system used required for the digital low-pass filtering of signal all the way
Several and impulse response is all the same.
M digital controlled oscillator NCO is designed, is believed with the road the M low frequency interpolation base-band digital obtained after digital low-pass filtering operation
Number orthogonal Frequency mixing processing is carried out by multiplier, wherein the digital angular frequency of M digital controlled oscillator is ω0,ω1,…ωm,…
ωM-1, and be successively equal to
By M multiplier output signal i.e. be mixed output digit signals simultaneously be sent into width phase imbalance correction module, to because
I, Q samples the unbalance influence of bring and compensates, and obtains the road M calibration digital signal and is sent into rear class adder, i.e., calibrates the road M
Digital signal carries out summation process, obtains the digital signal of digital output signal i.e. high-speed sampling and reconstruct.
Although the illustrative specific embodiment of the present invention is described above, in order to the technology of the art
Personnel understand the present invention, it should be apparent that the present invention is not limited to the range of specific embodiment, to the common skill of the art
For art personnel, if various change the attached claims limit and determine the spirit and scope of the present invention in, these
Variation is it will be apparent that all utilize the innovation and creation of present inventive concept in the column of protection.
Claims (2)
1. a kind of method of high-speed sampling and reconstruct, which comprises the following steps:
(1), M orthogonal local oscillation is subjected to Frequency mixing processing with the big bandwidth signal of input respectively, obtains the road M mixed frequency signal, wherein the
The simulation resonance angular frequency of the orthogonal local oscillation on the road m is Ωm, and it is equal to (2m+1) π fs/ (2M), m=0,1 ..., M-1；
(2), low-pass filtering is carried out to the road M mixed frequency signal respectively, obtains M roadbed band signal, wherein is used per low-pass filtering all the way
Simulation low-pass filter performance parameter it is all the same, cutoff frequency fs/(2M)；
(3), M roadbed band signal is sampled respectively, obtains the road M baseband digital signal, wherein per the ADC's sampled all the way
Sample clock frequency is all the same, and is fs/(2M)；
(4), interpolation processing is carried out to the road M baseband digital signal respectively, obtains the road M interpolation baseband digital signal, wherein per all the way
The interpolation factor of the interpolation arithmetic module of interpolation processing is 2M；
(5), digital low-pass filtering operation is carried out to the road M interpolation baseband digital signal respectively, obtains the road M low frequency interpolation base-band digital
Signal, wherein the wave digital lowpass filter that each railway digital low-pass filtering uses, required for the tap coefficient and impulse used
It responds all the same；
It (6), is ω by the i-th tunnel and angular frequency for the road M low frequency interpolation baseband digital signaliDigital signal carry out it is orthogonal mixed
Frequently, the road M mixing output digit signals are obtained, wherein ωi=(2i+1) π/(2M)；
(7), output digit signals are mixed for the road M, while carry out width phase imbalance correction, sample the unbalance shadow of bring to because of I, Q
Sound compensates, and obtains the road M calibration digital signal,
(8), the road M calibration digital signal is summed up, obtains the digital signal of high-speed sampling and reconstruct, and the number is believed
Number sample rate be fs。
2. the method for high-speed sampling according to claim 1 and reconstruct, which is characterized in that described step (4)~(8) use
Digital signal processing device designs corresponding module and carries out.
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| CN111474525A (en) * | 2020-04-16 | 2020-07-31 | 上海交通大学 | Ultra-wideband radar target echo signal simulation method and simulator |
| CN112260979A (en) * | 2020-10-22 | 2021-01-22 | 电子科技大学 | Multichannel parallel segmented modulation method |
| CN113708863A (en) * | 2021-09-10 | 2021-11-26 | 中国人民解放军63891部队 | Method and device for constructing spectrum sensing training data set |
| CN114844553A (en) * | 2022-03-29 | 2022-08-02 | 北京航空航天大学 | Single code element rate sampling method based on prior filtering for high-speed transmission |
| CN115765744A (en) * | 2023-02-10 | 2023-03-07 | 成都立思方信息技术有限公司 | Broadband signal sampling method |
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| CN113708863A (en) * | 2021-09-10 | 2021-11-26 | 中国人民解放军63891部队 | Method and device for constructing spectrum sensing training data set |
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| CN114844553A (en) * | 2022-03-29 | 2022-08-02 | 北京航空航天大学 | Single code element rate sampling method based on prior filtering for high-speed transmission |
| CN115765744A (en) * | 2023-02-10 | 2023-03-07 | 成都立思方信息技术有限公司 | Broadband signal sampling method |
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