CN110035580B - Constant-current control circuit of boosting type LED drive circuit and application thereof - Google Patents
Constant-current control circuit of boosting type LED drive circuit and application thereof Download PDFInfo
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- CN110035580B CN110035580B CN201910317717.1A CN201910317717A CN110035580B CN 110035580 B CN110035580 B CN 110035580B CN 201910317717 A CN201910317717 A CN 201910317717A CN 110035580 B CN110035580 B CN 110035580B
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- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
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- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
- H05B45/50—Circuit arrangements for operating light-emitting diodes [LED] responsive to malfunctions or undesirable behaviour of LEDs; responsive to LED life; Protective circuits
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
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- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B20/00—Energy efficient lighting technologies, e.g. halogen lamps or gas discharge lamps
- Y02B20/30—Semiconductor lamps, e.g. solid state lamps [SSL] light emitting diodes [LED] or organic LED [OLED]
Abstract
The invention provides a constant current control circuit, wherein the input end of a Delay is connected with a GATE end, and the output end of the Delay is connected with the input end of an inverter J21; one input end of the AND GATE J22 is connected with the output end of the inverter J21, the other input end is connected with the GATE end, and the output end is connected with the R end of the RS trigger J23; an S end of the RS trigger J23 is connected with an inductive current zero-crossing signal zcd, and a Q end outputs a signal disch; the input end of the inverter J31 is connected with the GATE end, and the output end is connected with the CK end of the D trigger DFF; the D end of the D trigger DFF is connected with the VCC end, and the R end is connected with the inductive current zero-crossing signal zcd; the input end of the inverter J32 is connected with the Q end of the D trigger DFF, and a signal Non-Tout is output; the constant current control method has the advantages of being reliable and stable, and being capable of controlling the constant current precision of the output current in the full voltage range for the boost type LED switch driving scheme.
Description
Technical Field
The invention discloses a constant current control circuit of a boosting type LED drive circuit and application thereof
Background
In recent years, high-brightness LED lighting is gradually replacing traditional light sources such as incandescent lamps and fluorescent lamps with advantages of high light efficiency, long service life, high reliability and no pollution. Nowadays, due to the rapid development of LED illumination, the original incandescent lamp with dozens of watts can be directly replaced by the LED bulb with several watts, so that a large amount of energy can be saved.
According to the load characteristics of the LED, the LED can not be directly supplied with a voltage source like a common incandescent lamp, otherwise, the voltage fluctuation is slightly increased, and the current is increased to the extent of burning the LED. In order to stabilize the working current of the LED and ensure that the LED can work normally and reliably, a controllable constant current source is required for control.
Disclosure of Invention
The invention aims to provide a constant current control circuit of a boost LED drive circuit and application thereof, and a reliable and stable constant current control method, which can control the constant current precision of output current in a full voltage range for a boost LED switch drive scheme; to overcome the disadvantages of the prior art.
The invention provides a constant current control circuit, comprising: a sampling circuit J1, a signal generation circuit J2, a signal generation circuit J3, and a current algorithm function circuit J4; the signal generating circuit J2 comprises a Delay, an inverter J21, an AND gate J22 and an RS trigger J23; the input end of the delayer is connected with the GATE end, and the output end of the delayer is connected with the input end of the inverter J21; one input end of the AND GATE J22 is connected with the output end of the inverter J21, the other input end is connected with the GATE end, and the output end is connected with the R end of the RS trigger J23; an S end of the RS trigger J23 is connected with an inductive current zero-crossing signal zcd, and a Q end outputs a signal disch; the signal generation circuit J3 includes an inverter J31, a D flip-flop DFF, and an inverter J32; the input end of the inverter J31 is connected with the GATE end, and the output end is connected with the CK end of the D trigger DFF; the D end of the D trigger DFF is connected with the VCC end, and the R end is connected with the inductive current zero-crossing signal zcd; the input end of the inverter J32 is connected with the Q end of the D trigger DFF, and a signal Non-Tout is output; the sampling circuit J1 comprises a control switch S11, a control switch S12, an energy storage capacitor C13, an operational amplifier G14, a control switch S15, a control switch S16, a filter resistor R17, a filter capacitor C18 and an inverter J19; one end of the control switch S11 is connected with the CS end, the other end is connected with the non-inverting input end of the operational amplifier G14, and the GATE end signal controls the on-off of the control switch S11; one end of the control switch S12 is connected with the positive phase input end of the operational amplifier G14, the other end is grounded, and the signal disch controls the on-off of the control switch S12; one end of the energy storage capacitor C13 is connected with the positive phase input end of the operational amplifier G14, and the other end is grounded; the negative phase input end of the operational amplifier G14 is connected with the output end of the operational amplifier G14; one end of the control switch S15 is connected with the output end of the operational amplifier G14, and the other end is respectively connected with one end of the control switch S16 and one end of the filter resistor R17; the other end of the control switch S16 is grounded; the other end of the filter resistor R17 outputs a signal Vcal-avg; one end of the filter capacitor C18 is connected with the other end of the filter resistor R17, and the other end is grounded; the input end of the inverter J19 is connected with a signal Non-Tout, and the output end controls the on-off of the control switch S15; the signal Non-Tout controls the on-off of the control switch S16; the current algorithm function circuit J4 comprises an operational amplifier EA41, an operational amplifier G42, a current source I43 and a capacitor C44; the positive phase input end of the operational amplifier EA41 is connected with the output signal Vcal-avg of the sampling circuit J1, the negative phase input end is connected with the constant current control reference voltage Vref _ cc, and the output end is connected with the COMP end; the input end of the current source I43 is connected with the VCC end, and the output end is connected with the negative phase input end of the operational amplifier G42; the non-inverting input terminal of the operational amplifier G42 is connected to the COMP terminal, and outputs a constant current control signal norm _ off.
In addition, the invention provides an LED driving chip, which comprises the constant current control circuit K1, a peak current detection circuit K2, a logic control circuit K3, a zero-crossing current detection circuit K4 and an MOS tube driving circuit K5; the input of the constant current control circuit K1 is connected with a CS end and a COMP end, and outputs a constant current control signal norm _ off; the peak current detection circuit K2 detects and limits the peak current of the inductor and outputs a peak current arrival signal Ipk _ off; the zero-crossing current detection circuit K4 detects the zero crossing point of the inductive current and outputs a current zero-crossing signal zcd; the logic control circuit K3 inputs a signal peak current reaching signal Ipk _ off, a signal constant current control signal norm _ off and a current zero-crossing signal zcd and outputs a signal MOS _ ON; the MOS tube driving circuit K5 is connected with the output signal MOS _ ON of the logic control circuit K3, and the output is connected with the GATE end and the zero-crossing current detection circuit K4.
Further, the present invention provides an LED driving chip, which may further have the following features: the low-voltage power supply circuit K6 is also included; the low voltage supply circuit K6 inputs a high voltage from the HV terminal and outputs a low voltage to the Vcc terminal.
Further, the present invention provides an LED driving chip, which may further have the following features: with the GND terminal connected to ground.
In addition, the present invention provides a step-up LED switch driving circuit, comprising: an input capacitor C1, an energy storage capacitor C2, an external capacitor C4, a charging and discharging inductor L1, a diode D2, a switching MOS tube M1, a current detection resistor Rs, an LED load D1, and an LED driving chip T1 as claimed in claim 2; one end of the input capacitor C1 is connected with the direct-current voltage Vin, and the other end is grounded; one end of the charge and discharge inductor L1 is connected with the direct-current voltage Vin, and the other end is connected with the drain electrode of the switch MOS tube M1; the HV end of the LED driving chip T1 is connected with the direct-current voltage Vin; one end of the energy storage capacitor C2 is connected with the Vcc end of the LED driving chip T1, and the other end is grounded; one end of the external capacitor C4 is connected with the COMP end of the LED driving chip T1, and the other end of the external capacitor C4 is grounded; the grid electrode of the switch MOS tube M1 is connected with the Gate end of the LED driving chip T1, and the source electrode is connected with the CS end of the LED driving chip T1; one end of the current detection resistor Rs is connected with the source electrode of the switch MOS transistor M1, and the other end of the current detection resistor Rs is grounded; the anode of the diode D2 is connected with the drain of the switch MOS tube M1, and the cathode is connected with one end of the LED load D1; the other end of the LED load D1 is grounded.
Further, the present invention provides a step-up LED switch driving circuit, which may further have the following features: also included is an output capacitor C3; the output capacitor C3 is connected in parallel across the LED load D1.
Further, the present invention provides a step-up LED switch driving circuit, which may further have the following features: the GND terminal of the LED driving chip T1 is grounded.
Drawings
Fig. 1 is a circuit diagram of a boost LED switch driving circuit according to the present invention.
Fig. 2 is a waveform diagram of the operation of the boost LED switch driving circuit according to the present invention.
Fig. 3 is a circuit diagram of an LED driving chip according to the present invention.
Fig. 4 is a circuit diagram of the signal generation circuit J2 in the present invention.
Fig. 5 is a circuit diagram of the signal generation circuit J3 in the present invention.
Fig. 6 is a circuit diagram of the sampling circuit J1 in the present invention.
Fig. 7 is a circuit diagram of the current algorithm function circuit J4 in the present invention.
Fig. 8 is a waveform diagram in the present invention.
Reference numerals:
rs-current detection resistor
L1-Charge and discharge inductor
M1-switching MOS tube
D1-LED load
D2-free wheel diode
Iout-LED load output current
Vin-input rectified voltage
Im-current of inductor L1
Is-charging current of inductor L1
Id-discharge current of inductor L1
Im-current of inductor L1
Vcs-Voltage across Current sense resistor Rs
Id-discharge current of inductor L1
Vgate-MOS transistor M1 grid voltage
Im _ pk-inductance L1 peak current
Vcs _ pk-peak voltage of Vcs
Ton-inductor L1 charging time
Tdis-discharge time of inductor L1
Tdisc-time for inductor L1 to have a current of 0
T-switching cycle time
Gate signal of Gate-MOS transistor M1
MOS _ ON-output signal of logic control circuit K3
drn-drain of MOS transistor M1
zcd-zero crossing signal of inductive current
Ipk _ off-peak current arrival signal
norm _ off-constant current control circuit output signal
Vcs-Voltage across Current sense resistor Rs
Vgate-MOS transistor M1 grid voltage
zcd-detection signal of zero crossing point of inductive current
G14-operational amplifier
C13-energy storage capacitor
C17-filter capacitor
R18-filter resistance
Vm-voltage of the capacitor Cs
Vcal-peak voltage of Vcs when MOS transistor M1 is turned off
Vcal _ avg-Vcal average voltage
Vref _ cc-constant current control reference voltage
The specific implementation mode is as follows:
the invention is further described below with reference to the following figures and specific examples.
Fig. 1 is a circuit diagram of a boost LED switch driving circuit according to the present invention.
As shown in fig. 1, a boost LED switch driving circuit includes a rectifier bridge, an input capacitor C1, an energy storage capacitor C2, an external capacitor C4, a charging/discharging inductor L1, a freewheeling diode D2, a switching MOS transistor M1, a current detection resistor Rs, an LED load D1, an output capacitor C3, and an LED driving chip T1. The LED driving chip T1 has an HV terminal, a Vcc terminal, a COMP terminal, a DIM terminal, a Gate terminal, a CS terminal, and a GND terminal.
The ac input ACin is rectified to output a dc voltage Vin. One end of the input capacitor C1 is connected to the dc voltage Vin, and the other end is connected to ground. One end of the charge and discharge inductor L1 is connected to the DC voltage Vin, and the other end is connected to the drain of the switch MOS transistor M1. The HV terminal of the LED driving chip T1 is connected to the dc voltage Vin. One end of the energy storage capacitor C2 is connected with the Vcc end of the LED driving chip T1, and the other end is grounded. One end of the external capacitor C4 is connected to the COMP end of the LED driving chip T1, and the other end is grounded. The Gate of the switching MOS transistor M1 is connected to the Gate of the LED driving chip T1, and the source is connected to the CS terminal of the LED driving chip T1. One end of the current detection resistor Rs is connected with the source electrode of the switch MOS transistor M1, and the other end is grounded. The anode of the freewheeling diode D2 is connected to the drain of the switching MOS transistor M1, and the cathode is connected to one end of the LED load D1. The other end of the LED load D1 is grounded. The output capacitor C3 is connected in parallel across the LED load D1. The GND terminal of the LED driving chip T1 is grounded, and the DIM terminal is suspended.
The LED driving chip T1 and external components form a boost LED switch driving circuit for providing a constant current output to the LED load D1. The ac input is rectified and filtered by an input capacitor C1 to generate a dc voltage Vin for powering the LED load. COMP termination to external capacitor C4 provides loop compensation for constant current control. The Gate of the external switching MOS transistor M1 is driven by the Gate of the LED driving chip T1. Since the charging and discharging inductor L1 supplies current to the LED load D1 only when the switching MOS transistor M1 Is turned off, the current Is flowing through the current detection resistor Rs Is only the charging current of the input power source to the charging and discharging inductor L1, and the true load current Iout Is the average value of the discharging current Id of the charging and discharging inductor L1 to the LED load D1.
Fig. 3 is a circuit diagram of an LED driving chip according to the present invention.
As shown in fig. 3, in order to indirectly obtain the information of Iout by detecting Is, the present invention establishes a constant current control circuit in the LED driving chip T1, so that the output current can be accurately controlled by detecting Is in real time, and reliable and stable constant current control Is achieved.
The LED driving chip includes: the circuit comprises a constant current control circuit K1, a peak current detection circuit K2, a logic control circuit K3, a zero-cross current detection circuit K4, a MOS tube driving circuit K5 and a low-voltage power supply circuit K6.
The low-voltage power supply circuit K6 inputs high voltage from the HV end, outputs low voltage to the Vcc end, and stores the energy in the external capacitor C4 to supply power to other functional modules inside the LED driving chip (all modules are connected with VCC by default). The peak current detection circuit K2 detects and limits the peak current of the inductor, and outputs a peak current arrival signal Ipk _ off. The zero-crossing current detection circuit K4 detects the zero crossing of the inductor current and outputs a current zero-crossing signal zcd. The input of the constant current control circuit K1 is connected to the CS terminal and the COMP terminal, and outputs a constant current control signal norm _ off. The logic control circuit K3 inputs a signal peak current reaching signal Ipk _ off, a signal constant current control signal norm _ off and a current zero-crossing signal zcd and outputs a signal MOS _ ON; the switching state of the MOS transistor M1 is determined to achieve the purpose of constant voltage output. The MOS tube driving circuit K5 is connected with the output signal MOS _ ON of the logic control circuit K3, and the output is connected with the GATE end and the zero-crossing current detection circuit K4. And the GND end of the LED driving chip is grounded.
The constant current control circuit K1 includes: a sampling circuit J1, a signal generation circuit J2, a signal generation circuit J3, and a current algorithm function circuit J4.
As shown in fig. 4, the signal generation circuit J2 includes a Delay, an inverter J21, an and gate J22, and an RS flip-flop J23. The input end of the delayer is connected with the GATE end, and the output end of the delayer is connected with the input end of the inverter J21; one input end of the AND GATE J22 is connected with the output end of the inverter J21, the other input end is connected with the GATE end, and the output end is connected with the R end of the RS trigger J23; the S end of the RS trigger J23 is connected with an inductor current zero-crossing signal zcd, and the Q end of the RS trigger J23 outputs a signal disch.
As shown in fig. 5, the signal generation circuit J3 includes an inverter J31, a D flip-flop DFF, and an inverter J32. The input end of the inverter J31 is connected with the GATE end, and the output end is connected with the CK end of the D trigger DFF; the D end of the D trigger DFF is connected with the VCC end, and the R end is connected with the inductive current zero-crossing signal zcd; the input end of the inverter J32 is connected with the Q end of the D trigger DFF, and the signal Non-Tout is output.
As shown in fig. 6, the sampling circuit J1 includes: the control circuit comprises a control switch S11, a control switch S12, an energy storage capacitor C13, an operational amplifier G14, a control switch S15, a control switch S16, a filter resistor R17, a filter capacitor C18 and an inverter J19. One end of the control switch S11 is connected with the CS end, the other end is connected with the non-inverting input end of the operational amplifier G14, and the GATE end signal controls the on-off of the control switch S11; one end of the control switch S12 is connected with the positive phase input end of the operational amplifier G14, the other end is grounded, and the signal disch controls the on-off of the control switch S12; one end of the energy storage capacitor C13 is connected with the positive phase input end of the operational amplifier G14, and the other end is grounded; the negative phase input end of the operational amplifier G14 is connected with the output end of the operational amplifier G14; one end of the control switch S15 is connected with the output end of the operational amplifier G14, and the other end is respectively connected with one end of the control switch S16 and one end of the filter resistor R17; the other end of the control switch S16 is grounded; the other end of the filter resistor R17 outputs a signal Vcal-avg; one end of the filter capacitor C18 is connected with the other end of the filter resistor R17, and the other end is grounded; the input end of the inverter J19 is connected with a signal Non-Tout, and the output end controls the on-off of the control switch S15; the signal Non-Tout controls the on/off of the control switch S16.
As shown in fig. 7, the current algorithm function circuit J4 includes an operational amplifier EA41, an operational amplifier G42, a current source I43, and a capacitor C44. The positive phase input end of the operational amplifier EA41 is connected with the output signal Vcal-avg of the sampling circuit J1, the negative phase input end is connected with the constant current control reference voltage Vref _ cc, and the output end is connected with the COMP end; the input end of the current source I43 is connected with the VCC end, and the output end is connected with the negative phase input end of the operational amplifier G42; the non-inverting input terminal of the operational amplifier G42 is connected to the COMP terminal, and outputs a constant current control signal norm _ off.
The signal generation circuits J2 and J3 function to generate signals disch and Non-Tout and output the signals to the sampling circuit J1. The sampling circuit is used for processing the voltage Vcs at two ends of the current detection resistor Rs into a voltage signal which can represent output current, and the specific process is as follows: 1. the switches S11 and S12 are controlled by the signals Gate and disch, and the peak voltage of Vcs is sampled and stored in the capacitor C13 (Vm) when the MOS transistor M1 is turned on. 2. The Vm voltage is changed into a Vcs peak voltage Vcal when the MOS tube M1 is turned off by the operational amplifier G14 and the switches S15 and S16 controlled by the signal Non-Tout. 3. The average value of Vcal voltage, Vcal _ avg, is generated by resistor R17 and capacitor C18. The voltage signal Vcal _ avg that the current algorithm function circuit can really represent the output current is extracted from Vcs, and the voltage value is as follows:
the relationship between the Vcal _ avg signal and the output current can thus be established as:
by detecting the Vcal _ avg signal, the constant current output control of the boost LED switch driving scheme is achieved.
While the present invention has been described in detail with reference to the preferred embodiments, it should be understood that the above description should not be taken as limiting the invention. Various modifications and alterations to this invention will become apparent to those skilled in the art upon reading the foregoing description. Any invention creation, insubstantial replacement, change or modification without departing from the spirit of the invention falls within the protection scope of the invention.
Claims (7)
1. A constant current control circuit is characterized in that: the current-sampling circuit comprises a sampling circuit J1, a signal generating circuit J2, a signal generating circuit J3 and a current algorithm function circuit J4;
the signal generating circuit J2 comprises a Delay, an inverter J21, an AND gate J22 and an RS trigger J23;
the input end of the delayer is connected with the GATE end, and the output end of the delayer is connected with the input end of the inverter J21; one input end of the AND GATE J22 is connected with the output end of the inverter J21, the other input end is connected with the GATE end, and the output end is connected with the R end of the RS trigger J23; an S end of the RS trigger J23 is connected with an inductive current zero-crossing signal zcd, and a Q end outputs a signal disch;
the signal generation circuit J3 includes an inverter J31, a D flip-flop DFF, and an inverter J32;
the input end of the inverter J31 is connected with the GATE end, and the output end is connected with the CK end of the D trigger DFF; the D end of the D trigger DFF is connected with the VCC end, and the R end is connected with the inductive current zero-crossing signal zcd; the input end of the inverter J32 is connected with the Q end of the D trigger DFF, and a signal Non-Tout is output;
the sampling circuit J1 comprises a control switch S11, a control switch S12, an energy storage capacitor C13, an operational amplifier G14, a control switch S15, a control switch S16, a filter resistor R17, a filter capacitor C18 and an inverter J19;
one end of the control switch S11 is connected with the CS end, the other end is connected with the non-inverting input end of the operational amplifier G14, and the GATE end signal controls the on-off of the control switch S11; one end of the control switch S12 is connected with the positive phase input end of the operational amplifier G14, the other end is grounded, and the signal disch controls the on-off of the control switch S12; one end of the energy storage capacitor C13 is connected with the positive phase input end of the operational amplifier G14, and the other end is grounded; the negative phase input end of the operational amplifier G14 is connected with the output end of the operational amplifier G14; one end of the control switch S15 is connected with the output end of the operational amplifier G14, and the other end is respectively connected with one end of the control switch S16 and one end of the filter resistor R17; the other end of the control switch S16 is grounded; the other end of the filter resistor R17 outputs a signal Vcal-avg; one end of the filter capacitor C18 is connected with the other end of the filter resistor R17, and the other end is grounded; the input end of the inverter J19 is connected with a signal Non-Tout, and the output end controls the on-off of the control switch S15; the signal Non-Tout controls the on-off of the control switch S16;
the current algorithm function circuit J4 comprises an operational amplifier EA41, an operational amplifier G42, a current source I43 and a capacitor C44;
the positive phase input end of the operational amplifier EA41 is connected with the output signal Vcal-avg of the sampling circuit J1, the negative phase input end is connected with the constant current control reference voltage Vref _ cc, and the output end is connected with the COMP end; the input end of the current source I43 is connected with the VCC end, and the output end is connected with the negative phase input end of the operational amplifier G42; the non-inverting input terminal of the operational amplifier G42 is connected to the COMP terminal, and outputs a constant current control signal norm _ off.
2. An LED driver chip, its characterized in that:
the constant current control circuit K1, the peak current detection circuit K2, the logic control circuit K3, the zero-crossing current detection circuit K4 and the MOS tube driving circuit K5 are included according to claim 1;
the input of the constant current control circuit K1 is connected with a CS end and a COMP end, and outputs a constant current control signal norm _ off;
the peak current detection circuit K2 detects and limits the peak current of the inductor and outputs a peak current arrival signal Ipk _ off;
the zero-crossing current detection circuit K4 detects the zero crossing point of the inductive current and outputs a current zero-crossing signal zcd;
the logic control circuit K3 inputs a signal peak current reaching signal Ipk _ off, a signal constant current control signal norm _ off and a current zero-crossing signal zcd and outputs a signal MOS _ ON;
the MOS tube driving circuit K5 is connected with the output signal MOS _ ON of the logic control circuit K3, and the output is connected with the GATE end and the zero-crossing current detection circuit K4.
3. The LED driving chip of claim 2, wherein:
the low-voltage power supply circuit K6 is also included; the low voltage supply circuit K6 inputs a high voltage from the HV terminal and outputs a low voltage to the Vcc terminal.
4. The LED driving chip of claim 2, wherein: with the GND terminal connected to ground.
5. A step-up LED switch driving circuit is characterized in that:
the LED driving circuit comprises an input capacitor C1, an energy storage capacitor C2, an external capacitor C4, a charging and discharging inductor L1, a diode D2, a switching MOS tube M1, a current detection resistor Rs, an LED load D1 and an LED driving chip T1 as claimed in claim 2;
one end of the input capacitor C1 is connected with the direct-current voltage Vin, and the other end is grounded;
one end of the charge and discharge inductor L1 is connected with the direct-current voltage Vin, and the other end is connected with the drain electrode of the switch MOS tube M1;
the HV end of the LED driving chip T1 is connected with the direct-current voltage Vin;
one end of the energy storage capacitor C2 is connected with the Vcc end of the LED driving chip T1, and the other end is grounded;
one end of the external capacitor C4 is connected with the COMP end of the LED driving chip T1, and the other end of the external capacitor C4 is grounded;
the grid electrode of the switch MOS tube M1 is connected with the Gate end of the LED driving chip T1, and the source electrode is connected with the CS end of the LED driving chip T1;
one end of the current detection resistor Rs is connected with the source electrode of the switch MOS transistor M1, and the other end of the current detection resistor Rs is grounded;
the anode of the diode D2 is connected with the drain of the switch MOS tube M1, and the cathode is connected with one end of the LED load D1;
the other end of the LED load D1 is grounded.
6. A boost LED switch driver circuit according to claim 5, wherein:
also included is an output capacitor C3; the output capacitor C3 is connected in parallel across the LED load D1.
7. A boost LED switch driver circuit according to claim 5, wherein:
the GND terminal of the LED driving chip T1 is grounded.
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|---|---|---|---|---|
| TWI384171B (en) * | 2010-01-05 | 2013-02-01 | Richtek Technology Corp | Thermal foldback control for a light-emitting diode |
| CN103648202B (en) * | 2013-12-18 | 2017-02-08 | 矽力杰半导体技术(杭州)有限公司 | Active power factor correction control circuit, chip and LED (Light Emitting Diode) drive circuit |
| CN206365079U (en) * | 2016-12-06 | 2017-07-28 | 上海灿瑞科技股份有限公司 | The LED drive chip and circuit of a kind of compatible lead and trail edge light modulator |
| CN108093528B (en) * | 2018-01-10 | 2024-03-26 | 上海灿瑞科技股份有限公司 | Overvoltage protection circuit applied to LED driving chip |
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2019
- 2019-04-19 CN CN201910317717.1A patent/CN110035580B/en active Active
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