CN109546861A - A kind of method of LLC cavity voltage conversion ratio dynamic regulation - Google Patents
A kind of method of LLC cavity voltage conversion ratio dynamic regulation Download PDFInfo
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- CN109546861A CN109546861A CN201811413656.0A CN201811413656A CN109546861A CN 109546861 A CN109546861 A CN 109546861A CN 201811413656 A CN201811413656 A CN 201811413656A CN 109546861 A CN109546861 A CN 109546861A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention discloses a kind of method of LLC cavity voltage conversion ratio dynamic regulation, the LLC resonant cavity includes resonant capacitance 1, magnetic integrated transformer 2 and switch control inductance 3；Switch control inductance 3 is in series by linear inductance 3-1, power switch tube 3-2 and power switch tube 3-3, and wherein the source electrode of power switch tube 3-2 is connected with the source electrode of power switch tube 3-3, constitutes a two-way full control switch；The switch control inductance 3 is in parallel with the secondary windings of magnetic integrated transformer 2；A kind of method of LLC cavity voltage conversion ratio dynamic regulation proposed by the invention, the switching sequence of two power switch tubes in inductance 3 is controlled by control switch, can voltage conversion ratio to resonant cavity carry out dynamic regulation, realize that LLC resonant converter keeps high efficiency in wide output voltage range application and can significantly improve light-load efficiency.
Description
Technical field
The present invention relates to power electronic technique and its application fields, more particularly to this needs such as similar battery chargers
Width funtion output area, efficient LLC resonant converter.
Background technique
LLC resonant converter is a kind of Inductivity-Inductivity-capacitance series resonance DC-DC converter, master power switch device
Part can realize that zero-current switching may be implemented in Zero-voltage soft switch, secondary commutation diode with full-load range, and voltage stress is small,
Output does not need filter inductance, therefore complete machine conversion efficiency is high, and small in size, power density is big, obtains research extensively and application.
LLC resonant converter can obtain greater efficiency, on condition that LLC resonant converter work is attached in resonant frequency point
Closely.When LLC resonance frequency off-resonance point, the efficiency of converter can be reduced.Therefore in the application of some wide output voltage ranges
In (such as electric car charge power supply), it is desirable that LLC resonant cavity has biggish voltage conversion ratio adjustable range, such case
Under, LLC is difficult to obtain satisfactory complete machine overall efficiency, especially light-load efficiency.
LLC resonant converter adjusts output power by change frequency, when controlled resonant converter work is converted in unit voltage
When the resonant frequency point of rate, conduction loss and switching loss are minimum, can obtain high efficiency.But to adapt to wide output voltage range
With the requirement of load variation, the working frequency of LLC resonant converter can a wide range of off-resonance frequency.To realize high voltage conversion
Rate, working frequency need to be less than resonance frequency, and the low-limit frequency of LLC resonant converter is an important indicator of Design of Transformer,
Too low lowest operating frequency causes magnetic core of transformer volume to increase, and reduces power density and efficiency.To realize that low-voltage turns
Rate is changed, working frequency need to be greater than resonance frequency, and primary switching devices turn-off power loss increases, and secondary commutation diode loses ZCS spy
Property, cause efficiency quickly to reduce.Voltage conversion ratio resonant cavity circulation is other than resonator parameter, also by the shadow of load resistance
It rings, so, the load dependence and wide output voltage range of LLC resonant converter require so that LLC Resonator design becomes tired
It is difficult and complicated.Meeting voltage conversion ratio adjustable range, then LLC resonant converter light-load efficiency reduces, light-load efficiency is optimized,
Then in identical frequency variation range, the voltage conversion ratio adjustable range of LLC resonant converter is difficult to meet.
Document " Double-Phase High-Efficiency, Wide Load Range High-Voltage Low-
Voltage LLC DCDC Converter forElectric HybridVehicles》(IEEE Transactions
OnPower Electronics, 2015,30 (4), 1876-1886) LLC resonant cavity magnetizing inductance is analyzed to resonant cavity conducting
The turn-off power loss of loss and main switch is analyzed, it is indicated that biggish magnetizing inductance can reduce conduction loss and main switch
The turn-off power loss of pipe, therefore be conducive to improve the overall efficiency of converter under light condition using big magnetizing inductance.But it is small
Magnetizing inductance LLC resonant converter can be made to obtain wider output voltage adjustable range.The design of traditional LLC controlled resonant converter
In, magnetizing inductance parameter is not adjustable after circuit hardware determines.In order to realize the adjusting of magnetizing inductance, document
《Light-Load Efficiency Improvement Strategy forLLC Resonant Converter
Utilizing a Step-Gap Transformer》(2014International Power Electronics
Conference (IPEC-Hiroshima 2014-ECCEASIA), 2014, pp.1734-1737.) by magnetic core of transformer
Stepping air gap is used on center pillar, obtains biggish magnetizing inductance at light load, and magnetizing inductance reduces when overloaded, is guaranteeing to export with this
LLC resonant converter light-load efficiency is improved under the premise of voltage regulation limits.But the variation of this method magnetizing inductance is non-linear
And it is uncontrollable, and processing stepping air gap leads to increased costs.Document " LLC Resonant Converter for
Electric Vehicle Battery Chargers》(IET PowerElectronics,2016,9,(12),pp.2369-
2376) realize two transformers connected in parallel work using a two-way power switch device: two-way switch is connected when overloaded, two changes
The work of depressor primary parallel, resonant cavity magnetizing inductance is smaller, meets voltage gain requirement.Switch disconnects at light load, only one
Transformer work, resonant cavity magnetizing inductance is larger, reduces primary conduction loss and switching loss, improves light-load efficiency.But resonance
Inductance can not be integrated in transformer, and volume is caused to increase, and magnetizing inductance can only switch between two fixed, flexible adjustment
Spend not good enough, only one transformer works at light load, another transformer is idle, and devices use rate is not high.
The present invention gives a kind of methods of LLC cavity voltage conversion ratio dynamic regulation, realize LLC resonant cavity excitation
Inductance continuously adjusts, and can be with the transformation of loading condition by software dynamic regulation, thus with a kind of very flexible side
Just mode solves the problems, such as that aforementioned magnetizing inductance adjusting is not easy, and realizes the dynamic regulation of LLC cavity voltage conversion ratio,
And optimize overall efficiency of the LLC resonant converter in entire loading range.
Summary of the invention
The technical problem to be solved by the present invention is to provide a kind of control of LLC resonant cavity magnetizing inductance programmable regulating
Method, since the ratio of magnetizing inductance and resonant inductance has adjustment effect to voltage conversion ratio, it is achieved that cavity voltage
The Programmable Dynamic of conversion ratio is adjusted, and is that LLC resonant converter is a kind of completely new using providing in wide output voltage range
Method is conducive to LLC resonant converter and expands output voltage range and improve light-load efficiency.
In order to solve the above technical problems, the technical scheme adopted by the invention is that:
A kind of method of LLC cavity voltage conversion ratio dynamic regulation, it is characterised in that the LLC resonant cavity includes resonance
Capacitor 1, magnetic integrated transformer 2 and switch control inductance 3；Switch control inductance 3 by linear inductance 3-1, power switch tube 3-2 and
Power switch tube 3-3 is in series, and wherein the source electrode of power switch tube 3-2 is connected with the source electrode of power switch tube 3-3, constitutes one
A two-way full control switch；The switch control inductance 3 is in parallel with the secondary windings of magnetic integrated transformer 2.
The method of the LLC cavity voltage conversion ratio dynamic regulation is connected in parallel on magnetic integrated transformer 2 times by adjusting
What the equivalent inductance of the switch control inductance 3 at grade both ends was realized.2 grade both ends paralleling switches of magnetic integrated transformer control inductance 3
Resonant cavity equivalent circuit it is as shown in Figure 2.In figure, CrFor resonant capacitance, LrFor resonant inductance, Lm-iniFor magnetic integrated transformer 2
Magnetizing inductance, a2LSCIIt is transmitted to the equivalent inductance value that primary obtains for equivalent switch inductance, a is that magnetic integrates transformation
The turn ratio of the armature winding of device 2 and secondary set group, ReThe equivalent resistance of magnetic integrated transformer primary is transmitted to for load resistance.
Because work has in high frequency state
Lm-ini> > a2·LSCI (1)
Therefore it can be approximately considered:
Lm-eq≈a2·LSCI (2)
Therefore the original magnetizing inductance L of magnetic integrated transformer 2m-iniCan be larger, not necessarily like biography in magnetic core of transformer magnetic circuit
System LLC resonance transformer places air gap like that, therefore can reduce transformer edge effect, improves transformer efficiency, reduces and becomes
Depressor volume.
The switch control inductance 3 is in series by linear inductance 3-1, power switch tube 3-2 and power switch tube 3-3,
Wherein the source electrode of power switch tube 3-2 is connected with the source electrode of power switch tube 3-3, constitutes a two-way full control switch；It is two-way complete
Control the control driving signal and transformer secondary output winding voltage e of switchABPhase relation it is as shown in Figure 3.Switch control inductance 3 exists
The principle Analysis of one switch periods is as follows: t0Moment, because of eABFor positive polarity, S1It is in an off state, flow through switch
The inductive current for controlling inductance 3 is zero.t1Moment, driving signal make S1Conducting, while S2Shutdown, because of inductance La, electric current iABFrom
Zero linear increase, S1Zero current passing, S2Zero-current switching.t2Moment, transformer secondary output winding voltage eABThe pole reversal, simultaneously
Inductive current iABReach maximum value and then starts linear reduce.t3Moment, inductive current iABIt is reduced to zero, due to S2Reversed resistance
It is disconnected, electric current iABZero is remained, until t4Moment, S1Shutdown, S2Conducting, S1Realize zero-current switching, S2Realize that zero current is led
It is logical.S2After conducting, electric current iABReverse linear increases from zero.t5Moment, transformer secondary output winding voltage eABThe pole reversal, electric current iAB
It inversely increases maximum value and then starts linear reduction, arrive t6Moment is reduced to zero, due to S at this time1Blocking effect, switch control
The electric current i of inductance 3 processedABRemain zero.As it can be seen that in a switch periods, S1And S2It can realize zero current turning-on and zero electricity
Stream shutdown, and S1And S2Conducting resistance very little, therefore switching device S1And S2Switching loss and conduction loss all very littles.
The equivalent inductance of above-mentioned switch control inductance 3 and the relationship of phase angle [alpha] are as follows:
Its graphical representation is as shown in Figure 4, it is seen that the equivalent inductance value of switch control inductance 3 can be in LaWithin the scope of~∞
It adjusts, there is sufficiently wide adjustable range.
Therefore, by formula (2) it is found that the equivalent magnetizing inductance of resonant cavity can be adjusted in a wide range.And excitation
The ratio of inductance and resonant inductance, is defined as k:
Under identical loading condition, different value of K is that the voltage conversion ratio curve of LLC resonant cavity is as shown in Figure 5.As it can be seen that k
It is higher to be worth lesser LLC cavity voltage conversion ratio, and the biggish LLC cavity voltage conversion ratio of k value is lower.Therefore, by public affairs
Formula (4) and formula (2) by the voltage that regulating switch controls the adjustable LLC resonant cavity of equivalent inductance of inductance 3 it is found that converted
Rate, and this adjusting method can be achieved on programmable continuously adjust.
Compared with prior art, the advantageous effect of present invention is that:
The voltage conversion ratio of LLC resonant converter can by being connected in parallel on the progress of switch control inductance 3 at secondary windings both ends
Programming is adjusted, magnetizing inductance required for can adjusting according to the special circumstances of different loads, to realize voltage conversion ratio
It adjusts, and the conduction loss and switching loss of optimal cavity, optimizes light-load efficiency；Relative to swashing for traditional switch great-jump-forward
Magnetic adjustment of inductance, the present invention are that LLC resonant converter provides a kind of completely new control under Width funtion conversion ratio application environment
Adjusting method.
Detailed description of the invention
It in order to more clearly explain the embodiment of the invention or the technical proposal in the existing technology, below will be to institute in embodiment
Attached drawing to be used is needed to be briefly described, it should be apparent that, the accompanying drawings in the following description is only some implementations of the invention
Example, for those of ordinary skill in the art, without any creative labor, can also be according to these attached drawings
Obtain other attached drawings.
Fig. 1 is the principle of resonant cavity in a kind of method of LLC cavity voltage conversion ratio dynamic regulation of the embodiment of the present invention
Figure；
Fig. 2 is the equivalent circuit diagram of LLC resonant cavity in the embodiment of the present invention；
Fig. 3 is the circuit structure and work wave schematic illustration that switch controls inductance 3；
Fig. 4 is that switch controls the phase angle of inductance 3 and the graph of relation of equivalent inductance；
Fig. 5 is the analogous diagram of different value of K of embodiment of the present invention LLC cavity voltage conversion ratio；
Fig. 6 is electric current in switch control inductance with the schematic diagram of phase angle variations.
Specific embodiment
With reference to the accompanying drawing, technical solution of the present invention is described in detail.
Following will be combined with the drawings in the embodiments of the present invention, and technical solution in the embodiment of the present invention carries out clear, complete
Site preparation description, it is clear that described embodiments are only a part of the embodiments of the present invention, instead of all the embodiments.It is based on
Embodiment in the present invention, it is obtained by those of ordinary skill in the art without making creative efforts every other
Embodiment shall fall within the protection scope of the present invention.
The purpose of the present invention is
For LLC resonant converter when resonant frequency point works, voltage conversion ratio is unrelated with load resistance, conversion efficiency
Height, electromagnetic interference is small, and power density is big, therefore in the application of the constant voltage outputs such as communication power supply, server power supply, TV set power
Field can obtain unusual application.But it is needing to need wide output voltage variation range in electric car charge power supply etc.
In, since LLC resonant converter is to realize that voltage conversion ratio is adjusted by changing frequency, so working frequency cannot
It is constant in resonance frequency, cause the odds for effectiveness of LLC resonant converter that cannot fully demonstrate.Often in voltage in traditional design
Compromise between regulation and light-load efficiency, technically this selection for being mainly reflected in LLC resonant cavity magnetizing inductance parameter
On.Biggish magnetizing inductance can optimize light-load efficiency, but voltage conversion ratio adjustable range is in identical frequency variation range
It is to reduce, and lesser magnetizing inductance can increase voltage conversion ratio adjustable range, but light-load efficiency is lower.If excitation is electric
Sense dynamic adjusting then can solve this problem, and the present invention has then well solved this problem.
To achieve the above object, the present invention provides following schemes:
A kind of method of LLC cavity voltage conversion ratio dynamic regulation, the schematic diagram of resonant cavity are as shown in Figure 1.Its feature
It is that the LLC resonant cavity includes resonant capacitance 1, magnetic integrated transformer 2 and switch control inductance 3；Switch control inductance 3 is by line
Property inductance 3-1, power switch tube 3-2 and power switch tube 3-3 are in series, wherein the source electrode and power of power switch tube 3-2
The source electrode of switching tube 3-3 connects, and constitutes a two-way full control switch；Time of the switch control inductance 3 and magnetic integrated transformer 2
Grade winding parallel.
The method of the LLC cavity voltage conversion ratio dynamic regulation is connected in parallel on magnetic integrated transformer 2 times by adjusting
What the equivalent inductance of the switch control inductance 3 at grade both ends was realized.2 grade both ends paralleling switches of magnetic integrated transformer control inductance 3
Resonant cavity equivalent circuit it is as shown in Figure 2.In figure, CrFor resonant capacitance, LrFor resonant inductance, Lm-iniFor magnetic integrated transformer 2
Magnetizing inductance, a2LSCIIt is transmitted to the equivalent inductance value that primary obtains for equivalent switch inductance, a is that magnetic integrates transformation
The turn ratio of the armature winding of device 2 and secondary set group, ReThe equivalent resistance of magnetic integrated transformer primary is transmitted to for load resistance.
Because work has in high frequency state
Lm-ini> > a2·LSCI (1)
Therefore it can be approximately considered:
Lm-eq≈a2·LSCI (2)
Therefore the original magnetizing inductance L of magnetic integrated transformer 2m-iniCan be larger, not necessarily like biography in magnetic core of transformer magnetic circuit
System LLC resonance transformer places air gap like that, therefore can reduce transformer edge effect, improves transformer efficiency, reduces and becomes
Depressor volume.
The switch control inductance 3 is in series by linear inductance 3-1, power switch tube 3-2 and power switch tube 3-3,
Wherein the source electrode of power switch tube 3-2 is connected with the source electrode of power switch tube 3-3, constitutes a two-way full control switch；It is two-way complete
Control the control driving signal and transformer secondary output winding voltage e of switchABPhase relation it is as shown in Figure 3.Switch control inductance 3 exists
The principle Analysis of one switch periods is as follows: t0Moment, because of eABFor positive polarity, S1It is in an off state, flow through switch
The inductive current for controlling inductance 3 is zero.t1Moment, driving signal make S1Conducting, while S2Shutdown, because of inductance La, electric current iABFrom
Zero linear increase, S1Zero current passing, S2Zero-current switching.t2Moment, transformer secondary output winding voltage eABThe pole reversal, simultaneously
Inductive current iABReach maximum value and then starts linear reduce.t3Moment, inductive current iABIt is reduced to zero, due to S2Reversed resistance
It is disconnected, electric current iABZero is remained, until t4Moment, S1Shutdown, S2Conducting, S1Realize zero-current switching, S2Realize that zero current is led
It is logical.S2After conducting, electric current iABReverse linear increases from zero.t5Moment, transformer secondary output winding voltage eABThe pole reversal, electric current iAB
It inversely increases maximum value and then starts linear reduction, arrive t6Moment is reduced to zero, due to S at this time1Blocking effect, switch control
The electric current i of inductance 3 processedABRemain zero.As it can be seen that in a switch periods, S1And S2It can realize zero current turning-on and zero electricity
Stream shutdown, and S1And S2Conducting resistance very little, therefore switching device S1And S2Switching loss and conduction loss all very littles.
The equivalent inductance of above-mentioned switch control inductance 3 and the relationship of phase angle [alpha] are as follows:
Its graphical representation is as shown in Figure 4, it is seen that the equivalent inductance value of switch control inductance 3 can be in LaWithin the scope of~∞
It adjusts, there is sufficiently wide adjustable range.With the variation of phase angle [alpha], the current waveform and the phase that are flowed through in switch control inductance 3
The relation schematic diagram of parallactic angle α is as shown in Figure 6.When α=pi/2, the equivalent inductance L of switch control inductanceSCI=La, flow through switch
The electric current for controlling inductance 3 is triangular wave；As α=π, LSCI=∞, switch control inductance 3 are equivalent to open circuit.
Therefore, by formula (2) it is found that the equivalent magnetizing inductance of resonant cavity can be adjusted in a wide range.And excitation
The ratio of inductance and resonant inductance, is defined as k:
Under identical loading condition, different value of K is that the voltage conversion ratio curve of LLC resonant cavity is as shown in Figure 5.As it can be seen that k
It is higher to be worth lesser LLC cavity voltage conversion ratio, and the biggish LLC cavity voltage conversion ratio of k value is lower.Therefore, by public affairs
Formula (4) and formula (2) by the voltage that regulating switch controls the adjustable LLC resonant cavity of equivalent inductance of inductance 3 it is found that converted
Rate, and this adjusting method can be achieved on programmable continuously adjust.
According to required voltage slew rate requirement and lowest operating frequency, by Fig. 5, determine that minimum k value is kmin, resonant cavity
It is equivalent minimum magnetizing inductance be
Lm-eq-min=kmin·Lr (5)
Resonant cavity maximum magnetizing inductance is Lm-eq-max, value are as follows:
In formula, Lm1For maximum magnetizing inductance amount needed for realization ZVS under idle condition, tdeadIt is dead for resonant cavity main switch
Area's time, CHBFor the total equivalent capacity of bridge arm, Vo(min)For output voltage minimum value, Vin(max)For input voltage maximum value,
GDC(max)For cavity voltage conversion ratio maximum value, Ts(min)For minimum switch periods；Lm2It is required by guaranteeing under low-limit frequency
Maximum gain needed for maximum magnetizing inductance amount, frFor resonant frequency, Ts(max)For maximum switch periods.Lm-eq-max
Take Lm1And Lm2In that lesser value.
By stating above, a kind of method of LLC cavity voltage conversion ratio dynamic regulation proposed by the invention has following
Several advantages:
1, the magnetizing inductance of magnetic integrated transformer 2 can be very big, so being like that obtain not necessarily like traditional LLC resonance transformer
The size for obtaining suitable air gap needed for suitable magnetizing inductance calculates, reduces design difficulty and processing cost, while also disappearing substantially
In addition to edge effect, transformer energy transmission efficiency is improved；
2, the switch control inductance 3 for being connected in parallel on transformer secondary output can be with flexible modulation equivalent inductance, in the design may be used
Flexibly according to the equivalent magnetizing inductance of suitable resonant cavity required for loading condition selection, to optimize LLC resonant converter
Efficiency: when overloaded, selecting lesser equivalent magnetizing inductance to meet voltage slew rate requirement, select larger magnetizing inductance at light load,
Improve light-load efficiency.
Claims (9)
1. a kind of method of LLC cavity voltage conversion ratio dynamic regulation, it is characterised in that the LLC resonant cavity includes resonance electricity
Hold 1, magnetic integrated transformer 2 and switch control inductance 3；Switch control inductance 3 is by linear inductance 3-1, power switch tube 3-2 and function
Rate switching tube 3-3 is in series, and wherein the source electrode of power switch tube 3-2 is connected with the source electrode of power switch tube 3-3, constitutes one
Two-way full control switch；The switch control inductance 3 is in parallel with the secondary windings of magnetic integrated transformer 2.
2. a kind of method of LLC cavity voltage conversion ratio dynamic regulation according to claim 1, which is characterized in that function
The driving signal of rate switching tube 3-2 and power switch tube 3-3 are complementary and do not have dead time, and duty ratio is fixed as 50%, driving
The frequency of signal is identical as the working frequency of LLC resonant cavity.
3. the driving signal of power switch tube 3-2 according to claim 2 and power switch tube 3-3 and transformer secondary output around
The phase difference of group voltage signal is α, and the value range of α is pi/2~π, and the phase of transformer secondary output winding voltage signal is advanced
The phase of driving signal.
4. according to claim 1, the equivalent inductance L of the switch control inductance 3SCIAre as follows:
L in formulaaFor the inductance value of linear inductance 3-1.
5. a kind of method of LLC cavity voltage conversion ratio dynamic regulation according to claim 1, which is characterized in that magnetic
The leakage inductance of integrated transformer is resonant inductance needed for resonant cavity, is not inserted into air gap in magnetic integrated transformer magnetic circuit, magnetic core is equivalent
Magnetic permeability is larger, and magnetizing inductance value is also larger, value Lm-ini,
And meet:
Lm-ini> > a2·LSCI
In formula, μeffFor magnetic circuit Effective permeability, NpFor the number of turns of armature winding, AcIt is long-pending for core cross section, lcFor the length of magnetic path, a
For the turn ratio of primary winding and secondary windings.
6. according to claim 5, the equivalent magnetizing inductance of LLC resonant converter resonant cavity are as follows:
7. a kind of method of LLC cavity voltage conversion ratio dynamic regulation according to claim 1,
It is characterized in that, resonant cavity minimum magnetizing inductance is Lm-eq-min
Lm-eq-min=kmin·Lr
In formula, kminFor the minimum value of the ratio of magnetizing inductance and resonant inductance, LrFor magnetic integrated transformer primary leakage inductance, simultaneously
It is also the resonant inductance of resonant cavity.
8. a kind of method of LLC cavity voltage conversion ratio dynamic regulation according to claim 1, which is characterized in that humorous
Vibration chamber maximum magnetizing inductance is Lm-eq-max
In formula, Lm1For maximum magnetizing inductance amount needed for realization zero voltage switch under idle condition, tdeadFor resonant cavity main switch
Pipe dead time, CHBFor the total equivalent capacity of bridge arm, Vo(min)For output voltage minimum value, Vin(max)For input voltage maximum value,
GDC(max)For cavity voltage conversion ratio maximum value, Ts(min)For minimum switch periods；Lm2It is required by guaranteeing under low-limit frequency
Maximum voltage conversion ratio needed for maximum magnetizing inductance amount, frFor resonant frequency, Ts(max)For maximum switch periods,
Lm-eq-maxTake Lm1And Lm2In smaller value.
9. a kind of method of LLC cavity voltage conversion ratio dynamic regulation according to claim 1, which is characterized in that logical
Overregulate the driving signal of power switch tube 3-2 and power switch tube 3-3 and the phase difference of transformer secondary output winding voltage signal
For α, make the equivalent magnetizing inductance of resonant cavity in Lm-eq-min~Lm-eq-maxSection variation.
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201811413656.0A CN109546861B (en) | 2018-11-26 | 2018-11-26 | Method for dynamically adjusting voltage conversion rate of LLC resonant cavity |
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110896211A (en) * | 2019-11-29 | 2020-03-20 | 深圳市科华恒盛科技有限公司 | Resonant circuit abnormality control circuit, control method and resonant device |
| CN111786583A (en) * | 2020-06-08 | 2020-10-16 | 湖南大学 | High frequency resonance inverter |
Citations (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1585253A (en) * | 2004-06-02 | 2005-02-23 | 燕山大学 | Series resonant high-frequency chain sinusoidal waev inverse power supply circuit |
| CN101412140A (en) * | 2008-11-17 | 2009-04-22 | 江苏科技大学 | Zero-voltage soft switch topological main circuit of arc welding inverter |
| CN101686015A (en) * | 2008-09-23 | 2010-03-31 | 台达电子工业股份有限公司 | Forward-flyback converter with active clamping circuit |
| CN101902129A (en) * | 2010-07-01 | 2010-12-01 | 西安交通大学 | Current-type multi-resonance direct current (DC) converter |
| CN103891123A (en) * | 2011-10-25 | 2014-06-25 | 株式会社村田制作所 | Inverter device |
| CN105207486A (en) * | 2015-09-06 | 2015-12-30 | 南京航空航天大学 | Bidirectional resonance DC converter and control method thereof |
| CN107947587A (en) * | 2017-11-10 | 2018-04-20 | 漳州科华技术有限责任公司 | A kind of high-efficiency constant-flow Width funtion output circuit |
| CN108521177A (en) * | 2018-06-08 | 2018-09-11 | 南京航空航天大学 | Controlled resonant converter regulating device and control method based on additional coupling inductance |
-
2018
- 2018-11-26 CN CN201811413656.0A patent/CN109546861B/en active Active
Patent Citations (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1585253A (en) * | 2004-06-02 | 2005-02-23 | 燕山大学 | Series resonant high-frequency chain sinusoidal waev inverse power supply circuit |
| CN101686015A (en) * | 2008-09-23 | 2010-03-31 | 台达电子工业股份有限公司 | Forward-flyback converter with active clamping circuit |
| CN101412140A (en) * | 2008-11-17 | 2009-04-22 | 江苏科技大学 | Zero-voltage soft switch topological main circuit of arc welding inverter |
| CN101902129A (en) * | 2010-07-01 | 2010-12-01 | 西安交通大学 | Current-type multi-resonance direct current (DC) converter |
| CN103891123A (en) * | 2011-10-25 | 2014-06-25 | 株式会社村田制作所 | Inverter device |
| CN105207486A (en) * | 2015-09-06 | 2015-12-30 | 南京航空航天大学 | Bidirectional resonance DC converter and control method thereof |
| CN107947587A (en) * | 2017-11-10 | 2018-04-20 | 漳州科华技术有限责任公司 | A kind of high-efficiency constant-flow Width funtion output circuit |
| CN108521177A (en) * | 2018-06-08 | 2018-09-11 | 南京航空航天大学 | Controlled resonant converter regulating device and control method based on additional coupling inductance |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110896211A (en) * | 2019-11-29 | 2020-03-20 | 深圳市科华恒盛科技有限公司 | Resonant circuit abnormality control circuit, control method and resonant device |
| CN111786583A (en) * | 2020-06-08 | 2020-10-16 | 湖南大学 | High frequency resonance inverter |
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