CN107612386A - Current mode Simplify matrix converter and its control method for coordinating - Google Patents
Current mode Simplify matrix converter and its control method for coordinating Download PDFInfo
- Publication number
- CN107612386A CN107612386A CN201710777320.1A CN201710777320A CN107612386A CN 107612386 A CN107612386 A CN 107612386A CN 201710777320 A CN201710777320 A CN 201710777320A CN 107612386 A CN107612386 A CN 107612386A
- Authority
- CN
- China
- Prior art keywords
- chopper
- port
- current mode
- output
- matrix
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
Abstract
The present invention relates to a kind of current mode Simplify matrix converter, the converter includes three-phase input power supply, input filter, matrix chopper, high frequency transformer, current mode chopper, output filter and load.Output port R, S, T of three-phase input power supply are corresponding with input port R0, S0, T0 of input filter to be connected；Output port r1, s1, t1 of input filter are correspondingly connected to input side ports r2, s2, t2 of matrix chopper；Primary side port A, B of high frequency transformer correspond to outlet side port A0, B0 of connection matrix chopper, and secondary port a, b of the high frequency transformer are connected to input side ports a0, b0 of current mode chopper；Output port w, v of current mode chopper are connected with input port w0, v0 of output filter respectively, and output port w1, v0 of the output filter are connected with port w2, v2 for loading.Meanwhile the invention also discloses the control method of the converter.Function admirable of the present invention, efficiency high.
Description
Technical field
The present invention relates to electric and electronic technical field, more particularly to current mode Simplify matrix converter and its coordination controlling party
Method.
Background technology
With extensive use of the ion accelerator in each field, more stringent want is it is also proposed to its field power supply performance
Ask.Magnet load has strict demand to its field power supply response speed, to ensure the quick change in magnetic field, meanwhile, it can incite somebody to action
Excess energy quick release in accelerator.Low for traditional magnet power supply power factor, harmonic pollution is big, and energy is unable to bidirectional flow
The problems such as dynamic, need a kind of low-cost high-efficiency badly and " green " magnet power supply of energy-feedback power grid can be realized.
The content of the invention
The technical problems to be solved by the invention are to provide the current mode Simplify matrix conversion of a kind of function admirable, efficiency high
Device.
Another technical problem to be solved by this invention is to provide the coordination control of the current mode Simplify matrix converter
Method.
To solve the above problems, current mode Simplify matrix converter of the present invention, it is characterised in that：The converter bag
Include three-phase input power supply, input filter, matrix chopper, high frequency transformer, current mode chopper, output filter and bear
Carry；Output port R, output port S, output port T and the input filter input port of the three-phase input power supply
R0, input port S0, input port T0 are corresponding to be connected；The output port r1 of the input filter, output port s1, output end
Mouth t1 is correspondingly connected to the input side ports r2 of the matrix chopper, input side ports s2, input side ports t2；The high frequency becomes
Primary side port A, the primary side port B of depressor correspondingly connect the outlet side port A0 of the matrix chopper, outlet side port B0, should
Secondary port a, the secondary port b of high frequency transformer are connected to the input side ports a0 of the current mode chopper, input side ports
b0；Output port w, the output port v of the current mode chopper input port w0 with the output filter, inputs respectively
Port v0 is connected, and output port w1, the output port v0 of the output filter are connected with port w2, the port v2 of the load.
Switch S in the matrix chopperapp、Sann、Sbpp、Sbnn、Scpp、ScnnSubstituted using two-way switch.
The current mode chopper applied voltage two-way type switch includes a full keyholed back plate IGBT S being cascaded1With
One diode D1；The colelctor electrode of the full keyholed back plate is connected with the anode of the diode.
The control method for coordinating of current mode Simplify matrix converter as described above, it is characterised in that：The matrix copped wave
After device uses bipolarity space vector modulating method, according to the synchronizing signal of the matrix chopper and the direction pair of output current
The current mode chopper carries out sending out ripple control.
The bipolarity space vector modulating method comprises the steps：
(1) tactful sector is divided, division principle reaches maximum for the absolute value of a certain phase phase voltage, and with remaining two-phase
Polarity of voltage is opposite；
(2) bipolarity Space vector modulation is carried out：Each traditional switch cycleT s It is divided into two equal half periods, precedingT s / 2 weeks
During the phase, basic vector is synthesized by two effective one zero vectors of vector, rearT s / 2 cycles, basic vector are by precedingT s / 2 weeks
The same zero vector synthesis of the effective vector of phase in the opposite direction, may be such that at oneT s It is opposite that size equidirectional is obtained in cycle
Two vectors；
(3) sector residing for foundation current phasor, before calculatingT s / 2 cycles, effective vector duty cycle are respectivelyd x1 ,d y1 , zero vector accounts for
Empty ratiod 0 =1-d x1 -d y1 ；Before later half period vector usesT s The dutycycle that/2 cycles obtained, i.e.,d x2 = d x1 ,d y2 = d y1 。
The step (1) in whenU sa >0, U sb <0, U sc <It is the first sector when 0；WhenU sa >0, U sb >0, U sc <When 0
For the second sector；WhenU sa <0, U sb >0, U sc <It is the 3rd sector when 0；WhenU sa <0, U sb >0, U sc >It is the 4th fan when 0
Area；WhenU sa <0, U sb <0, U sc >It is the 5th sector when 0；WhenU sa >0, U sb <0, U sc >It is the 6th sector when 0；It is describedU sa 、U sb 、U sc For the three-phase input voltage of the corresponding three-phase input power supply.
The hair ripple control refers to control according to the synchronizing signal of the matrix chopper and the demand of output current：
In energy main story, i.e. output voltageU o More than zero, electric currentI o During more than zero, if the matrix chopper exports synchronizing signal
For just, the high frequency transformer original edge voltage is also for just, then the current mode chopper upper left bridge arm switchs S1 and bottom right bridge arm
It is open-minded to switch S4；If matrix chopper output synchronizing signal is negative, the high frequency transformer original edge voltage be it is negative, then it is described
Current mode chopper upper right bridge arm switchs S2 and lower-left bridge arm switch S3 is open-minded；
In energy afterflow energy regenerative, i.e. output voltageU o Less than zero, electric currentI o During more than zero, if matrix chopper output is synchronous
Signal is just, and now the high frequency transformer original edge voltage is being also for just, then the current mode chopper upper left bridge arm switch S2 and
Bottom right bridge arm switch S3 is open-minded；If the matrix chopper output synchronizing signal is negative, the high frequency transformer original edge voltage is
Negative, then the current mode chopper upper right bridge arm switch S1 and lower-left bridge arm switch S4 are open-minded.
The present invention has advantages below compared with prior art：
1st, current mode Simplify matrix converter (Reduced Matrix Converter, CRMC) of the present invention is a kind of new work(
Rate converter, used topological structure have few conversion series, power density and high conversion efficiency, input and output electrical isolation
And the advantages that energy main story and afterflow energy regenerative, it is suitable for the occasion that direct current need to be provided and require afterflow energy regenerative, such as ion
Accelerator magnet power supply.Meanwhile the present invention has sinusoidal input current, input unity power factor and exports the excellent of Constant Direct Current
Good input and output performance, and possess energy main story and afterflow energy regenerative function, high frequency transformer coupling front stage chopper, realize
Load is isolated with power network, improves security of system.
2nd, CRMC primes matrix converter of the present invention is only achieved that by one-stage transfor-mation is transformed into power frequency ac voltage
High frequency positive negative pulse stuffing voltage, it is easy to rear class high frequency transformer to transmit, relatively conventional converter, eliminates inversion link, simplify
Topological circuit, improve efficiency.
3rd, invention uses front stage coordination control strategy, and prime matrix chopper uses bipolarity space vector
Modulation strategy, rear class current chopping device couple through high frequency transformer with prime matrix chopper, according to prime matrix chopper hair
The synchronizing signal gone out and output current direction, which are realized, coordinates waveform control, and converter can be made to export stable DC, possessing energy just
Pass and afterflow energy regenerative function (one, two quadrant).
4th, control method of the present invention is simple, implements and is easier, more green.
Brief description of the drawings
The embodiment of the present invention is described in further detail below in conjunction with the accompanying drawings.
Fig. 1 is the topological circuit figure of the present invention.
Fig. 2 is common emitter two-way switch schematic diagram of the present invention.
Fig. 3 is that single tube of the present invention adds rectifier bridge two-way switch schematic diagram.
Fig. 4 is inverse parallel two-way switch schematic diagram of the present invention.
Fig. 5 is that four-quadrant of the present invention illustrates schematic diagram.
Fig. 6 is that three-phase input voltage sector of the present invention divides schematic diagram.
Fig. 7 is bipolarity Space Vector Modulation Strategy Vector modulation schematic diagram of the present invention.
Fig. 8 is that bipolarity Vector Modulation strategy dutycycle of the present invention distributes schematic diagram.
Fig. 9 is CRMC rectification stages output voltage turn-on sequence figure of the present invention.
When Figure 10 is CRMC energy main story of the present invention, rear class current mode chopper control waveform.
When Figure 11 is CRMC afterflows energy regenerative of the present invention, rear class current mode chopper control waveform.
Figure 12 is that CRMC inputs phase voltage and phase current waveform.
Figure 13 is CRMC output voltages and current waveform.
Primary voltage of transformer and electric current partial enlargement waveform when Figure 14 is CRMC energy main storys.
The partial enlargement waveform of primary voltage of transformer and electric current when Figure 15 is CRMC afterflow energy regeneratives.
In figure：1-three-phase input power supply；2-input filter；3-matrix chopper；4-high frequency transformer；5-electricity
Flow pattern chopper；6-output filter；7-load.
Embodiment
As shown in figure 1, current mode Simplify matrix converter, the converter include three-phase input power supply 1, input filter 2,
Matrix chopper 3, high frequency transformer 4, current mode chopper 5, output filter 6 and load 7.
Output port R, output port S, output port T and input filter 2 input port of three-phase input power supply 1
R0, input port S0, input port T0 are corresponding to be connected；Output port r1, output port s1, the output port of input filter 2
T1 is correspondingly connected to the input side ports r2 of matrix chopper 3, input side ports s2, input side ports t2；The original of high frequency transformer 4
Side end mouth A, primary side port B correspond to the outlet side port A0 of connection matrix chopper 3, outlet side port B0, the high frequency transformer 4
Secondary port a, secondary port b be connected to the input side ports a0 of current mode chopper 5, input side ports b0；Current mode copped wave
The input port w0 with output filter 6, input port v0's output port w, output port v of device 5 are connected respectively, output filter
Output port w1, the output port v0 of ripple device 6 are connected with port w2, the port v2 of load 7.
Wherein：Switch S in matrix chopper 3app、Sann、Sbpp、Sbnn、Scpp、ScnnSubstituted using two-way switch
（Referring to Fig. 2, Fig. 3 and Fig. 4）.
The applied voltage two-way type of current mode chopper 5 switch includes a full keyholed back plate IGBT S being cascaded1With one
Individual diode D1（Referring to Fig. 5）；The full colelctor electrode of keyholed back plate is connected with the anode of diode.
The control method for coordinating of current mode Simplify matrix converter refers to：Matrix chopper 3 uses bipolarity space vector modulation
After method, current mode chopper 5 is carried out according to the synchronizing signal of matrix chopper 3 and the direction of output current to send out ripple control i.e.
Can.
Bipolarity space vector modulating method comprises the steps：
(1) tactful sector being divided as shown in Figure 6, division principle reaches maximum for the absolute value of a certain phase phase voltage, and with
Remaining two-phase voltage opposite polarity.
Wherein：WhenU sa >0, U sb <0, U sc <It is the first sector when 0；WhenU sa >0, U sb >0, U sc <It is second when 0
Sector；WhenU sa <0, U sb >0, U sc <It is the 3rd sector when 0；WhenU sa <0, U sb >0, U sc >It is the 4th sector when 0；WhenU sa <0, U sb <0, U sc >It is the 5th sector when 0；WhenU sa >0, U sb <0, U sc >It is the 6th sector when 0；U sa 、U sb 、U sc For
The three-phase input voltage of three-phase input power supply 1 corresponding to Fig. 1.
(2) bipolarity Space vector modulation is carried out, as shown in Figure 7：Each traditional switch cycleT s It is divided into two equal half cycles
Phase, precedingT s During/2 cycle, basic vector is synthesized by two effective one zero vectors of vector, rearT s / 2 cycles, basic vector
It is by precedingT s The same zero vector synthesis of the effective vector of/2 cycles in the opposite direction, may be such that at oneT s Size is obtained in cycle
Two opposite vectors of equidirectional.
(3) sector residing for foundation current phasor, before calculatingT s / 2 cycles, effective vector duty cycle are respectivelyd x1 ,d y1 , null vector
Measure dutycycled 0 =1-d x1 -d y1； .Because being high frequency switching, time delay can be ignored substantially, so before later half period vector is availableT s The dutycycle that/2 cycles obtained, i.e.,d x2 = d x1 ,d y2 = d y1 , Fig. 8 is the distribution of bipolarity Space Vector Modulation Strategy dutycycle
Figure.
For example, within each Ts cycles of the 3rd sector, flow path is current phasor successivelyI bc 、I ba 、I bb 、I cb 、I ab 、I bb , whereinI ij Represent electric current byiThe two-way IGBT of bridge arm is flowed into phasejBridge arm two-way switch pipe under phase, such asI bc Then represent two-way opened
CloseS bp （ComprisingS bp 、S pb ）WithS cn （ComprisingS cn 、S nc ）Conducting, residue switch are closed, now the output voltage of matrix chopperU pn =U bc .This sector output voltage order is followed successively byU bc —>U ba —>U bb —>U cb —>U ab —>U bb , as shown in Figure 9.It can similarly derive
Go out whole Switch State Combination in Power Systems and output voltage under remaining five sector.Meanwhile export a square-wave synchronous signal, i.e., precedingT s / 2 cycles exported high level, afterT s / 2 cycles exported low level, and this signal coordinating coordinates rear class to use.
Hair ripple control refers to control according to the synchronizing signal of matrix chopper 3 and the demand of output current：
In energy main story, i.e. output voltageU o More than zero, electric currentI o During more than zero, it is if matrix chopper 3 exports synchronizing signal
Just, the original edge voltage of high frequency transformer 4 is also for just, then the upper left bridge arm switch S1 of current mode chopper 5 and bottom right bridge arm switch S4 are opened
It is logical；If it is negative that matrix chopper 3, which exports synchronizing signal, the original edge voltage of high frequency transformer 4 is negative, the then upper right of current mode chopper 5
Bridge arm switchs S2 and lower-left bridge arm switch S3 is open-minded, as shown in Figure 10；
In energy afterflow energy regenerative, i.e. output voltageU o Less than zero, electric currentI o During more than zero, if matrix chopper 3 exports synchronous letter
Number for just, now the original edge voltage of high frequency transformer 4 is being also for just, then the upper left bridge arm switch S2 of current mode chopper 5 and bottom right bridge arm
It is open-minded to switch S3；If it is negative that matrix chopper 3, which exports synchronizing signal, the original edge voltage of high frequency transformer 4 is negative, then current mode copped wave
The upper right bridge arm of device 5 switchs S1 and lower-left bridge arm switch S4 is open-minded, as shown in figure 11.
High frequency transformer 4 can be made to export stable DC.Matrix chopper 3, current mode chopper 5 coordinate control, Ke Yishi
The two-way flow of existing energy so that circuit works in one, two quadrant（Referring to Fig. 5）.
Simulating, verifying
In order to verify the validity and feasibility of current source type Simplify matrix converter and its control method for coordinating of the present invention,
Simulating, verifying has been carried out under MATLAB/Simulink environment.Simulation process setting is as follows：Preceding 0.5s runs on energy main story shape
State, 0.5s run on afterflow energy regenerative state, outlet side series connection one dc source simulation feedback energy, simulation result such as Figure 12-figure
Shown in 15.
Figure 12 is input phase voltage and phase current waveform, it can be seen that during energy main story, the same phase of voltage x current
Position, unity power factor operation is realized, afterflow energy regenerative state, input voltage and input current phase difference 180 are switched to after 0.5s
Degree, realizes the feedback of energy, and input current sine degree is preferable, demonstrates the good input characteristics of CRMC of the present invention and one or two
Quadrant jobs ability.
Figure 13 knows by waveform to coordinate the lower CRMC output voltages of control and current waveform, and during energy main story, voltage x current is equal
For on the occasion of after 0.5s, voltage direction changes, and the sense of current keeps constant, and output voltage current ripples are smaller, demonstrate
The present invention coordinates the lower CRMC of control and works in one, two quadrant, realizes the two-way flow ability of energy.
The partial enlargement waveform of primary voltage of transformer and electric current when Figure 14 is energy main story, is known, voltage and electricity by waveform
Same polarity is flowed, CRMC is demonstrated and works in energy main story state；Primary voltage of transformer and electric current when Figure 15 is afterflow energy regenerative
Partial enlargement waveform, voltage and current is in opposite direction, demonstrates CRMC and works in energy regenerative pattern, the above results demonstrate the present invention
The correctness of coordination control strategy.
Claims (7)
1. current mode Simplify matrix converter, it is characterised in that：The converter includes three-phase input power supply（1）, input filter
（2）, matrix chopper（3）, high frequency transformer（4）, current mode chopper（5）, output filter（6）And load（7）；Described three
Phase input power（1）Output port R, output port S, output port T and the input filter（2）Input port R0,
Input port S0, input port T0 are corresponding to be connected；The input filter（2）Output port r1, output port s1, output end
Mouth t1 is correspondingly connected to the matrix chopper（3）Input side ports r2, input side ports s2, input side ports t2；The height
Frequency power transformer（4）Primary side port A, primary side port B correspondingly connect the matrix chopper（3）Outlet side port A0, output
Side ports B0, the high frequency transformer（4）Secondary port a, secondary port b be connected to the current mode chopper（5）Input side
Port a0, input side ports b0；The current mode chopper（5）Output port w, output port v respectively with it is described output filter
Ripple device（6）Input port w0, input port v0 be connected, the output filter（6）Output port w1, output port v0 and institute
State load（7）Port w2, port v2 connections.
2. current mode Simplify matrix converter as claimed in claim 1, it is characterised in that：The matrix chopper（3）In
Switch Sapp、Sann、Sbpp、Sbnn、Scpp、ScnnSubstituted using two-way switch.
3. current mode Simplify matrix converter as claimed in claim 1, it is characterised in that：The current mode chopper（5）Institute
A full keyholed back plate IGBT S for including being cascaded with voltage two-way type switch1With a diode D1；The collection of the full keyholed back plate
Electrode is connected with the anode of the diode.
4. the control method for coordinating of current mode Simplify matrix converter as claimed in claim 1, it is characterised in that：The matrix
Chopper（3）After bipolarity space vector modulating method, according to the matrix chopper（3）Synchronizing signal and output electricity
The direction of stream is to the current mode chopper（5）Carry out sending out ripple control.
5. the control method for coordinating of current mode Simplify matrix converter as claimed in claim 4, it is characterised in that：It is described bipolar
Property space vector modulating method comprises the steps：
(1) tactful sector is divided, division principle reaches maximum for the absolute value of a certain phase phase voltage, and with remaining two-phase
Polarity of voltage is opposite；
(2) bipolarity Space vector modulation is carried out：Each traditional switch cycleT s It is divided into two equal half periods, precedingT s / 2 cycles
When, basic vector is synthesized by two effective one zero vectors of vector, rearT s / 2 cycles, basic vector are by precedingT s / 2 cycles
The same zero vector synthesis of effective vector in opposite direction, may be such that at oneT s It is opposite that size equidirectional is obtained in cycle
Two vectors；
(3) sector residing for foundation current phasor, before calculatingT s / 2 cycles, effective vector duty cycle are respectivelyd x1 ,d y1 , zero vector accounts for
Empty ratiod 0 =1-d x1 -d y1 ；Before later half period vector usesT s The dutycycle that/2 cycles obtained, i.e.,d x2 = d x1 ,d y2 = d y1 。
6. the control method for coordinating of current mode Simplify matrix converter as claimed in claim 5, it is characterised in that：The step
(1) in whenU sa >0, U sb <0, U sc <It is the first sector when 0；WhenU sa >0, U sb >0, U sc <It is the second sector when 0；WhenU sa
<0, U sb >0, U sc <It is the 3rd sector when 0；WhenU sa <0, U sb >0, U sc >It is the 4th sector when 0；WhenU sa <0, U sb <
0, U sc >It is the 5th sector when 0；WhenU sa >0, U sb <0, U sc >It is the 6th sector when 0；It is describedU sa 、U sb 、U sc To be corresponding
The three-phase input power supply（1）Three-phase input voltage.
7. the control method for coordinating of current mode Simplify matrix converter as claimed in claim 4, it is characterised in that：The hair ripple
Control refers to according to the matrix chopper（3）Synchronizing signal and the demand of output current control：
In energy main story, i.e. output voltageU o More than zero, electric currentI o During more than zero, if the matrix chopper（3）The synchronous letter of output
Number for just, the high frequency transformer（4）Original edge voltage is also for just, then the current mode chopper（5）Upper left bridge arm switch S1 and
Bottom right bridge arm switch S4 is open-minded；If the matrix chopper（3）It is negative, the high frequency transformer to export synchronizing signal（4）Primary side
Voltage is negative, the then current mode chopper（5）Upper right bridge arm switchs S2 and lower-left bridge arm switch S3 is open-minded；
In energy afterflow energy regenerative, i.e. output voltageU o Less than zero, electric currentI o During more than zero, if the matrix chopper（3）Output is same
Signal is walked as just, now the high frequency transformer（4）Original edge voltage is also for just, then the current mode chopper（5）Upper left bridge arm
Switch S2 and bottom right bridge arm switch S3 is open-minded；If the matrix chopper（3）It is negative, the high frequency transformer to export synchronizing signal
（4）Original edge voltage is negative, the then current mode chopper（5）Upper right bridge arm switchs S1 and lower-left bridge arm switch S4 is open-minded.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201710777320.1A CN107612386A (en) | 2017-09-01 | 2017-09-01 | Current mode Simplify matrix converter and its control method for coordinating |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201710777320.1A CN107612386A (en) | 2017-09-01 | 2017-09-01 | Current mode Simplify matrix converter and its control method for coordinating |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN107612386A true CN107612386A (en) | 2018-01-19 |
Family
ID=61056896
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201710777320.1A Pending CN107612386A (en) | 2017-09-01 | 2017-09-01 | Current mode Simplify matrix converter and its control method for coordinating |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN107612386A (en) |
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109787493A (en) * | 2019-03-26 | 2019-05-21 | 哈工大（张家口）工业技术研究院 | The binary cycle Current Decoupling modulator approach of three-phase single-level formula AC-DC converter |
| CN111147002A (en) * | 2019-08-12 | 2020-05-12 | 东南大学 | Matrix motor driving system based on bidirectional wireless power transmission |
| CN113141121A (en) * | 2021-04-22 | 2021-07-20 | 东南大学 | Current source type high-frequency isolation matrix type cascade converter and control method |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101174798A (en) * | 2007-11-16 | 2008-05-07 | 华中科技大学 | Control method for matrix transforming machine and its device |
| CN102969932A (en) * | 2012-12-20 | 2013-03-13 | 中南大学 | Multifunctional current-type bidirectional AC (Alternating-Current)/DC (Direct-Current) converter and control method thereof |
| CN103944409A (en) * | 2014-04-17 | 2014-07-23 | 华为技术有限公司 | Control method, equipment and system for frequency convertor |
| CN107104602A (en) * | 2017-04-17 | 2017-08-29 | 燕山大学 | The special logic formula current mode of AND-OR gate construction is unhitched coupling single-polarity PWM method |
-
2017
- 2017-09-01 CN CN201710777320.1A patent/CN107612386A/en active Pending
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101174798A (en) * | 2007-11-16 | 2008-05-07 | 华中科技大学 | Control method for matrix transforming machine and its device |
| CN102969932A (en) * | 2012-12-20 | 2013-03-13 | 中南大学 | Multifunctional current-type bidirectional AC (Alternating-Current)/DC (Direct-Current) converter and control method thereof |
| CN103944409A (en) * | 2014-04-17 | 2014-07-23 | 华为技术有限公司 | Control method, equipment and system for frequency convertor |
| CN107104602A (en) * | 2017-04-17 | 2017-08-29 | 燕山大学 | The special logic formula current mode of AND-OR gate construction is unhitched coupling single-polarity PWM method |
Non-Patent Citations (2)
| Title |
|---|
| ALEJANDRO GARCES 等: ""Impact of operation principle on the losses of a reduced"", 《2010 IEEE INTERNATIONAL SYMPOSIUM ON INDUSTRIAL ELECTRONICS》 * |
| 王辉 等: ""高频链矩阵整流器的研究综述"", 《电网技术》 * |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109787493A (en) * | 2019-03-26 | 2019-05-21 | 哈工大（张家口）工业技术研究院 | The binary cycle Current Decoupling modulator approach of three-phase single-level formula AC-DC converter |
| CN111147002A (en) * | 2019-08-12 | 2020-05-12 | 东南大学 | Matrix motor driving system based on bidirectional wireless power transmission |
| CN111147002B (en) * | 2019-08-12 | 2021-09-03 | 东南大学 | Matrix motor driving system based on bidirectional wireless power transmission |
| CN113141121A (en) * | 2021-04-22 | 2021-07-20 | 东南大学 | Current source type high-frequency isolation matrix type cascade converter and control method |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN108923666B (en) | Dual-output two-stage matrix converter modulation method based on carrier PWM | |
| CN107276448B (en) | A kind of H bridge cascaded multilevel inverter based on phase shift space vector modulating method | |
| CN106972603A (en) | The V2G chargers and its control method of a kind of use High Frequency Link matrix converter | |
| CN107612386A (en) | Current mode Simplify matrix converter and its control method for coordinating | |
| CN106655842B (en) | The novel unipolar alternate frequency multiplication SPWM modulator approach of single-phase high frequency chain matrix rectifier | |
| CN106487267A (en) | A kind of single-phase grid-connected inverter topological structure and its control method | |
| CN105429497A (en) | Optimized modular multi-level converter (MMC) submodule capacitance voltage equalization control method | |
| CN105186898A (en) | Simplified multi-level space vector pulse width modulation method for any-level single-phase cascaded H-bridge type converter and modulation soft core thereof | |
| CN105207504A (en) | Half-bridge and full-bridge mixed type MMC topology with voltage enhancement characteristic | |
| CN104578869A (en) | Capacitance self-voltage-sharing three-phase multi-level converter circuit with direct-current bus | |
| CN108429469B (en) | Z-source two-stage matrix converter modulation method based on carrier PWM | |
| CN103346668A (en) | Control system for restraining high-frequency electromagnetic interference at output end of indirect matrix converter | |
| CN205051611U (en) | Motor drive system that restraines switched reluctance motor torque ripple | |
| CN102082523B (en) | Controlling method of compositely controlled cascaded multilevel inverter and multilevel inverter | |
| Chattopadhyay et al. | Cascaded H-Bridge & neutral point clamped hybrid asymmetric multilevel inverter topology for grid interactive transformerless photovoltaic power plant | |
| CN104052083A (en) | Grid connection inverter hybrid modulating device and method | |
| CN105207503A (en) | Power electronic transformer control method based on hybrid pulse width modulation (HPWM) | |
| CN112701725B (en) | Grid-connected inverter with mixed conduction mode | |
| CN106998152B (en) | Electrical isolation Uniderectional DC-DC converter without Pressure and Control | |
| CN105099221A (en) | Simplified multilevel space vector pulse width modulation method for single-phase cascaded three-level bridge type converter of any number of level and modulation soft core thereof | |
| CN107017797B (en) | Accumulator cell charging and discharging single-phase high frequency chain matrix converter separate type vector modulation method | |
| CN108092534A (en) | The control method and device of single-phase Five-level converter | |
| CN106787915B (en) | Inhibit the dual carrier SVPWM control method of energy back feed device circulation | |
| CN109861576A (en) | A kind of Z-source inverter allowing work in discontinuous conduct mode | |
| CN107681914A (en) | Switching capacity T source inventers and modulator approach based on active clamp |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| RJ01 | Rejection of invention patent application after publication | ||
| RJ01 | Rejection of invention patent application after publication |
Application publication date: 20180119 |