CN108429469B - Z-source two-stage matrix converter modulation method based on carrier PWM - Google Patents

Z-source two-stage matrix converter modulation method based on carrier PWM Download PDF

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CN108429469B
CN108429469B CN201810135054.7A CN201810135054A CN108429469B CN 108429469 B CN108429469 B CN 108429469B CN 201810135054 A CN201810135054 A CN 201810135054A CN 108429469 B CN108429469 B CN 108429469B
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CN108429469A (en
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王汝田
韩旭
赵艳峰
钟哲夫
贾松达
王雪
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Northeast Electric Power University
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Northeast Dianli University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
    • H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
    • H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
    • H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M5/4585—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only having a rectifier with controlled elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load

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Abstract

The invention relates to a Z-source two-stage matrix converter modulation method based on carrier PWM, which is characterized in that for a rectification stage, an input phase voltage is divided into six sectors, two line voltages with the maximum amplitude and positive polarity are selected in each sector to synthesize an output direct current voltage, and a corresponding duty ratio is calculated; for the inverter stage, space voltage vector modulation is adopted, and the duty ratio of an effective voltage vector and a zero voltage vector is calculated according to the sector where the reference voltage vector is located; for the Z source network, the direct voltage vector is correctly and reasonably inserted into the inverter level zero vector, and the voltage transmission ratio is improved. According to the whole modulation process, a power switch PWM signal diagram is drawn, modulation signals of six groups of bidirectional power switches of a rectifier stage and modulation signals of six groups of power switches of an inverter stage are respectively calculated and compared with the same triangular carrier signal, and a driving signal of the bidirectional power switches of the rectifier stage and a driving signal of the power switches of the inverter stage are obtained. The method is simple in calculation and easy to implement.

Description

Z-source two-stage matrix converter modulation method based on carrier PWM
Technical Field
The invention belongs to the technical field of alternating current-alternating current energy conversion devices, and particularly relates to a Z-source two-stage matrix converter modulation method based on carrier PWM.
Background
The two-stage matrix converter is used as an AC-AC two-stage converter, not only enables input and output to be good sine waveforms, but also has the advantages of bidirectional energy transfer, four-quadrant operation, no need of large-capacity energy storage elements, adjustable input power factor, capability of approximately reaching 1 and the like. Although the advantages are numerous, the voltage transmission ratio is low, the maximum voltage transmission ratio is only 0.866, and the output performance is susceptible to abnormal input, which severely limits the application and popularization of the circuit. A Z source network is expanded into a two-stage matrix converter, and the Z source two-stage matrix converter is provided. Only passive elements are added, and the purpose of improving the voltage transmission ratio is achieved by utilizing the unique direct connection state of the Z source network on the premise of not increasing the number of power switches. And due to the existence of the Z source network, the influence of abnormal input on the output performance is greatly restrained.
At present, a modulation method for a Z-source two-stage matrix converter is mainly a space vector modulation strategy, and comprises space vector modulation of a rectification stage with a zero vector, space vector modulation of a rectification stage without a zero vector, and maximum boost control and mixed minimum stress control which are provided on the basis of the space vector. However, when the space vector modulation method is applied, complex trigonometric function calculation is required, the process is complex, and programming and hardware realization are not facilitated.
Disclosure of Invention
The invention aims to provide a Z-source two-stage matrix converter modulation method based on carrier PWM, which is scientific, reasonable, high in applicability and good in effect and aims to solve the problem that the existing Z-source two-stage matrix converter modulation strategy is complex.
The technical scheme adopted for realizing the purpose of the invention is that the Z source two-stage matrix converter modulation method based on carrier PWM comprises a rectification stage, an inverter stage and a Z source network, wherein the rectification stage is a three-phase bridge rectification circuit consisting of six groups of bidirectional power switches, the inverter stage is a three-phase inverter circuit consisting of six groups of power switches, and the Z source network is an X-type network consisting of two identical inductors and two identical capacitors, and is characterized in that:
for the rectification stage, dividing the input phase voltage into six sectors, selecting two line voltages with the maximum and positive polarity in each sector to synthesize the output direct-current voltage, enabling the output to contain no zero voltage, and calculating the corresponding duty ratio;
for the inverter stage, a through vector is inserted on the basis of space voltage vector modulation, and the introduction of the through vector provides a unique boosting function for the Z-source inverter stage;
for Z-source networks, there are two modes of operation: and then drawing a switch modulation sequence diagram according to the modulation processes of the rectifier stage and the inverter stage, respectively calculating modulation signals of six groups of bidirectional power switches of the rectifier stage and the inverter stage, and comparing the modulation signals with the same triangular carrier signal to obtain a driving signal of the rectifier stage bidirectional power switch and a driving signal of the inverter stage power switch.
Further, the triangular carrier signal amplitude is from-U1To U1The change is that the number of the first and second,the carrier period is the same as the modulation period.
Further, the Z-source two-stage matrix converter modulation method based on carrier PWM is characterized by comprising the following steps:
1) the modulation signals of the six groups of bidirectional power switches of the rectifier stage are respectively as follows:
when u isw>At the time of 0, the number of the first,
vwp＝U1；vxp＝-U1；vyp＝-U1
Figure BDA0001576020140000021
when u isw<At the time of 0, the number of the first,
Figure BDA0001576020140000022
vwn＝U1；vxn＝-U1；vyn＝-U1
wherein, w, x, y ∈ { a, b, c } vwp、vxp、vyp、vwn、vxn、vynModulating signals of six groups of bidirectional power switches of a rectifying stage; w is the phase with the maximum absolute value in the three-phase input, and x and y are the other two phases; when u isw>When 0, the x and y two-phase lower bridge arm switch pulse signals are complementary, uw<When 0, the switching pulse signals of the upper bridge arms of the x phase and the y phase are complementary;
2) the modulation signals of the inverter stage are:
Figure BDA0001576020140000023
wherein, VX1And VX2The modulation signal is an inversion-level X-phase modulation signal; u. ofXOutputting X-phase voltage for inverter stage, X ∈ { A, B, C }, and dxAnd dyFor synthesizing the duty ratio of two input line voltages of the direct current voltage, the calculation formula is as follows:
Figure BDA0001576020140000031
Figure BDA0001576020140000032
the calculation formula of the average value of the direct current voltage output by the rectifier stage is as follows:
Figure BDA0001576020140000033
wherein, UiFor the input phase voltage amplitude to be the input phase voltage amplitude,
uoffsetfor the bias voltage, the calculation formula is:
Figure BDA0001576020140000034
wherein u ismax＝max(uA,uB,uC),umin＝min(uA,uB,uC)；
3) The modulation signals of the through vector are as follows:
Figure BDA0001576020140000035
wherein, Vst1～Vst7Modulation signals for the 7 through vectors inserted in the inverter stage;
4) and respectively comparing the modulation signals of the six groups of bidirectional power switches of the rectifier stage, the modulation signals of the six groups of power switches of the inverter stage and the modulation signals of the through vectors with set triangular carrier signals to obtain driving signals for controlling the bidirectional power switches of the rectifier stage and the driving signals for controlling the power switches of the inverter stage.
Compared with the space vector modulation method, the Z-source two-stage matrix converter modulation method based on the carrier PWM avoids complex trigonometric function calculation in one modulation period, is easy to realize, ensures good input and output waveform quality, and has the advantages of scientific and reasonable method, strong applicability, good effect and the like.
Drawings
FIG. 1 is a schematic diagram of a Z-source two-stage matrix converter topology;
FIG. 2 is a schematic diagram of a three-phase input voltage sector division;
FIG. 3 is a schematic diagram of an inverter stage voltage space vector;
FIG. 4 is a schematic diagram of PWM signals of power switches of a rectification stage and an inverter stage;
FIG. 5 is a schematic diagram of a through zero voltage condition;
FIG. 6 is a schematic diagram of a non-shoot-through zero voltage condition;
FIG. 7 is a schematic diagram of carrier PWM to generate a rectification stage PWM signal;
FIG. 8 is a schematic diagram of carrier PWM generating inverter stage PWM signals;
fig. 9 is a waveform diagram of the output dc voltage of the rectifying stage of the Z-source two-stage matrix converter, the voltage of the Z-source capacitor, the output voltage of the a-phase, the output three-phase current, and the input voltage and current of the a-phase according to the modulation method of the present invention.
Detailed Description
The invention is described in further detail below with reference to the figures and specific embodiments.
FIG. 1 is a topological block diagram of a Z-source two-stage matrix converter, ua、ub、ucRepresenting three-phase input phase voltages; u. ofA、uB、uCRepresenting three-phase output phase voltages;
first, the duty ratio of each vector of the rectification stage and the inverter stage is calculated.
For a rectifier stage, the three-phase input phase voltages are:
Figure BDA0001576020140000041
the input three-phase input voltage is divided into 6 sectors as shown in fig. 2. Each sector has the same characteristics: one phase has the maximum absolute voltage, while the other two phases have opposite voltage polarities. Two maximum line voltages of positive polarity are selected in each sector to synthesize the output dc voltage. Take the first sector as an example，uaPositive polarity and maximum absolute value, ub、ucThe polarity is negative, so the output line voltage is uacAnd uabThe corresponding duty ratio is dxAnd dyIn order to make the input side power factor 1 and the input current waveform sinusoidal, it is necessary that the input current of each phase is in phase and magnitude proportional to the voltage. Therefore, in one modulation period, the local average value of the input current of each phase is proportional to the amplitude of the corresponding input phase voltage, so that:
Figure BDA0001576020140000051
local average value of DC voltage in one modulation period
Figure BDA0001576020140000052
Comprises the following steps:
Figure BDA0001576020140000053
wherein, UiIs the input phase voltage amplitude.
From the above analysis, the power switch states and dc voltages and corresponding duty cycles in each sector can be obtained as shown in table 1.
TABLE 1 rectifier stage Power switch State and DC Voltage
Figure BDA0001576020140000054
For the inverter stage, the three-phase output phase voltages are set as follows:
Figure BDA0001576020140000055
fig. 3 is a schematic diagram of the inverter stage voltage space vector. Assuming that the reference output voltage vector is located in the first sector, according to the synthesis principle of the reference voltage vector, the duty ratio of each voltage vector of the inverter stage can be obtained as follows:
Figure BDA0001576020140000061
Figure BDA0001576020140000062
d0+d7＝1-d1-d2
Figure BDA0001576020140000063
wherein d is1And d2Is a significant vector U1And U2Duty cycle of (d); d0And d7Is a zero vector U0And U7Duty cycle of (d);
Figure BDA0001576020140000064
is to output a reference voltage, and
Figure BDA0001576020140000065
in order to obtain three-phase symmetric input current and output voltage, the power switching states of the rectifier stage and the inverter stage should be effectively combined. The rectifier stage having two states u in each modulation periodacAnd uabThe duty ratio is dxAnd dy. Therefore, the power switch states of the inverter stage should also be divided into two groups, and the rectifier stage and the inverter stage duty cycle are combined as follows:
d1(x)＝d1dx；d2(x)＝d2dx；d0(x)＝d0dx；d7(x)＝d7dx(6)
d1(y)＝d1dy；d2(y)＝d2dy；d0(y)＝d0dy；d7(y)＝d7dy(7)
the rectification stage and inverter stage power switch PWM signals are shown in fig. 4.
For a Z-source network, there are two operating states: a shoot-through zero voltage condition and a non-shoot-through zero voltage condition. When the direct current is in a zero voltage state, the inverter stage is in a short circuit, all power switches in the rectifier stage are closed, the direct current side is disconnected with the alternating current input power supply, the capacitor charges the inductor, the inductor stores energy, and an equivalent circuit is shown in fig. 5; in a non-direct-through zero-voltage state, the rectification stage and the Z source network supply power to the inverter stage together, so that the system has high voltage transmission capability, and an equivalent circuit is shown in fig. 6.
Defining boost factor for Z-source two-stage matrix converter
Figure BDA0001576020140000066
Wherein d isstD is a direct duty ratio of 0 tost≤0.5。
In a Z-source network, the inductance L1＝L2And a capacitor C1＝C2Then, the following relationship exists:
Figure BDA0001576020140000071
the voltage transmission ratio of the Z-source two-stage matrix converter can be simplified as follows:
Figure BDA0001576020140000072
wherein m is a modulation factor, and m is more than or equal to 0 and less than or equal to 1.
From the above analysis, it can be seen that when m and B are changed within the allowable range, the voltage transfer ratio of the Z-source two-stage matrix converter can be changed from 0 to 4.33, which is much larger than the transfer ratio of the conventional matrix converter from 0 to 0.866.
Selecting isosceles triangular wave as carrier signal with the same period as modulation period and amplitude from-U1To U1In a variation, carrier PWM generates a rectification stage PWM signal as shown in fig. 7, from which it can be derived that the carrier signal is:
Figure BDA0001576020140000073
wherein, VtIs a triangular carrier signal, U1Is its amplitude.
The drive signal of the rectifier stage being obtained by comparing a modulated wave VcnAnd a triangular carrier. According to FIG. 7, Vap＝U1Therefore, the upper bridge arm power switch of the phase a is continuously conducted; when V iscnGreater than VtWhen the power switch of the lower bridge arm of the c phase is turned on, the other four power switches are turned off; when V iscnLess than VtAnd meanwhile, the b-phase lower bridge arm power switch keeps on, and the other four power switches are turned off.
Combining with the duty ratio calculation formula (2) of the rectifier stage, the obtained rectifier stage power switch modulation signal is:
vap＝U1；vbp＝U1；vcp＝U1(11)
van＝-U1；vcn＝(2dx-1)U1
wherein, the b-phase lower bridge arm power switch driving signal SbnAnd c phase lower bridge arm power switch driving signal ScnComplementary, and therefore dependent on the drive signal v of the c-phase lower arm power switchcnAnd then the driving signals of the b and c two-phase lower bridge arm power switches can be obtained. The modulated signals of the six groups of bidirectional power switches of the rectifier stage are obtained by sorting and induction:
when u isw>At the time of 0, the number of the first,
Figure BDA0001576020140000081
when u isw<At the time of 0, the number of the first,
Figure BDA0001576020140000082
wherein, w, x, y ∈ { a, b, c } vwp、vxp、vyp、vwn、vxn、vynModulating signals of six groups of bidirectional power switches of a rectifying stage; w is the phase with the maximum absolute value in the three-phase input, and x and y are the other two phases;when u isw>When 0, the driving signals of the x and y two-phase lower bridge arm switches are complementary, uw<And when 0, the driving signals of the upper bridge arm switches of the x phase and the y phase are complementary.
The power switch driving signal of the upper bridge arm of each phase of the inverter stage is obtained by comparing two modulation signals with a carrier signal, as shown in fig. 8, in which phase a is taken as an example. By combining with the duty ratio calculation formula (5) of the inverter stage and by sorting and induction, the modulation signals of each phase of power switch of the inverter stage are:
Figure BDA0001576020140000083
wherein, VX1And VX2The modulation signal is an inversion-level X-phase modulation signal; u. ofXOutputting X-phase voltage for inverter stage, X ∈ { A, B, C }, and dxAnd dyTo synthesize the duty cycle of the two line voltages of the output dc voltage. Two modulation signals VX1、VX2Comparing with carrier wave to obtain two groups of signals SX1，SX2Drive signal S of X-phase upper bridge arm power switchXThe two groups of signals can be obtained through logical operation in an equation (15), and the driving signal of the lower bridge arm power switch is complementary with the driving signal of the upper bridge arm power switch.
Figure BDA0001576020140000084
The length of the through time influences the amplitude of the output voltage of the inverter stage, and the through state is inserted into any time in the zero vector, so that the effect is the same, the proper time for inserting the through state is found, the calculation can be simplified, and the modulation method of the Z source two-stage matrix converter based on the carrier PWM is simpler. As shown in fig. 8, taking the input and output in the first sector as an example, a through state is inserted in each zero vector action time, and the driving signal of the through state is obtained by comparing two modulation signals and a carrier signal, similar to the effective vector. With dst2For example, Vst2And Vst3Is two modulated signals thereof, the modulated signals being compared with a carrier signalAnd comparing with the same or operation, the carrier PWM modulation method in the through state can be obtained.
According to fig. 8, and in combination with equations (3), (5), (6) and (9), the modulation signal in the through state can be expressed as:
Vst1＝(dstdx-1)U1(16)
Vst2＝(dx-dy-dstdx)U1(17)
Vst3＝(dx-dy)U1(18)
Vst4＝(dx-dy)U1(19)
Vst5＝(dx+dstdy-dy)U1(20)
Vst6＝(2dx+2dy-dstdy-1)U1(21)
Vst7＝(2dx+2dy-1)U1(22)
and respectively comparing the modulation signals of the six groups of bidirectional power switches of the rectifier stage, the modulation signals of the six groups of power switches of the inverter stage and the modulation signals of the through vectors with set triangular carrier signals to obtain driving signals for controlling the bidirectional power switches of the rectifier stage and the driving signals for controlling the power switches of the inverter stage.
In order to illustrate the effectiveness of the modulation method of the present invention, simulation was performed using Matlab software. The simulation parameters are as follows: the amplitude of the input voltage is 200V, and the frequency is 50 Hz; setting the amplitude of the output voltage to 275V and the frequency to 100 Hz; z source network inductance L1、L2Are all 1mH, a capacitor C1、C2Are all 220 mu F; the load resistance is 16 Ω and the inductance is 12 mH. The simulated waveform is shown in fig. 9. The output DC voltage of the rectification stage is a pulse wave, and the maximum average value of the pulse wave in one modulation period is about 346V; the voltage of the Z source network capacitor is stabilized at about 508V and is far higher than the output direct-current voltage of the rectifier stage; the A-phase output voltage is a pulse wave, and after the three-phase output voltage acts on the resistive load, a sinusoidal three-phase symmetrical current waveform is generated; the a-phase input current is a sine wave,and is nearly in phase with the voltage. Simulation results show that the carrier PWM-based Z-source two-stage matrix converter modulation method can ensure good input and output performance.

Claims (1)

1. A modulation method of a Z-source two-stage matrix converter based on carrier PWM comprises a rectification stage, an inverter stage and a Z-source network, wherein the rectification stage is a three-phase bridge rectification circuit formed by six groups of bidirectional power switches, the inverter stage is a three-phase inverter circuit formed by six groups of power switches, and the Z-source network is an X-type network formed by two identical inductors and capacitors, and is characterized in that:
for the rectification stage, dividing the input phase voltage into six sectors, selecting two line voltages with the maximum and positive polarity in each sector to synthesize the output direct-current voltage, enabling the output to contain no zero voltage, and calculating the corresponding duty ratio;
for the inverter stage, a through vector is inserted on the basis of space voltage vector modulation, and the introduction of the through vector provides a unique boosting function for the Z-source inverter stage;
for Z-source networks, there are two modes of operation: a direct-connection zero-voltage state and a non-direct-connection zero-voltage state, then drawing a switch modulation sequence chart according to the modulation process of a rectifier stage and an inverter stage, respectively calculating the modulation signals of six groups of bidirectional power switches of the rectifier stage and the modulation signals of six groups of power switches of the inverter stage, comparing the modulation signals with the same triangular carrier signal to obtain the driving signals of the rectifier stage bidirectional power switches and the driving signals of the inverter stage power switches, wherein the amplitude of the triangular carrier signal is-U1To U1A variation having a carrier period identical to the modulation period;
the method specifically comprises the following steps:
1) the modulation signals of the six groups of bidirectional power switches of the rectifier stage are respectively as follows:
when u isw>At the time of 0, the number of the first,
vwp＝U1；vxp＝-U1；vyp＝-U1
vwn＝-U1；
Figure FDA0002452720130000011
when u isw<At the time of 0, the number of the first,
vwp＝-U1；
Figure FDA0002452720130000012
vwn＝U1；vxn＝-U1；vyn＝-U1
wherein, w, x, y ∈ { a, b, c } vwp、vxp、vyp、vwn、vxn、vynModulating signals of six groups of bidirectional power switches of a rectifying stage; w is the phase with the maximum absolute value in the three-phase input, and x and y are the other two phases; when u isw>When 0, the x and y two-phase lower bridge arm switch pulse signals are complementary, uw<When 0, the switching pulse signals of the upper bridge arms of the x phase and the y phase are complementary;
2) the modulation signals of the inverter stage are:
Figure FDA0002452720130000021
wherein, VX1And VX2The modulation signal is an inversion-level X-phase modulation signal; u. ofXOutputting X-phase voltage for inverter stage, X ∈ { A, B, C }, and dxAnd dyFor synthesizing the duty ratio of two input line voltages of the direct current voltage, the calculation formula is as follows:
Figure FDA0002452720130000023
the calculation formula of the average value of the direct current voltage output by the rectifier stage is as follows:
Figure FDA0002452720130000024
wherein, UiFor the input phase voltage amplitude to be the input phase voltage amplitude,
uoffsetfor the bias voltage, the calculation formula is:
Figure FDA0002452720130000025
wherein u ismax＝max(uA,uB,uC),umin＝min(uA,uB,uC)；
3) The modulation signals of the through vector are as follows:
Figure FDA0002452720130000026
wherein, Vst1～Vst7For the modulated signals of the 7 through vectors inserted in the inverter stage, dstD is a direct duty ratio of 0 tost≤0.5；
4) And respectively comparing the modulation signals of the six groups of bidirectional power switches of the rectifier stage, the modulation signals of the six groups of power switches of the inverter stage and the modulation signals of the through vectors with set triangular carrier signals to obtain driving signals for controlling the bidirectional power switches of the rectifier stage and the driving signals for controlling the power switches of the inverter stage.
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