CN107040228B - Failure circuit suitable for nonlinear regulator - Google Patents
Failure circuit suitable for nonlinear regulator Download PDFInfo
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- CN107040228B CN107040228B CN201710433139.9A CN201710433139A CN107040228B CN 107040228 B CN107040228 B CN 107040228B CN 201710433139 A CN201710433139 A CN 201710433139A CN 107040228 B CN107040228 B CN 107040228B
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03G—CONTROL OF AMPLIFICATION
- H03G3/00—Gain control in amplifiers or frequency changers without distortion of the input signal
- H03G3/20—Automatic control
- H03G3/30—Automatic control in amplifiers having semiconductor devices
Abstract
The application discloses a failure circuit suitable for a nonlinear regulator, which utilizes a first operational amplifier, a first resistor, a second resistor, a third resistor and a 1-to-2 analog switch to form an inverse proportion operational amplifier circuit with two different proportion gain coefficients, responds to an insensitive area by utilizing a window voltage comparator, and selects which proportion gain coefficient is output by the response signal through the 1-to-2 analog switch.
Description
Technical Field
The present application relates to the field of process control systems, and more particularly to a failure circuit for a nonlinear regulator.
Background
In a process control system, a feedback type proportional, integral and differential regulator (i.e. a PID regulator) is widely adopted to carry out deviation regulation on a controlled variable, so that the actual value of the controlled variable is consistent with a set value required by a production process, but with development of an automation technology and complexity of the production process, the control performance of the PID regulator cannot meet the requirement on a process or a nonlinear process with lag time and the like, and therefore, the nonlinear regulator with an insensitive area appears, and the regulator is formed by adding a failure circuit on the basis of the PID regulator, so that the failure circuit is a key circuit of the nonlinear regulator with the insensitive area and plays a vital role in realizing optimal control of the process, thereby achieving the aim of improving the control quality.
The disabling circuit is a nonlinear amplification unit with a dead zone, the proportional gain of the disabling circuit is substantially reduced in a region near the control point of the nonlinear regulator, and the proportional gain of the disabling circuit is restored outside the region. The principle of the present application is that the gain coefficient of the operational amplifier is changed by selecting the on or off state of the diode, and the diode is not an ideal switching element, the on state of the diode needs threshold voltage, the off state of the diode has leakage current, so that an accurate and stable dead zone (the zone with greatly reduced proportional gain) is difficult to obtain, and when the regulating system starts and stops or the setting value is suddenly changed, the output of the system can be greatly overshoot and oscillates for many times under the action of the integral term of PID control due to the existence of many diode nonlinear elements in the regulating system.
Disclosure of Invention
The application aims to provide a failure circuit of a nonlinear regulator, which avoids the use of a diode in the existing scheme and solves the problems of low precision, poor anti-interference capability, poor response and the like caused by the existing scheme.
The application solves the technical problems as follows: a failure circuit for a nonlinear regulator, comprising: the window voltage comparator comprises a window voltage comparator, a first operational amplifier, a first resistor, a first feedback branch, a second feedback branch, a 1-to-2-path analog switch and an inverter, wherein the 1-to-2-path analog switch and the inverter are used for gating the first feedback branch or the second feedback branch, a voltage input signal Vi of a failure circuit is connected to an inverting input end of the first operational amplifier through the inverter and the first resistor, a non-inverting input end of the first operational amplifier is connected to ground, an output end of the first operational amplifier is connected with an inverting input end of the first operational amplifier through the first feedback branch or the second feedback branch, a voltage input signal Vi is connected to an input end of the window voltage comparator, an output end of the window voltage comparator is connected with a control end of the 1-to-2-path analog switch, the first feedback branch comprises a second resistor, a resistance value of the first resistor is equal to a resistance value of the second resistor, a resistance value of the first resistor is far greater than a resistance value of the third resistor, and a threshold voltage of the window voltage comparator is far greater than a threshold voltage upper limit value and a threshold voltage lower limit value of the window voltage lower limit value is not higher than a threshold voltage region.
Further, the window voltage comparator includes: the voltage comparator, be used for outputting voltage high threshold's bleeder circuit, be used for with voltage input signal Vi conversion output is its absolute value's absolute value circuit, absolute value circuit's output with voltage comparator's inverting input end is connected, bleeder circuit's output with voltage comparator's homophase input end is connected, voltage comparator's output with 1 to 2 way analog switch's control end is connected. The absolute value circuit is utilized to take the absolute value of the voltage input signal Vi, so that only the voltage comparator is needed to compare the voltage input signal Vi with positive or negative polarity at the same time, the circuit is optimized, and the circuit cost is saved.
Further, the absolute value circuit includes: the output end of the second operational amplifier is connected with the inverting input end of the voltage comparator through the sixth resistor, the inverting input end and the non-inverting input end of the second operational amplifier are respectively connected with the inverting input end of the zero-crossing comparator through the fourth resistor and the fifth resistor, the non-inverting input end of the second operational amplifier is connected with the ground through the switch K, the driving control circuit of the switch K is controlled by the output of the zero-crossing comparator to control the on or off of the switch K, the inverting input end of the zero-crossing comparator inputs the voltage input signal Vi, the non-inverting input ends of the zero-crossing comparator are connected with the ground, and the resistance values of the fourth resistor, the fifth resistor and the sixth resistor are equal.
The beneficial effects of the application are as follows: the failure circuit of the structure utilizes a first operational amplifier, a first resistor, a second resistor, a third resistor and a 1-to-2 analog switch to form an inverse proportion operational amplifier circuit with two different proportion gain coefficients, a window voltage comparator is utilized to respond to an insensitive area, and a response signal is utilized to select which proportion gain coefficient is selected through the 1-to-2 analog switch.
Drawings
In order to more clearly illustrate the technical solutions in the embodiments of the present application, the drawings that are required to be used in the description of the embodiments will be briefly described below. It is evident that the drawings described are only some embodiments of the application, but not all embodiments, and that other designs and drawings can be obtained from these drawings by a person skilled in the art without inventive effort.
FIG. 1 is a schematic diagram of the circuit connections of a failure circuit;
fig. 2 is a schematic diagram of the coordinates of the regulation characteristic of the malfunctioning circuit.
Detailed Description
The conception, specific structure, and technical effects produced by the present application will be clearly and completely described below with reference to the embodiments and the drawings to fully understand the objects, features, and effects of the present application. It is apparent that the described embodiments are only some embodiments of the present application, but not all embodiments, and that other embodiments obtained by those skilled in the art without inventive effort are within the scope of the present application based on the embodiments of the present application. In addition, all coupling/connection relationships mentioned herein do not refer to direct connection of the components, but rather, refer to the fact that a more optimal coupling structure may be formed by adding or subtracting coupling aids depending on the particular implementation. The technical features in the application can be interactively combined on the premise of no contradiction and conflict.
Embodiment 1, referring to fig. 1 and 2, a failure circuit suitable for a nonlinear regulator, vi is a voltage input signal of the failure circuit, vo is a voltage output signal of the failure circuit, and V2 is a voltage signal of an output terminal of the second operational amplifier A2. The voltage input signal Vi is connected with an inverting input end of the first operational amplifier A1 through an inverter, the first operational amplifier A1, the 1-to-2 analog switch a2, the first resistor R1, the second resistor R2 and the third resistor R3 form an inverting proportional operational amplifier circuit with selectable gain, wherein the first resistor R1 is connected with the inverting input end of the first operational amplifier A1, the second resistor R2 and the third resistor R3 serve as two feedback branches of the inverting proportional operational amplifier circuit, the two feedback branches are controlled by gating control of the 1-to-2 analog switch a2, gating control ends a of the 1-to-2 analog switch a2 are controlled, when a control end a of the 1-to-2 analog switch a2 is connected with a low level, Y-B0 is conducted, when a control end a of the 1-to-2 analog switch a2 is connected with a high level, the resistance value of the first resistor R1 is equal to the resistance value of the second resistor R2, and the resistance value of the first resistor R1 is far greater than the resistance value of the third resistor R3.
The window voltage comparator a1 includes: the voltage dividing circuit is used for converting and outputting the voltage input signal Vi into an absolute value of the voltage input signal Vi, the voltage dividing circuit is used for dividing +E to ground voltage of a potentiometer Rw, the output end of the absolute value circuit a11 is connected with the inverting input end of the voltage comparator A4, the output end of the potentiometer Rw is connected with the same-phase end of the voltage comparator A4, and the output end of the voltage comparator A4 is connected with the control end A of the 1-to-2-path analog switch a 2. The voltage high threshold and the voltage low threshold of the window voltage comparator a1 are respectively the voltage upper limit value and the voltage lower limit value of the dead zone, the voltage high threshold of the embodiment is marked as +Ems, and the voltage low threshold is marked as-Ems.
The absolute value circuit a11 comprises a second operational amplifier A2, a zero-crossing comparator A3, a fourth resistor R4, a fifth resistor R5, a sixth resistor R6, a switch K and a driving control circuit a111 of the switch K, wherein the output end of the second operational amplifier A2 is connected with the inverting input end of the voltage comparator A4, the output end of the second operational amplifier A2 is connected with the inverting input end of the second operational amplifier A2 through the sixth resistor R6, the inverting input end and the non-inverting input end of the second operational amplifier A2 are respectively connected with the inverting input end of the zero-crossing comparator A3 through the fourth resistor R4 and the fifth resistor R5, the non-inverting input end of the second operational amplifier A2 is oppositely connected through the switch K, the driving control circuit a111 of the switch K is controlled by the control of the output of the zero-crossing comparator A3 to realize the opposite connection or disconnection of the non-inverting input end of the second operational amplifier A2, and the non-inverting input end of the zero-crossing comparator A2 is connected with the inverting input end of the fourth resistor A3 and the non-inverting input end of the zero-crossing comparator A3, and the non-inverting input ends of the zero-crossing comparator A3 are respectively connected with the non-inverting input ends of the fourth resistor R5 and the zero-crossing comparator A3, and the non-inverting input ends of the zero-crossing resistor A3 are equal. The application provides that the driving control circuit a111 of the switch K is an existing element, and has the function of controlling the switch K to be closed or opened according to the high level or the low level of the output of the zero-crossing comparator A3, wherein the switch K is closed when the output of the zero-crossing comparator A3 is in the low level, and the switch K is opened when the output of the zero-crossing comparator A3 is in the high level.
The failure circuit utilizes a first operational amplifier A1, a first resistor R1, a second resistor R2, a third resistor R3 and A1-to-2 analog switch a2 to form an inverse proportion operational amplifier circuit with two different proportion gain coefficients, responds to an insensitive area by utilizing a window voltage comparator A1, and selects which proportion gain coefficient is output by the response signal through the 1-to-2 analog switch a 2.
The working principle of the failure circuit is as follows: the zero-crossing comparator A3 constitutes a zero-crossing comparator for detecting the polarity of the voltage input signal Vi. When the voltage input signal Vi is greater than or equal to 0, the zero-crossing comparator A3 outputs a low level, the switch K is turned off by the driving control circuit a111 of the switch K, the second operational amplifier A2, the fourth resistor, the fifth resistor and the sixth resistor R4, the sixth resistor R5 and the sixth resistor R6 form a differential operational amplifier, and the values of the fourth resistor, the fifth resistor and the sixth resistor R4, the R5 resistor and the sixth resistor are equal, so that the gain of the differential operational amplifier is +1, that is, the voltage signal v2=vi at the output end of the second operational amplifier A2, V2 is sent to the inverting input end of the voltage comparator A4, and the voltage is compared with the voltage high threshold +ems (which is the voltage division value of the potentiometer Rw to +e to the ground) applied to the non-inverting input end of the voltage comparator A4.
When v2=vi < +ems is not less than 0, the voltage comparator A4 outputs a high level to the control end a, Y-B1 of the 1-to-2-path analog switch a2 to be conducted, the voltage input signal Vi is obtained by an inverter to obtain-Vi, and then the voltage input signal Vi is obtained by an inverting proportional operational amplifier circuit formed by the first operational amplifier A1, the first resistor R1 and the third resistor R3: vo is in phase with Vi, vo/vi=r3/R1, since the first resistor R1 is much larger than the third resistor R3, vo/Vi < <1.
When v2=vi+ems, the voltage comparator A4 outputs low level to the control end a of the 1-to-2 analog switch a2, the Y-B0 is turned on, the voltage input signal Vi is obtained through the inverter to obtain-Vi, and then the voltage input signal Vi is obtained through the inverting proportional operational amplifier circuit formed by the first operational amplifier A1, the first resistor R1 and the second resistor R2: vo is in phase with Vi, vo/vi=r2/R1, and Vo/vi=1 because the resistance of the first resistor R1 is equal to the resistance of the second resistor R2.
When Vi <0, the zero-crossing comparator A3 outputs a high level, the switch K is closed by the driving control circuit a111 of the switch K, the second operational amplifier A2, the fourth and the sixth resistors R4 and R6 form an inverting proportional operational amplifier, and since r4=r6, the gain is-1, that is v2= -Vi, the voltage is sent to the inverting terminal of the voltage comparator A4 and is compared with the voltage +ems applied to the non-inverting terminal of the voltage comparator A4:
when 0 is less than or equal to V2= -Vi < +Ems, the voltage comparator A4 outputs high level to the control end A of the 1-to-2-path analog switch a2, Y-B1 is conducted, vi is obtained through an inverter to obtain-Vi, and then the reverse phase proportion operational amplifier circuit formed by the first operational amplifier A1, the first resistor R1 and the third resistor R3 is used for obtaining the high-voltage power supply circuit: vo is in phase with Vi, vo/vi=r3/R1, since the first resistor R1 is much larger than the third resistor R3, vo/Vi < <1.
When v2= -Vi > + Ems, the voltage comparator A4 outputs low level to the control end a, Y-B0 of the 1-to-2-path analog switch a2 to be turned on, vi is obtained through an inverter, and then is obtained through an inverting proportional operational amplifier circuit formed by the first operational amplifier A1, the first resistor R1 and the second resistor R2: vo/vi=r2/R1, since the resistance of the first resistor R1 is equal to the resistance of the second resistor R2, vo/vi=1.
In summary, vo/Vi < <1, i.e., the proportional gain of the failure circuit is substantially smaller than 1 in the dead zone-Ems to +ems, and Vo/vi=1, i.e., the proportional gain of the failure circuit is restored to the original value of 1 outside the dead zone-Ems to +ems, and the adjustment characteristic curve of the failure circuit is shown in fig. 2.
While the preferred embodiment of the present application has been described in detail, the application is not limited to the embodiments, and various equivalent modifications and substitutions can be made by those skilled in the art without departing from the spirit of the application, and these modifications and substitutions are intended to be included in the scope of the present application as defined in the appended claims.
Claims (1)
1. A failure circuit for a nonlinear regulator, comprising: the voltage input signal Vi of the failure circuit is connected to the inverting input end of the first operational amplifier through the inverter and the first resistor, the non-inverting input end of the first operational amplifier is grounded, the output end of the first operational amplifier is connected with the inverting input end of the first operational amplifier through the first feedback branch or the second feedback branch, the voltage input signal Vi is connected to the input end of the window voltage comparator, the output end of the window voltage comparator is connected with the control end of the 1-to-2-path analog switch, the first feedback branch comprises a second resistor, and the second feedback branch comprises a third resistor, and the voltage high threshold value and the voltage low threshold value of the window voltage comparator are respectively the voltage upper limit value and the voltage lower limit value of an insensitive area;
wherein the window voltage comparator comprises: the voltage comparator, the bleeder circuit used for outputting the high threshold value of the said voltage, the absolute value circuit used for converting the said voltage input signal Vi to its absolute value, the output end of the said absolute value circuit is connected with inverting input end of the said voltage comparator, the output end of the said bleeder circuit is connected with the in-phase input end of the said voltage comparator, the output end of the said voltage comparator is connected with control end of the said 1-to-2 way analog switch;
wherein the absolute value circuit includes: the output end of the second operational amplifier is connected with the inverting input end of the voltage comparator through the sixth resistor, the inverting input end and the non-inverting input end of the second operational amplifier are respectively connected with the inverting input end of the zero-crossing comparator through the fourth resistor and the fifth resistor, the non-inverting input end of the second operational amplifier is connected with the ground through the switch K, the driving control circuit of the switch K is controlled by the output of the zero-crossing comparator to control the on or off of the switch K, the inverting input end of the zero-crossing comparator inputs the voltage input signal Vi, and the non-inverting input end of the zero-crossing comparator is connected with the ground;
the working principle of the failure circuit is as follows: when the voltage input signal Vi is more than or equal to 0, the zero-crossing comparator outputs a low level, the switch K is turned off through a driving control circuit of the switch K, the second operational amplifier, the fourth resistor, the fifth resistor and the sixth resistor form a differential operational amplifier, the resistance values of the fourth resistor, the fifth resistor and the sixth resistor are equal, the gain of the differential operational amplifier is +1, namely, the voltage signal v2=vi at the output end of the second operational amplifier is sent to the inverting input end of the voltage comparator, and the voltage signal v2 is compared with the voltage high threshold +ems added to the non-inverting input end of the voltage comparator;
when V2 = Vi < +Ems is more than or equal to 0, the voltage comparator outputs a high level to the control end of the 1-to-2 analog switch, a voltage input signal Vi is obtained by the inverter and is in phase with Vo through an inverting proportion operational amplifier circuit formed by the first operational amplifier, the first resistor and the third resistor, vo/Vi = R3/R1, vo is a voltage output signal of a failure circuit, R1 refers to the first resistor, R3 refers to the third resistor, and the resistance value of the first resistor is far greater than that of the third resistor, so Vo/Vi < <1;
when v2=vi+ems, the voltage comparator outputs a low level to the control end of the 1-to-2 analog switch, the voltage input signal Vi obtains-Vi through the inverter, and then Vo and Vi are in phase through an inverting proportional operational amplifier circuit formed by the first operational amplifier, the first resistor and the second resistor, vo/vi=r2/R1, R2 refers to the second resistor, and the resistance value of the first resistor is equal to the resistance value of the second resistor, so Vo/vi=1.
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201710433139.9A CN107040228B (en) | 2017-06-09 | 2017-06-09 | Failure circuit suitable for nonlinear regulator |
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| Application Number | Priority Date | Filing Date | Title |
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| CN201710433139.9A CN107040228B (en) | 2017-06-09 | 2017-06-09 | Failure circuit suitable for nonlinear regulator |
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| CN107040228A CN107040228A (en) | 2017-08-11 |
| CN107040228B true CN107040228B (en) | 2023-09-26 |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN108768311B (en) * | 2018-07-09 | 2023-08-25 | 佛山科学技术学院 | Nonlinear regulator and dead zone circuit thereof |
| CN113822086A (en) * | 2021-09-10 | 2021-12-21 | 江南大学 | Novel diode-free absolute value circuit |
Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102201792A (en) * | 2010-03-25 | 2011-09-28 | 上海沙丘微电子有限公司 | Automatic gain control circuit of audio power amplifier |
| JP2013251657A (en) * | 2012-05-31 | 2013-12-12 | New Japan Radio Co Ltd | Voltage follower input type differential amplifier |
| CN206790449U (en) * | 2017-06-09 | 2017-12-22 | 佛山科学技术学院 | A kind of failure circuit suitable for dead-band regulator |
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2017
- 2017-06-09 CN CN201710433139.9A patent/CN107040228B/en active Active
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102201792A (en) * | 2010-03-25 | 2011-09-28 | 上海沙丘微电子有限公司 | Automatic gain control circuit of audio power amplifier |
| JP2013251657A (en) * | 2012-05-31 | 2013-12-12 | New Japan Radio Co Ltd | Voltage follower input type differential amplifier |
| CN206790449U (en) * | 2017-06-09 | 2017-12-22 | 佛山科学技术学院 | A kind of failure circuit suitable for dead-band regulator |
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