CN106774572B - Miller-compensated circuit and electronic circuit - Google Patents

Miller-compensated circuit and electronic circuit Download PDF

Info

Publication number
CN106774572B
CN106774572B CN201611123817.3A CN201611123817A CN106774572B CN 106774572 B CN106774572 B CN 106774572B CN 201611123817 A CN201611123817 A CN 201611123817A CN 106774572 B CN106774572 B CN 106774572B
Authority
CN
China
Prior art keywords
miller
output
output transistor
circuit
connect
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
CN201611123817.3A
Other languages
Chinese (zh)
Other versions
CN106774572A (en
Inventor
苏强
奕江涛
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Guangzhou Huizhi Microelectronics Co.,Ltd.
Original Assignee
GUANGZHOU HUIZHI MICROELECTRONIC CO Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by GUANGZHOU HUIZHI MICROELECTRONIC CO Ltd filed Critical GUANGZHOU HUIZHI MICROELECTRONIC CO Ltd
Priority to CN201611123817.3A priority Critical patent/CN106774572B/en
Publication of CN106774572A publication Critical patent/CN106774572A/en
Priority to PCT/CN2017/115340 priority patent/WO2018103754A1/en
Application granted granted Critical
Publication of CN106774572B publication Critical patent/CN106774572B/en
Priority to US16/409,848 priority patent/US10763796B2/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/38—Positive-feedback circuit arrangements without negative feedback
    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
    • G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
    • G05F1/10—Regulating voltage or current
    • G05F1/46—Regulating voltage or current wherein the variable actually regulated by the final control device is dc
    • G05F1/56—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices
    • G05F1/561—Voltage to current converters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
    • H03F1/08—Modifications of amplifiers to reduce detrimental influences of internal impedances of amplifying elements
    • H03F1/14—Modifications of amplifiers to reduce detrimental influences of internal impedances of amplifying elements by use of neutralising means
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/45—Differential amplifiers
    • H03F3/45071—Differential amplifiers with semiconductor devices only
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
    • H03F3/45—Differential amplifiers
    • H03F3/45071—Differential amplifiers with semiconductor devices only
    • H03F3/45076—Differential amplifiers with semiconductor devices only characterised by the way of implementation of the active amplifying circuit in the differential amplifier
    • H03F3/45475—Differential amplifiers with semiconductor devices only characterised by the way of implementation of the active amplifying circuit in the differential amplifier using IC blocks as the active amplifying circuit
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2200/00—Indexing scheme relating to amplifiers
    • H03F2200/129—Indexing scheme relating to amplifiers there being a feedback over the complete amplifier
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2203/00—Indexing scheme relating to amplifiers with only discharge tubes or only semiconductor devices as amplifying elements covered by H03F3/00
    • H03F2203/45—Indexing scheme relating to differential amplifiers
    • H03F2203/45116—Feedback coupled to the input of the differential amplifier
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2203/00—Indexing scheme relating to amplifiers with only discharge tubes or only semiconductor devices as amplifying elements covered by H03F3/00
    • H03F2203/45—Indexing scheme relating to differential amplifiers
    • H03F2203/45511—Indexing scheme relating to differential amplifiers the feedback circuit [FBC] comprising one or more transistor stages, e.g. cascaded stages of the dif amp, and being coupled between the loading circuit [LC] and the input circuit [IC]
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2203/00—Indexing scheme relating to amplifiers with only discharge tubes or only semiconductor devices as amplifying elements covered by H03F3/00
    • H03F2203/45—Indexing scheme relating to differential amplifiers
    • H03F2203/45512—Indexing scheme relating to differential amplifiers the FBC comprising one or more capacitors, not being switched capacitors, and being coupled between the LC and the IC
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2203/00—Indexing scheme relating to amplifiers with only discharge tubes or only semiconductor devices as amplifying elements covered by H03F3/00
    • H03F2203/45—Indexing scheme relating to differential amplifiers
    • H03F2203/45528—Indexing scheme relating to differential amplifiers the FBC comprising one or more passive resistors and being coupled between the LC and the IC
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03F—AMPLIFIERS
    • H03F2203/00—Indexing scheme relating to amplifiers with only discharge tubes or only semiconductor devices as amplifying elements covered by H03F3/00
    • H03F2203/45—Indexing scheme relating to differential amplifiers
    • H03F2203/45534—Indexing scheme relating to differential amplifiers the FBC comprising multiple switches and being coupled between the LC and the IC

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Automation & Control Theory (AREA)
  • Amplifiers (AREA)

Abstract

The embodiment of the invention discloses a kind of miller-compensated circuit and electronic circuit, the compensation circuit includes：Difference amplifier, output transistor, load, miller capacitance, follower and current sampling circuit；The output end of the reverse input end of difference amplifier, the input signal for connecing miller-compensated circuit, positive input and output transistor connects, and output end is connect with output transistor, miller capacitance respectively；The first end of output transistor is connect with the first power supply, and the output end connection of second end and difference amplifier, third end is voltage output end, is connected respectively with positive input and load；The other end of load is connect with second source；The other end of miller capacitance is connect with the output end of current sampling circuit and follower simultaneously；The output end of follower is connect with the output end of miller capacitance and current sampling circuit；Current sampling circuit samples the first electric current of output transistor.

Description

Miller-compensated circuit and electronic circuit
Technical field
The present invention relates to electronic technology field more particularly to a kind of miller-compensated circuits and electronic circuit.
Background technology
Feedback control loop is got a lot of applications in electronic circuit, voltage adjuster, lock such as industrial quarters large-scale use Xiang Huan, analog-digital converter etc. are all based on feedback control loop and realize.But usually there is wild effect in feedback control loop, in practice The stability of feedback control loop is ensured often through loop compensation circuit.
Miller-compensated is a kind of general loop compensation circuit.But it is miller-compensated to introduce a Right-half-plant zero, this The bandwidth of the stability and limit feedback loop of feedback control loop will be largely effected on, so generally this can be eliminated using some way Zero changes its position to make it become Left half-plane zero.Fig. 1 is exactly a kind of common Miller benefit with follower Repay feedback control loop.The purpose for the follower being made of current source Ib and P channel MOS transistor MPF in Fig. 1 is exactly to eliminate Miller benefit The feedforward path repaid, to eliminate Right-half-plant zero.At this moment a new Left half-plane zero will be also introduced, position is：
Wherein ωzeroRepresent dead-center position, Gm,MPFRepresent the mutual conductance of PMOS transistor MPF, CcFor miller-compensated electric capacity Cc. Second pole location of feedback control loop is：
Wherein ωp2Represent the second pole location, Gm,MPORepresent the mutual conductance of PMOS output transistors MPO, CLIt represents in load Load capacitance.If compensating the Left half-plane zero using the second pole, need to meet relational expression ωzero=α * ωp2, It is equivalent to and needs Gm,MPF=α * Gm,MPO*(Cc/CL)；Here α can be preset positive real number, to ensure feedback control loop Stability and the bandwidth for extending feedback control loop.
But make ω there are one problemzero=α * ωp2Condition hardly results in satisfaction：Gm,MPOWith the electricity of output transistor MPO Rheology and change, to different output transistor MPO electric currents, cannot be satisfied Gm,MPF=α * Gm,MPO*(Cc/CL) set up.
Therefore existing miller-compensated circuit, when only output transistor MPO electric currents are constant, the second pole compensation could be utilized Left half-plane zero, and MPO electric currents Yi Dan variation once will appear compensation it is unbalance, it is poor to compensation effect occur, compensate stability The problems such as poor.
Invention content
In view of this, an embodiment of the present invention is intended to provide a kind of miller-compensated circuit and electronic circuit, expect to solve existing The compensation instability problem of miller-compensated circuit.
In order to achieve the above objectives, the technical proposal of the invention is realized in this way：
First aspect of the embodiment of the present invention provides a kind of miller-compensated circuit, including：Difference amplifier, output transistor, Load, miller capacitance, follower and current sampling circuit；
The difference amplifier includes reverse input end, positive input and an output end；Wherein, the reversed input End, the input signal for connecing the miller-compensated circuit；The output end of the positive input and the output transistor connects It connects；The output end of the difference amplifier is connect with the output transistor, the miller capacitance respectively；
The output transistor includes first end, second end and third end；Wherein, the first end connects with the first power supply It connects；The second end is connect with the output end of the difference amplifier, the third end be voltage output end, respectively with the difference Divide the positive input and the load connection of amplifier；
Described load one end is connect with the third end of the output transistor, and the other end is connect with second source；
Described miller capacitance one end is connect with the output of the difference amplifier, and the other end is electric with the current sample respectively Road is connected with the output end of the follower；
The input terminal of the follower is connect with the third end of the output transistor, and output end is electric with the Miller respectively Appearance is connected with the output end of the current sampling circuit；
The current sampling circuit samples the first electric current of the output transistor, the second electric current is obtained, by institute The output end that second circuit is stated in the current sampling circuit exports；Wherein, second electric current meets with first electric current Preset ratio relationship.
Based on said program, the miller-compensated circuit further includes：Feedback network；
The third end of the output transistor is connected by the positive input of the feedback network and the difference amplifier It connects.
Based on said program, the miller-compensated circuit further includes：Common mode gain circuit；
The follower is connect by the common mode gain circuit with the third end of the output transistor.
Based on said program, the gain range of the gain circuitry is more than 0.
Based on said program, the output transistor includes：Metal oxide semiconductor field-effect metal-oxide-semiconductor or ambipolar three Pole pipe.
Based on said program, when the output transistor is the metal-oxide-semiconductor, the follower includes：Metal-oxide-semiconductor；
When the output transistor is the double pole triode, the follower includes：Double pole triode.
Based on said program, when first power supply is positive supply, the second source is zero power supply；
When the second source is positive supply, first power supply is zero power supply.
Based on said program,
The follower includes：Metal oxide semiconductor field-effect metal-oxide-semiconductor or double pole triode.
Second aspect of the embodiment of the present invention provides a kind of electronic circuit, including one in above-mentioned miller-compensated circuit or It is multiple.
Miller-compensated circuit and electronic circuit provided in an embodiment of the present invention, introduce current sampling circuit, current sample Circuit provides an equal electric current than the curent change in output transistor by the circuit of acquisition output transistor for follower Source, so that the mutual conductance of output transistor and follower carries out the variation of grade ratio, it is solid using one in the prior art to solve Determine power supply and provide electric current for follower, the curent change of output transistor can not be followed and the compensation unbalance that changes, to It solves curent change in only output transistor, the mutual conductance of output transistor is caused to change, and the mutual conductance of follower is constant, leads The compensation unbalance of cause improves compensation stability and compensation effect.
Description of the drawings
Fig. 1 is a kind of electrical block diagram of miller-compensated circuit；
Fig. 2A is the electrical block diagram of the first miller-compensated circuit provided in an embodiment of the present invention；
Fig. 2 B are the electrical block diagram of second provided in an embodiment of the present invention miller-compensated circuit；
Fig. 2 C are the electrical block diagram of the third miller-compensated circuit provided in an embodiment of the present invention；
Fig. 3 is the electrical block diagram of the 4th kind of miller-compensated circuit provided in an embodiment of the present invention；
Fig. 4 is the optional electrical block diagram of 4 kinds of output transistors provided in an embodiment of the present invention；
Fig. 5 is the structural schematic diagram for the transistor that 4 kinds of followers provided in an embodiment of the present invention may include；
Fig. 6 is the electrical block diagram of the 5th kind of miller-compensated circuit provided in an embodiment of the present invention；
Fig. 7 is the electrical block diagram of the 6th kind of miller-compensated circuit provided in an embodiment of the present invention.
Specific implementation mode
Technical scheme of the present invention is further elaborated below in conjunction with Figure of description and specific embodiment.
As shown in Figure 2 A, the present embodiment provides a kind of miller-compensated circuits, including：Difference amplifier 310, output transistor 320, load 330, miller capacitance 340, follower 350 and current sampling circuit 360；
The difference amplifier 310 includes reverse input end, positive input and an output end；Wherein, described reversed Input terminal, the input signal VIN for connecing the miller-compensated circuit；The positive input and the output transistor 320 Output end connection；The output end of the difference amplifier 310, respectively with the output transistor 320, the miller capacitance 340 connections；
The output transistor 320 includes first end, second end and third end；Wherein, the first end and the first power supply Connection；The second end is connect with the output end of the difference amplifier 310, and the third end is voltage output end VOUT, point It is not connect with the positive input of the difference amplifier 310 and the load 330；
330 one end of the load are connect with the third end of the output transistor 320, and the other end is connect with second source；
340 one end of the miller capacitance is connect with the output of the difference amplifier 310, the other end respectively with the electric current Sample circuit is connected with the output end of the follower；
The input terminal of the follower 350 is connect with the third end of the output transistor 320, output end respectively with it is described Miller capacitance 340 is connected with the output end of the current sampling circuit 360；
The current sampling circuit 360 samples the first electric current of the output transistor 320, obtains the second electricity Stream, the output end by the second circuit in the current sampling circuit 360 export；Wherein, second electric current and described the One electric current meets preset ratio relationship.
The miller-compensated circuit described in the present embodiment, introduces current sampling circuit, current sampling circuit one here Aspect can acquire electric current current on output transistor 320, on the other hand according to the first electric current currently acquired, form second Electric current.Here the ratio between the second electric current and first electric current meets always preset ratio relationship.For example, the first electric current It is equal to preset value always with the current ratio of the second electric current.In this case, if the first curent change, second electric current can be sent out The variation of raw equal proportion, the variation of first electric current can be followed and change by being equivalent to the second electric current.Output transistor 320 across Lead with the mutual conductance of the follower 350 be presented with the electric current that each flows through it is positively related.First electric current is described defeated Go out the electric current on transistor 320, second electric current is the electric current on the follower 350, in this case, it is clear that output crystal Electric current grade ratio variation on pipe 320 and follower 350, the variation synchronous with the mutual conductance of follower 350 of output transistor 320, to The electric current just solved on output transistor 320 in the prior art is possible to change, and the electric current flowed through on the follower is not Variation, leads to the asynchronous variation of mutual conductance between output transistor 320 and follower 350, unbalance ask is compensated caused by Topic, and then solve the problems, such as that compensation caused by 320 current drift of output transistor is unstable.
In some embodiments, as shown in Figure 2 B, the miller-compensated circuit further includes：Feedback network 370；
The third end of the output transistor 320, just by the feedback network 370 and the difference amplifier 310 It is connected to input terminal.
The miller-compensated circuit described in the present embodiment further includes feedback network, and the feedback network 370 may include multiple Electronic element can be active electric network or passive network.The introducing of the feedback network, can be by adjusting the defeated of feedback network Enter the circuit structure between end and output end, the voltage output end that can adjust output transistor 320 is input to difference amplifier The voltage value of 310 positive input, to meet different usage scenarios.
For example, the feedback network may include adjustable resistance, the positive input of the difference amplifier 310 with it is described anti- The adjustable end connection for presenting network, by adjusting the position at adjustable end, it is clear that can adjust and be input to the positive defeated of difference amplifier Enter the voltage at end.Certainly, the difference amplifier 310 may also include it is multiple series winding and/or and even impedor, pass through The impedance value and/or connection relation for adjusting each impedor can adjust and be input to the positive input of the difference amplifier 301 The voltage at end.
In some embodiments, as shown in Figure 2 C, the miller-compensated circuit further includes：Common mode gain circuit 380；
The follower 350 is connect by the common mode gain circuit 380 with the third end of the output transistor 320.
The third end of output transistor is voltage output end, and the common mode gain circuit 380 is located at institute in the present embodiment It states between follower 350 and the third end of the output transistor 320.Here common mode gain circuit 380 can be not change friendship The phase for flowing signal carries out the circuit of signal amplification.It, can be in the present embodiment by the introducing of the common mode gain circuit 380 Ensure miller-compensated Property of Negative Feedback, and then ensures the stability of miller-compensated circuit；Simultaneously by adjusting common mode gain electricity The gain on road 380, thus it is possible to vary the gain of miller-compensated feedback loop, to adapt to different working environments.
For example, the gain range of the gain circuitry is more than 0.The gain range can take for 0.5,1,1.5,2 or 3 etc. Value.
In the present embodiment, 320 metal oxide semiconductor field-effect metal-oxide-semiconductor of the output transistor or ambipolar three pole Pipe.
The metal-oxide-semiconductor can be divided into N substrate, PMOS tube and substrate P, the NMOS tube of N-channel of P-channel again.Here N linings Bottom, P-channel, substrate P and N-channel contribute to describe the electrically charged attribute of corresponding component composition material itself institute, can join in detail See the prior art, is not just repeated herein.
The double pole triode can be divided into bipolar npn type triode and positive-negative-positive double pole triode again.
The output transistor 320 can be any one of the above type in the present embodiment.
The follower 350 may include at least one transistor in the present embodiment, and certainly, the follower 350 may be used also Including the linear element that one or more is connect with the transistor, for example, resistance.Certainly, the follower 350 may also include Multiple cascade transistors, in short, the mutual conductance of follower 350 described in the present embodiment and the electric current flowed through thereon are proportionate i.e. It can.
The transistor that the follower 350 includes in the present embodiment can be the metal-oxide-semiconductor or double pole triode.It is logical Often metal-oxide-semiconductor here equally can be NMOS tube or PMOS tube；The double pole triode can be positive-negative-positive double pole triode or Bipolar npn type triode.
In order to ensure the mutual conductance of follower 350 and output transistor 320 keeps accurate grade ratio to change, in the present embodiment, When the output transistor is the metal-oxide-semiconductor, the follower includes：Metal-oxide-semiconductor；When the output transistor is described bipolar When type triode, the follower includes：Double pole triode.
In this case, using same type of crystal between the output transistor 320 and the follower 350 Pipe can preferably ensure the mutual conductance grade ratio variation of output transistor 320 and follower 350 in this way.So that it is guaranteed that compensation is steady Qualitative and compensation effect.Certainly, in specific implementation, the transistor that the output transistor 320 and follower 350 include also may be used To belong to different types of transistor, but may need to consider different type transistor when configuring each transistor at this time If desired mutual conductance keeps stability to the sensibility different problems of electric current, it may be necessary to which other electronic components are asked to solve this Topic, for example, being realized by being connected to non-linear element etc. than variation etc..It can certainly be by according to different types of crystal The parameter of pipe so that it even belongs to the transistor of different types, can also meet and mutual conductance etc. occurs than variation with electric current Characteristic, such as so that the product phase of the mobility of different types of transistor, the length and width when gate medium capacitance of unit area Deng.
In some embodiments, when first power supply is positive supply, the second source is zero power supply；
When the second source is positive supply, first power supply is zero power supply.
Zero power supply can be the earth point or earthing power supply being connect with earth point in the present embodiment.Certainly, in this reality It can be reference power source to apply zero power supply described in example, and the positive supply is that the voltage value provided is higher than the power supply of zero power supply. It sets zero power supply to earth point in the present embodiment, the voltage provided needed for positive supply can be provided, can be reduced to just The requirement of power supply reduces the electricity that circuit is consumed.
A kind of electronic circuit is also provided in the present embodiment, it may include the miller-compensated circuit of any one of the above.The electronics Circuit further includes other electronic modules, other electronic modules can be connect with the reverse input end of the difference channel, for carrying For the VIN, can also be connect with the third end of the output transistor 320, the VOUT for receiving the three-polar output. In short, the electronic circuit provided in the present embodiment can have because including any one miller-compensated circuit of aforementioned schemes There is miller-compensated stabilization, reduces the unstable caused various circuit operation irregularity phenomenons because miller-compensated.
Several specific examples are provided below in conjunction with above-described embodiment：
Example one：
As shown in figure 3, a kind of miller-compensated circuit of this example offer, including difference amplifier 100, output transistor 102, Feedback network 112 and load 114.
The anti-phase input termination input signal VIN of the difference amplifier 100, the normal phase input end F of difference amplifier 100 The output of the output, difference amplifier 100 that connect feedback network 112 terminates the input terminal B of output transistor 102, output transistor 102 second end E connects output VOUT, the third termination power 1 of output transistor 102, the input termination output of feedback network 112 VOUT, load 114 is between output VOUT and power supply 2；Including common mode gain circuit 106, it is characterized in that common mode gain circuit is defeated Enter to connect node E, output meet node D, be input to output small-signal gain be A, A is positive real number；It is special including follower 108 Sign is that follower input meets node D, output meets node C；Including output current sample circuit 104, it is characterized in that output current is adopted Sample circuit samples the electric current of output transistor 102, to obtain the electric current proportional with the electric current IO of output transistor ISNS wherein ISNS=IO/M, M are the real number being manually set, electric current ISNS injection nodes C；Including capacitance 110, it is characterized in that electric Hold 110 1 terminated nodes B, a terminated nodes C, this capacitance act as miller capacitance；Including power supply 1, power supply 2, power supply 1, power supply 2 For positive supply and zero power supply or as one in ground GND, when power supply 1 is positive supply, power supply 2 is zero power supply, works as power supply 1 power supply 2 when being zero power supply is positive supply.
As shown in figure 4, output transistor 102 can be realized by PMOS transistor 200, realized by PNP transistor 202, by NMOS transistor 204 is realized or is realized by NPN transistor 206.If output transistor 102 is real by PMOS transistor 200 Existing, the second pole of feedback control loop is at this time：
Gm,200For the mutual conductance of PMOS transistor 200, μpFor the mobility of PMOS, COx, 200For the gate medium electricity of unit area Hold,For the breadth length ratio of PMOS transistor 200.
If output transistor 102 is realized by PNP transistor 202, the second pole of feedback control loop is at this time：
Wherein Gm,202For the mutual conductance of PNP transistor 202, Vt is thermal voltage.If output transistor 102 is by NMOS transistor 204 realize that the second pole of feedback control loop is at this time：
Wherein GM, 204For the mutual conductance of NMOS transistor 204, μnFor the mobility of NMOS, COx, 204It is situated between for the grid of unit area Matter capacitance,For the breadth length ratio of NMOS transistor 204.
If output transistor 102 is realized by NPN transistor 206, the second pole of feedback control loop is at this time：
Gm,206For the mutual conductance of NPN transistor 206.
As shown in figure 5, follower 108 can by PMOS transistor 300, PNP transistor 302, NMOS transistor 304 or NPN transistor 306 is realized.
If follower 108 is realized by PMOS transistor 300, the Left half-plane zero of feedback control loop is at this time：
Gm,300For the mutual conductance of PMOS transistor 300,For the breadth length ratio of PMOS transistor 300, the COx, 300For The gate medium capacitance of the unit area of PMOS transistor 300；The M is similarly preset ratio coefficient.
If follower 108 is realized by PNP transistor 302, the Left half-plane zero of feedback control loop is at this time：
Gm,302For the mutual conductance of PNP transistor 302.
If follower 108 is realized by NMOS transistor 304, the Left half-plane zero of feedback control loop is at this time：
Gm,304For the mutual conductance of NMOS transistor 304, μnFor the technique mutual conductance of NMOS,For NMOS transistor 304 Breadth length ratio；The COx, 304For the gate medium capacitance of the unit area of NMOS transistor 304.
If follower 108 is realized by NPN transistor 306, the Left half-plane zero of feedback control loop is at this time：
Gm,306For the mutual conductance of NPN transistor 306.
Due to the left side plane zero ω of feedback control loopzeroWith the second pole ωp2All with the electric current IO of output transistor Increase and increase, reduce with the reduction of the electric current IO of output transistor, and the electricity of its variation coefficient and output transistor It is unrelated to flow IO, so in output transistor curent change, can be very good to ensure left side plane zero ωzeroWith the second pole ωp2Mutually compensate for, the mutual conductance to solve the problems, such as output transistor is unbalance with being compensated caused by curent change.
Example two：
As shown in fig. 6, this example provides a kind of miller-compensated circuit.Its output transistor is by PMOS transistor 200 real It is existing；Follower is realized by PMOS transistor 300；PMOS transistor 400 constitutes output current sample circuit, PMOS transistor 400 drain current is sample rate current ISNS；Resistance 402 and resistance 404 constitute feedback circuit, and output node E is feedback electricity The input on road, node F are the output of feedback circuit；Resistance 408 and capacitance 406 constitute load；The input of common mode gain circuit and Output end short circuit, so the small-signal gain for being input to output is A=1.The second pole of feedback control loop is at this time：
The Left half-plane zero of feedback control loop is：
By ωzero=α * ωp2, can obtain
The electric current IO of this formula and output transistor is unrelated, it is possible to when ensureing output transistor curent change well, Left side plane zero ωzeroWith the second pole ωp2Mutually compensate for, to solve output transistor with curent change and mutual conductance becomes The problem of change, caused compensation failure.
Example three：
As shown in fig. 7, this example provides another miller-compensated circuit, output transistor is by PNP transistor 202 real It is existing；Follower is realized by NPN transistor 306；PNP transistor 500, NPN transistor 502, NPN transistor 504 constitute output The collector current of current sampling circuit, NPN transistor 504 is sample rate current ISNS；Current source 506 and PNP transistor 508 Common mode gain circuit is constituted, the small-signal gain for being input to output is A=1；Current source 510 and capacitance 512 constitute load；Instead Present the input and output side short circuit of network.The second pole of feedback control loop is at this time：
The Left half-plane zero of feedback control loop is：
By ωzero=α * ωp2, α=M can be obtained.
The electric current IO of this formula and output transistor is unrelated, it is possible to when ensureing output transistor curent change well, Left side plane zero ωzeroWith the second pole ωp2Mutually compensate for, to solve caused by the circuit of output transistor compensate lose The phenomenon that losing.
It is worth noting that：In Fig. 1 to Fig. 7 that invention provides, VDD refers to power supply, it is not intended that being same Power supply or provide with pressure value or with the power supply of electric current；GND indicates to be grounded.
The above description is merely a specific embodiment, but scope of protection of the present invention is not limited thereto, any Those familiar with the art in the technical scope disclosed by the present invention, can easily think of the change or the replacement, and should all contain Lid is within protection scope of the present invention.Therefore, protection scope of the present invention should be based on the protection scope of the described claims.

Claims (9)

1. a kind of miller-compensated circuit, which is characterized in that including：Difference amplifier, output transistor, load, miller capacitance, with With device and current sampling circuit；
The difference amplifier includes reverse input end, positive input and an output end；Wherein, the reverse input end, Input signal for connecing the miller-compensated circuit；The positive input is connect with the output end of the output transistor； The output end of the difference amplifier is connect with the output transistor, the miller capacitance respectively；
The output transistor includes first end, second end and third end；Wherein, the first end is connect with the first power supply；Institute It states second end to connect with the output end of the difference amplifier, the third end is voltage output end, is put with the difference respectively The positive input of big device and load connection；
Described load one end is connect with the third end of the output transistor, and the other end is connect with second source；
Described miller capacitance one end is connect with the output of the difference amplifier, the other end respectively with the current sampling circuit and The output end of the follower connects；
The input terminal of the follower is connect with the third end of the output transistor, output end respectively with the miller capacitance and The output end of the current sampling circuit connects；
The current sampling circuit samples the first electric current of the output transistor, obtains the second electric current, by described the Two electric currents are exported in the output end of the current sampling circuit, wherein second electric current meets default with first electric current Proportionate relationship；
When the output transistor is PMOS tube, the first end, second end and third end correspond to the PMOS tube respectively Source electrode, grid and drain electrode；When the output transistor is NMOS tube, the first end, second end and third end correspond to respectively Drain electrode, grid and the source electrode of the NMOS tube；When the output transistor be PNP triodes when, the first end, second end and Third end corresponds to the emitter of the PNP triode, base emitter-base bandgap grading and collector respectively；When the output transistor is NPN three-levels Guan Shi, the first end, second end and third end correspond to collector, base stage and the emitter of the NPN triode respectively.
2. miller-compensated circuit according to claim 1, which is characterized in that
The miller-compensated circuit further includes：Feedback network；
The third end of the output transistor is connect by the feedback network with the positive input of the difference amplifier.
3. the miller-compensated circuit stated according to claims 1 or 2, which is characterized in that
The miller-compensated circuit further includes：Common mode gain circuit；
The follower is connect by the common mode gain circuit with the third end of the output transistor.
4. miller-compensated circuit according to claim 3, which is characterized in that
The gain range of the gain circuitry is more than 0.
5. miller-compensated circuit according to claim 1 or 2, which is characterized in that
The output transistor includes：Metal oxide semiconductor field-effect metal-oxide-semiconductor or double pole triode.
6. miller-compensated circuit according to claim 5, which is characterized in that
When the output transistor is the metal-oxide-semiconductor, the follower includes：Metal-oxide-semiconductor；
When the output transistor is the double pole triode, the follower includes：Double pole triode.
7. miller-compensated circuit according to claim 1 or 2, which is characterized in that
When first power supply is positive supply, the second source is zero power supply；
When the second source is positive supply, first power supply is zero power supply.
8. miller-compensated circuit according to claim 1 or 2, which is characterized in that
The follower includes：Metal oxide semiconductor field-effect metal-oxide-semiconductor or double pole triode.
9. a kind of electronic circuit, which is characterized in that including the miller-compensated circuit of claim 1 to 8 any one of them.
CN201611123817.3A 2016-12-08 2016-12-08 Miller-compensated circuit and electronic circuit Active CN106774572B (en)

Priority Applications (3)

Application Number Priority Date Filing Date Title
CN201611123817.3A CN106774572B (en) 2016-12-08 2016-12-08 Miller-compensated circuit and electronic circuit
PCT/CN2017/115340 WO2018103754A1 (en) 2016-12-08 2017-12-08 Miller compensation circuit and electronic circuit
US16/409,848 US10763796B2 (en) 2016-12-08 2019-05-12 Miller compensation circuit and electronic circuit

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN201611123817.3A CN106774572B (en) 2016-12-08 2016-12-08 Miller-compensated circuit and electronic circuit

Publications (2)

Publication Number Publication Date
CN106774572A CN106774572A (en) 2017-05-31
CN106774572B true CN106774572B (en) 2018-10-26

Family

ID=58881677

Family Applications (1)

Application Number Title Priority Date Filing Date
CN201611123817.3A Active CN106774572B (en) 2016-12-08 2016-12-08 Miller-compensated circuit and electronic circuit

Country Status (3)

Country Link
US (1) US10763796B2 (en)
CN (1) CN106774572B (en)
WO (1) WO2018103754A1 (en)

Families Citing this family (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN106774572B (en) * 2016-12-08 2018-10-26 广州慧智微电子有限公司 Miller-compensated circuit and electronic circuit
FR3071628A1 (en) * 2017-09-25 2019-03-29 STMicroelectronics (Alps) SAS MILLER STABILIZATION AND COMPENSATION DEVICE AND METHOD
CN113342108B (en) * 2021-06-08 2022-09-06 成都华微电子科技股份有限公司 Parallel operational amplifier zero compensation circuit
CN117792300B (en) * 2024-02-23 2024-05-14 普源精电科技股份有限公司 Amplifier and oscilloscope

Family Cites Families (11)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2356991B (en) * 1999-12-02 2003-10-22 Zetex Plc A negative feedback amplifier circuit
US7088082B2 (en) * 2003-12-16 2006-08-08 Quick Logic Corporation Regulator with variable capacitor for stability compensation
US7589507B2 (en) * 2005-12-30 2009-09-15 St-Ericsson Sa Low dropout regulator with stability compensation
US7893670B2 (en) * 2009-02-20 2011-02-22 Standard Microsystems Corporation Frequency compensation scheme for stabilizing the LDO using external NPN in HV domain
CN101847028B (en) * 2010-04-14 2012-03-28 广州市广晟微电子有限公司 Dynamic compensation circuit with ultra-low power consumption and linear regulator with the same
CN102063148B (en) * 2010-12-31 2015-02-04 上海集成电路研发中心有限公司 Reference voltage generation circuit
CN103135642B (en) * 2011-11-23 2014-12-10 上海华虹宏力半导体制造有限公司 Loop circuit compensating circuit
CN103149962B (en) * 2011-12-07 2015-07-22 深圳市汇春科技有限公司 Low voltage-drop voltage stabilizer with extremely low static current
CN102681581A (en) * 2012-05-24 2012-09-19 苏州脉科库博环保科技有限公司 High-precision and high-speed LDO (low dropout regulator) circuit based on large-slew-rate error amplifier
CN103064455B (en) * 2012-12-07 2016-06-08 广州慧智微电子有限公司 A kind of miller-compensated linear voltage regulator circuit of dynamic zero point based on zero-regulator resistor
CN106774572B (en) * 2016-12-08 2018-10-26 广州慧智微电子有限公司 Miller-compensated circuit and electronic circuit

Also Published As

Publication number Publication date
CN106774572A (en) 2017-05-31
WO2018103754A1 (en) 2018-06-14
US20190267952A1 (en) 2019-08-29
US10763796B2 (en) 2020-09-01

Similar Documents

Publication Publication Date Title
CN106774572B (en) Miller-compensated circuit and electronic circuit
CN102931972B (en) Complementary metal-oxide-semiconductor (CMOS) input buffer
CN106200732A (en) Generate the circuit of output voltage and the method to set up of the output voltage of low dropout voltage regulator
CN102722207A (en) Low dropout regulator (LDO)
Maheshwari Voltage-mode full-wave precision rectifier and an extended application as ASK/BPSK circuit using a single EXCCII
CN106027030B (en) A kind of high speed High Linear fully differential follower
CN110908423B (en) Cascaded complementary source follower and control circuit
CN101839941B (en) Signal sensing amplifier
CN104090619A (en) Digital-analog hybrid circuit reference source with high work stability
CN111176358A (en) Low-power-consumption low-dropout linear voltage regulator
CN104426523A (en) Waveform transformation circuit with reduced jitter
Psychalinos et al. Low-voltage current controlled current conveyor
US7961049B2 (en) Amplifier with compensated gate bias
CN104076857A (en) Improved mixed-signal circuit
CN106227287A (en) There is the low pressure difference linear voltage regulator of protection circuit
Safari et al. A simple low voltage, high output impedance resistor based current mirror with extremely low input and output voltage requirements
CN104079300A (en) Power switching module of digital-analog hybrid circuit reference source
CN104090620A (en) High-bandwidth digital-analog hybrid circuit reference source
CN104090617A (en) Low-dropout linear regulator of improved digital-analog hybrid circuit
CN104076858A (en) Improved mixed-signal chip
CN203950239U (en) The band gap reference of Digital Analog Hybrid Circuits
CN103279163A (en) High-power-voltage-rejection-rate capacitor-free low-voltage-difference voltage regulator
CN115498970A (en) Amplifying circuit, differential amplifying circuit and amplifier
CN102890526B (en) CMOS band-gap reference voltage source
CN104090618A (en) Low-dropout linear voltage stabilization source of digital-analog hybrid circuit

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant
CP03 Change of name, title or address
CP03 Change of name, title or address

Address after: 510663 8th floor, building C2, Chuangxin building, No. 182, Kexue Avenue, Huangpu District, Guangzhou, Guangdong

Patentee after: Guangzhou Huizhi Microelectronics Co.,Ltd.

Address before: 510663 unit 307, third floor, C2, innovation building, No. 182, science Avenue, Science City, Guangzhou high tech Industrial Development Zone, Guangzhou, Guangdong Province

Patentee before: SMARTER MICROELECTRONICS (GUANG ZHOU) Co.,Ltd.