CN106452381A - Coupling-capacitance-free instrument amplifier with direct current offset inhibition function and implementation method thereof - Google Patents
Coupling-capacitance-free instrument amplifier with direct current offset inhibition function and implementation method thereof Download PDFInfo
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- CN106452381A CN106452381A CN201611102327.5A CN201611102327A CN106452381A CN 106452381 A CN106452381 A CN 106452381A CN 201611102327 A CN201611102327 A CN 201611102327A CN 106452381 A CN106452381 A CN 106452381A
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- circuit
- amplifier
- transconductance circuit
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- transconductance
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
- H03F3/45—Differential amplifiers
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
- H03F1/26—Modifications of amplifiers to reduce influence of noise generated by amplifying elements
Abstract
The invention relates to a coupling-capacitance-free instrument amplifier with a direct current offset inhibition function and an implementation method thereof. The instrument amplifier comprises a first transconductance circuit Gm1, a second transconductance circuit Gm2, a transimpedance amplifier, a charge pump circuit, a feedback resistance network and an offset inhibition feedback circuit. The instrument amplifier can be used in an electrocardiograph detection system on a portable device, and the problem that offset voltage interferes with output saturation generation and rail-to-rail input and output is effectively solved.
Description
Technical field
The present invention relates to heart rate monitoring front end field, particularly a kind of no coupled capacitor have DC maladjustment suppression function
Instrument amplifier and its implementation.
Background technology
As portable set and sports apparatus are for the demand more and more higher of heart rate detection, this kind of equipment requirements electrocardio prison
Survey chip power-consumption is low, and external device is as few as possible, and this demand causes the instrument amplifier for ECG signal sampling to become work
The focus of industry research.
Instrument amplifier general utility functions are to amplify small-signal, and suppression is superimposed upon the big offset voltage on signal, and electrocardio is believed
Number can regard the signal being superimposed with weaker nearly DC voltage compared with strong dc voltage as, thus be accordingly used in the instrument of detection electrocardiosignal
The requirement of amplifier common mode rejection ratio is very high, simultaneously as electrocardiosignal can carry polarizing voltage and low frequency wonder, instrument is amplified
Easily there is saturation in device outfan, so the suppression of offset voltage must be carried out while being also prevented from instrument to instrument amplifier
Amplifier exports saturation, and with a portable device, therefore power consumption requirements are little, and outward element is required less, simultaneously because the heart
Signal frequency is relatively low, belongs to nearly direct current signal, coupled capacitor cannot be used to separate DC voltage based on this some reason, and this is just
The corresponding design used in the instrument amplifier of cardioelectric monitor proposes new requirement.So one kind no coupled capacitor has direct current suppression
The key for being designed to cardioelectric monitor front-end chip of the instrument amplifier of function processed.
Cardioelectric monitor front-end chip system design can be divided mainly into traditional three amplifiers structure in the world at present, that is, pass through two
Buffer is followed by a difference amplifier as differential input end and offsets common-mode voltage (reference：Spinelli E.M, " AC-
Coupled Front-End for Biopotential Measurement ", IEEE Trans.Biomedical
Engineering, SC-36 (11), Vol.50 Τ pp.391-395, March 2003) and dynamic offset canceling, that is, use
Dynamic offset cancellation circuit is inserted in instrument amplifier, and offset voltage is eliminated (reference：J.F.Witte,“A current-
feedback instrumentation amplifier with 5V offset for bidirectional highside
Current-sensing ", IEEE J.Solid-State Circuits, vol.43, no.12, pp.2769 2775,
Dec.2008.), above instrument amplifier chip is obtained in the signal detection of each electronic product and is widely applied.But it is traditional
The shortcoming of three amplifiers is that input common-mode range is little, it is impossible to comprising Voltage rails, and secondly output is easily saturated, and is especially needing low work(
In the case of consumption.Insert dynamic offset cancellation circuit advantage in instrument amplifier to be offset voltage can be suppressed, common mode
Rejection ratio can reach very high.But circuit structure is complicated, and power consumption is larger, and the interference of chopping signal can be introduced.Traditional
Three amplifier structures cause output offset excessive in common mode input compared with conference and export saturation down to chip.And electrocardiosignal input
In the case of very high for the requirement of common mode input scope.So this proposes challenge to the design of ECG detecting chip.
Content of the invention
In view of this, the purpose of the present invention is to propose to the instrument that a kind of no coupled capacitor has DC maladjustment suppression function is put
Big device and its implementation, can be used in the cardiac electricity detecting system on portable set, effectively solve offset voltage interference
There is the problem of output saturation and full amplitude of oscillation input and output.
The present invention is realized using below scheme：The instrument that a kind of no coupled capacitor has DC maladjustment suppression function is amplified
Device, including the first transconductance circuit Gm1, the second transconductance circuit Gm2, trans-impedance amplifier, charge pump circuit, feedback resistive network and
Imbalance suppression feedback circuit；
The first transconductance circuit Gm1 is connected with the output of the second transconductance circuit Gm2 and is connected to and described puts across resistance
The input of big device, used as the main amplifier of the instrument amplifier；
The first input end of the second transconductance circuit Gm2 suppresses the outfan of feedback circuit to be connected with the imbalance, uses
To provide DC offset voltage；The input of the imbalance suppression feedback circuit is connected to the outfan of the instrument amplifier,
In order to feedback loop output signal；Second input of the second transconductance circuit Gm2 is connected to the instrument through resitstance voltage divider and puts
The outfan of big device, in order to arrange the overall gain of the instrument amplifier；
The power voltage input terminal of the first transconductance circuit Gm1 and the second transconductance circuit Gm2 is connected to the electricity
Lotus pump circuit, in order to lift the input common-mode range of instrument amplifier；
Two inputs of the first transconductance circuit Gm1 are used as the input of the instrument amplifier；Described put across resistance
The outfan of big device is used as the outfan of the instrument amplifier.
Further, the imbalance suppression feedback circuit is the inverting integrator being made up of amplifier A, resistance R, electric capacity C.
Further, the first transconductance circuit Gm1 and the second transconductance circuit Gm2 is identical structure, all to serve as reasons
PMOS and equivalent resistance become the common-source amplifier with active damping resistance.
Further, the trans-impedance amplifier includes electric current summing circuit and the classAB of output stage cascade.
Present invention also offers a kind of instrument based on no coupled capacitor mentioned above with DC maladjustment suppression function
The implementation method of amplifier, specially：Differential input signal Vin1, Vin2 are converted into and difference by the first transconductance circuit Gm1
The small-signal current for dividing input signal proportional；Two inputs of the second transconductance circuit Gm2 are anti-with imbalance suppression respectively
The output of current feed circuit and feedback resistive network are connected for monitoring signal offset voltage；The input of trans-impedance amplifier is divided
It is not connected with the first transconductance circuit Gm1, the output of the second transconductance circuit Gm2, provides through processing for rear class as output stage
Signal voltage；The input of imbalance suppression feedback circuit is connected with the output of trans-impedance amplifier, for believing any nearly direct current
Number the second transconductance circuit Gm2 is fed back to, so as to offset voltage is eliminated, baseline drift is filtered, prevent amplifier output saturation；By electricity
The output of lotus pump circuit is connected with the supply voltage of the first transconductance circuit Gm1, the second transconductance circuit Gm2, for lifting first
Transconductance circuit Gm1, the input common-mode range of the second transconductance circuit Gm2, so as to meet the demand of the full amplitude of oscillation input of circuit；Will feedback
One end of resistor network is connected with the output of trans-impedance amplifier, in order to monitor the output voltage of trans-impedance amplifier, by this voltage
The second transconductance circuit Gm2 is sent into after carrying out partial pressure is converted into electric current, the offset voltage of offset input signal.
Further, the filter cutoff frequency of the imbalance suppression feedback circuit is：
Wherein, A6For the resistance ratio value of feedback resistive network, R, C are respectively the electricity that connect on imbalance suppression feedback circuit
Resistance and capacitance.
Further, the first transconductance circuit Gm1 and the second transconductance circuit Gm2 is identical structure, all to serve as reasons
PMOS and equivalent resistance become the common-source amplifier with active damping resistance；The transconductance value of wherein the first transconductance circuit Gm1 is adopted
Calculated with following formula：
Wherein, R is the resistance value in the first transconductance circuit Gm1.
Compared with prior art, the present invention has following beneficial effect：The present invention can be used for the electrocardio on portable set
Detecting system, which can be held in low-power consumption environment, on the basis of the little high-gain of output voltage signal noise, using imbalance suppression
Feedback circuit, charge pump and classAB output circuit, effectively solve offset voltage interference and output saturation and the full amplitude of oscillation occur
The problem of input and output.
Description of the drawings
Fig. 1 is that the instrument amplifier circuit that the no coupled capacitor of the embodiment of the present invention has DC maladjustment suppression function is illustrated
Figure.
Fig. 2 is the mistake of the instrument amplifier circuit that the no coupled capacitor of the embodiment of the present invention has DC maladjustment suppression function
Adjust suppression feedback circuit.
Fig. 3 for the embodiment of the present invention no coupled capacitor have DC maladjustment suppression function instrument amplifier circuit across
Conductive path.
Fig. 4 for the embodiment of the present invention no coupled capacitor have DC maladjustment suppression function instrument amplifier circuit across
Impedance amplifier.
Specific embodiment
Below in conjunction with the accompanying drawings and embodiment the present invention will be further described.
The instrument amplifier that a kind of no coupled capacitor has DC maladjustment suppression function is present embodiments provided, including first
Transconductance circuit Gm1, the second transconductance circuit Gm2, trans-impedance amplifier, charge pump circuit, feedback resistive network and imbalance suppression are anti-
Current feed circuit；
The first transconductance circuit Gm1 is connected with the output of the second transconductance circuit Gm2 and is connected to and described puts across resistance
The input of big device, used as the main amplifier of the instrument amplifier；
The first input end of the second transconductance circuit Gm2 suppresses the outfan of feedback circuit to be connected with the imbalance, uses
To provide DC offset voltage；The input of the imbalance suppression feedback circuit is connected to the outfan of the instrument amplifier,
In order to feedback loop output signal；Second input of the second transconductance circuit Gm2 is connected to the instrument through resitstance voltage divider and puts
The outfan of big device, in order to arrange the overall gain of the instrument amplifier；
The power voltage input terminal of the first transconductance circuit Gm1 and the second transconductance circuit Gm2 is connected to the electricity
Lotus pump circuit, in order to lift the input common-mode range of instrument amplifier；
Two inputs of the first transconductance circuit Gm1 are used as the input of the instrument amplifier；Described put across resistance
The outfan of big device is used as the outfan of the instrument amplifier.
In the present embodiment, the imbalance suppression feedback circuit is the anti-phase integration being made up of amplifier A, resistance R, electric capacity C
Device.The DC maladjustment of the gain factor of instrument amplifier main amplifier output occurs in the input of imbalance suppression feedback circuit,
Imbalance suppression feedback circuit is used as an inverting integrator, and it is equal with normal phase input end to order about inverting input, makes main amplifier
DC maladjustment eliminate.While suppression feedback circuit of lacking of proper care is in systems as single pole high pass filter, in order to prevent instrument
Amplifier exports saturation, while keeping high-gain.
In the present embodiment, the first transconductance circuit Gm1 and the second transconductance circuit Gm2 is identical structure, to be
Become the common-source amplifier with active damping resistance by PMOS with equivalent resistance.PMOS is operated in sub-threshold region, to provide to rear class
Signal code, acts on the outfan of transconductance circuit Gm2, while exporting to trans-impedance amplifier, charge pump is in order to improve mutual conductance electricity
The supply voltage on road is to realize the input of the full amplitude of oscillation.
In the present embodiment, the trans-impedance amplifier includes electric current summing circuit and the classAB of output stage cascade.Difference
Current amplifier, floating current source composition electric current summing circuit, classAB outlet tube, electric capacity C1, C2 and classAB control electricity
Road constitutes classAB output stage.So that full swing signal and output current is provided, resitstance voltage divider and imbalance suppression feedback is acted on
Circuit.
(in Fig. 1,1 is the first transconductance circuit Gm1, and 2 is the second transconductance circuit Gm2, and 3 is trans-impedance amplifier, 4 as shown in Figure 1
For imbalance suppression feedback circuit, 5 is charge pump circuit, and 6 is feedback resistive network), the present embodiment additionally provides a kind of based on upper
No coupled capacitor described in text has the implementation method of the instrument amplifier of DC maladjustment suppression function, specially：Described first
Differential input signal Vin1, Vin2 are converted into the small-signal current proportional to differential input signal by transconductance circuit Gm1 (1)；
Two inputs of the second transconductance circuit Gm2 (2) are respectively with output and the feedback resistance net of imbalance suppression feedback circuit 4
Network 6 is connected for monitoring signal offset voltage；By the input of trans-impedance amplifier 3 respectively with the first transconductance circuit Gm1, second
The output of transconductance circuit Gm2 is connected, and provides treated signal voltage as output stage for rear class；By imbalance suppression feedback
The input of circuit is connected with the output of trans-impedance amplifier, for any nearly direct current signal is fed back to the second transconductance circuit Gm2, from
And offset voltage is eliminated, baseline drift is filtered, prevents amplifier output saturation；By the output of charge pump circuit 5 and the first mutual conductance
Circuit Gm1, the supply voltage of the second transconductance circuit Gm2 are connected, for lifting the first transconductance circuit Gm1, the second transconductance circuit
The input common-mode range of Gm2, so as to meet the demand of the full amplitude of oscillation input of circuit；Amplify by one end of feedback resistive network and across resistance
The output connection of device, in order to monitor the output voltage of trans-impedance amplifier, this voltage is carried out sending into the second mutual conductance electricity after partial pressure
Road Gm2 is converted into electric current, the offset voltage of offset input signal.
As shown in Fig. 2 in the present embodiment, it is contemplated that input signal Vin1, amplitude can be mingled with Vin2 much larger than required
The noise voltage of the offset voltage of signal, polarizing voltage, Hz noise and baseline drift, imbalance suppression feedback circuit is by amplifier
A, the integrator of resistance R, electric capacity C composition, the output to trans-impedance amplifier is integrated, export after comparing with reference level to across
Conductive path is used as voltage reference, it is contemplated that the impact of polarizing voltage and baseline drift, and imbalance suppression feedback circuit has in circuit
There is high pass filter function, can be by some extremely low frequency effect of signals suppression such as polarizing voltage and baseline drift, the filter cutoff
Frequency is：
Wherein, A6For the resistance ratio value of feedback resistive network, R, C are respectively connection on imbalance suppression feedback circuit 4
Resistance value and capacitance.
As shown in figure 3, (in Fig. 3,1 is that the first transconductance circuit Gm1,2 are power supply for the second transconductance circuit Gm2,3 and 4)
In the present embodiment, it is contemplated that the factor of input common-mode range, common mode rejection ratio and power consumption, input signal Vin1, Vin2 is by
One transconductance circuit Gm1 (1) is converted into signal code proportional thereto, input signal Vin1, and it is poor that Vin2 and transconductance circuit 1 are input into
Point being cross over circuit Gm2 (2) to second is connected, and input difference is cross over circuit to flowing out the signal code for producing Iout with second
The output current of Gm2 (2) is sued for peace, the resistance that the transconductance value of the first transconductance circuit Gm1 (1) can be by input difference to upper bridging
R determines, transconductance value is：
Wherein, R is the resistance value in the first transconductance circuit Gm1, current source 3, and 4 are cross over circuit for input difference to second
Gm2 provides bias current, makes input difference be operated in suitable scope to the second transconductance circuit Gm2, and charge pump circuit makes first
The supply voltage Vdd of transconductance circuit Gm1 rises to VH, and input difference is cross over the input common-mode range lifting of circuit Gm2 to second
To Vdd before.
(in Fig. 4,1 and 3 are electric current summing circuit, and 2 is floating current source, and 4 is classAB control electricity as shown in Figure 4
Road), in the present embodiment, the output current of two transconductance circuits is used as the input current in trans-impedance amplifier, the first mutual conductance electricity
The output current of road Gm1 and the second transconductance circuit Gm2 is Iin, is the input current of the electric current summing circuit 3 of trans-impedance amplifier,
The output current of two transconductance circuits is sued for peace in electric current summing circuit 3, when circuit stability, the electricity of two transconductance circuits
Stream is coupling, the two electric currents can be made to match by the feedback of feedback resistive network, 2 conduct of floating current source in Fig. 4
Electric current summing circuit 1 and the biasing circuit of electric current summing circuit 3, floating current source 2 flows out electric current summing circuit 1, inflow current
Summing circuit 3, the direct current biasing of the two circuits is carried out stable, while electric current summing circuit 1 and electric current summing circuit 3 is defeated
Go out to connect classAB control circuit 4, classAB 4 structures of control circuit identical with floating current source 2, classAB control circuit 4
Bias current also flows out electric current summing circuit 1, and inflow current summing circuit 3, classAB control circuit produces one relatively about 4
For stable bias voltage, it is connected with the grid of M1, M2 respectively, the gate source voltage of M1, M2 is secured, so as to also secure M1,
The quiescent current of M2, maintains circuit stability.M1, M2 are common-source amplifier structures, constitute classAB outlet tube.Electric capacity C1, C2
And classAB control circuit and classAB outlet tube collectively constitute classAB output stage, realize rail-to-rail output.
The foregoing is only presently preferred embodiments of the present invention, all impartial changes that is done according to scope of the present invention patent with
Modification, should all belong to the covering scope of the present invention.
Claims (7)
1. a kind of no coupled capacitor has the instrument amplifier of DC maladjustment suppression function, it is characterised in that：Including the first mutual conductance
Circuit Gm1, the second transconductance circuit Gm2, trans-impedance amplifier, charge pump circuit, feedback resistive network and imbalance suppression feedback electricity
Road；
The first transconductance circuit Gm1 is connected with the output of the second transconductance circuit Gm2 and is connected to the trans-impedance amplifier
Input, as the main amplifier of the instrument amplifier；
The first input end of the second transconductance circuit Gm2 suppresses the outfan of feedback circuit to be connected with the imbalance, in order to carry
For DC offset voltage；The input of the imbalance suppression feedback circuit is connected to the outfan of the instrument amplifier, in order to
Feedback loop output signal；Second input of the second transconductance circuit Gm2 is connected to the instrument amplifier through resitstance voltage divider
Outfan, in order to arrange the overall gain of the instrument amplifier；
The power voltage input terminal of the first transconductance circuit Gm1 and the second transconductance circuit Gm2 is connected to the charge pump
Circuit, in order to lift the input common-mode range of instrument amplifier；
Two inputs of the first transconductance circuit Gm1 are used as the input of the instrument amplifier；The trans-impedance amplifier
Outfan as the instrument amplifier outfan.
2. a kind of no coupled capacitor according to claim 1 has the instrument amplifier of DC maladjustment suppression function, and which is special
Levy and be：The imbalance suppression feedback circuit is the inverting integrator being made up of amplifier A, resistance R, electric capacity C.
3. a kind of no coupled capacitor according to claim 1 has the instrument amplifier of DC maladjustment suppression function, and which is special
Levy and be：The first transconductance circuit Gm1 and the second transconductance circuit Gm2 be identical structure, be all by PMOS and resistance etc.
Imitate into the common-source amplifier of the active damping resistance of band.
4. a kind of no coupled capacitor according to claim 1 has the instrument amplifier of DC maladjustment suppression function, and which is special
Levy and be：The trans-impedance amplifier includes the electric current summing circuit of output stage cascade and classAB.
5. a kind of no coupled capacitor based on described in claim 1 has the realization of the instrument amplifier of DC maladjustment suppression function
Method, it is characterised in that：Differential input signal Vin1, Vin2 are converted into believing with Differential Input by the first transconductance circuit Gm1
Number proportional small-signal current；Two inputs of the second transconductance circuit Gm2 are respectively with imbalance suppression feedback circuit
Output and feedback resistive network are connected for monitoring signal offset voltage；By the input of trans-impedance amplifier respectively with first
Transconductance circuit Gm1, the output of the second transconductance circuit Gm2 are connected, and provide treated signal electricity as output stage for rear class
Pressure；The input of imbalance suppression feedback circuit is connected with the output of trans-impedance amplifier, for feeding back to any nearly direct current signal
Second transconductance circuit Gm2, so as to eliminate offset voltage, filters baseline drift, prevents amplifier output saturation；By charge pump circuit
Output be connected with the supply voltage of the first transconductance circuit Gm1, the second transconductance circuit Gm2, for lifting the first transconductance circuit
Gm1, the input common-mode range of the second transconductance circuit Gm2, so as to meet the demand of the full amplitude of oscillation input of circuit；By feedback resistive network
One end be connected with the output of trans-impedance amplifier, in order to monitor the output voltage of trans-impedance amplifier, this voltage is carried out partial pressure
After send into the second transconductance circuit Gm2 and be converted into electric current, the offset voltage of offset input signal.
6. a kind of no coupled capacitor according to claim 5 has the realization of the instrument amplifier of DC maladjustment suppression function
Method, it is characterised in that：Described imbalance suppression feedback circuit filter cutoff frequency be：
Wherein, A6For the resistance ratio value of feedback resistive network, R, C are respectively the resistance value that connect on imbalance suppression feedback circuit
And capacitance.
7. a kind of no coupled capacitor according to claim 5 has the realization of the instrument amplifier of DC maladjustment suppression function
Method, it is characterised in that：The first transconductance circuit Gm1 and the second transconductance circuit Gm2 be identical structure, be all by PMOS
Become the common-source amplifier with active damping resistance with equivalent resistance；Under the transconductance value of wherein the first transconductance circuit Gm1 is adopted
Formula is calculated：
Wherein, R is the resistance value in the first transconductance circuit Gm1.
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| Application Number | Priority Date | Filing Date | Title |
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| CN201611102327.5A CN106452381B (en) | 2016-12-05 | 2016-12-05 | Instrument amplifier with direct current offset suppression function and implementation method thereof |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201611102327.5A CN106452381B (en) | 2016-12-05 | 2016-12-05 | Instrument amplifier with direct current offset suppression function and implementation method thereof |
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| CN106452381B CN106452381B (en) | 2023-03-14 |
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN108494370A (en) * | 2018-05-31 | 2018-09-04 | 福州大学 | Chopper-stabilized instrumentation amplifier |
| CN110638443A (en) * | 2019-11-07 | 2020-01-03 | 福州大学 | Electrocardiosignal reading circuit |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101471632A (en) * | 2007-12-26 | 2009-07-01 | 中国科学院微电子研究所 | Self-bias low-voltage operation transconductance amplifier circuit with controllable loop gain |
| CN102412786A (en) * | 2011-12-20 | 2012-04-11 | 东南大学 | Transconductance-enhancing passive frequency mixer |
| CN203000929U (en) * | 2012-12-14 | 2013-06-19 | 江苏教育学院 | No-coupling capacitance electrocardiosignal pre-amplification electric circuit |
| US20130169361A1 (en) * | 2011-12-30 | 2013-07-04 | Dialog Semiconductor Gmbh | Multi-Stage Fully Differential Amplifier with Controlled Common Mode Voltage |
| CN103595356A (en) * | 2013-11-12 | 2014-02-19 | 四川和芯微电子股份有限公司 | High-frequency bandwidth amplifying circuit |
-
2016
- 2016-12-05 CN CN201611102327.5A patent/CN106452381B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101471632A (en) * | 2007-12-26 | 2009-07-01 | 中国科学院微电子研究所 | Self-bias low-voltage operation transconductance amplifier circuit with controllable loop gain |
| CN102412786A (en) * | 2011-12-20 | 2012-04-11 | 东南大学 | Transconductance-enhancing passive frequency mixer |
| US20130169361A1 (en) * | 2011-12-30 | 2013-07-04 | Dialog Semiconductor Gmbh | Multi-Stage Fully Differential Amplifier with Controlled Common Mode Voltage |
| CN203000929U (en) * | 2012-12-14 | 2013-06-19 | 江苏教育学院 | No-coupling capacitance electrocardiosignal pre-amplification electric circuit |
| CN103595356A (en) * | 2013-11-12 | 2014-02-19 | 四川和芯微电子股份有限公司 | High-frequency bandwidth amplifying circuit |
Non-Patent Citations (1)
| Title |
|---|
| 徐军: "《电流差分跨导放大器及其高阶滤波器设计研究》", 《中国优秀硕士论文全文数据库信息科技辑》 * |
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN108494370A (en) * | 2018-05-31 | 2018-09-04 | 福州大学 | Chopper-stabilized instrumentation amplifier |
| CN108494370B (en) * | 2018-05-31 | 2023-12-29 | 福州大学 | Chopper stabilized instrumentation amplifier |
| CN110638443A (en) * | 2019-11-07 | 2020-01-03 | 福州大学 | Electrocardiosignal reading circuit |
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| Publication number | Publication date |
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| CN106452381B (en) | 2023-03-14 |
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