CN106329924A - System for improving load transient response performance - Google Patents
System for improving load transient response performance Download PDFInfo
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- CN106329924A CN106329924A CN201610804047.2A CN201610804047A CN106329924A CN 106329924 A CN106329924 A CN 106329924A CN 201610804047 A CN201610804047 A CN 201610804047A CN 106329924 A CN106329924 A CN 106329924A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
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Abstract
The invention belongs to the field of DC-DC conversion, and particularly relates to a system for improving load transient response performance. The system comprises a PWM control unit, a compensation unit, a sampling unit and an adjustment unit, wherein the PWM control unit is connected with a power input end and generates control signals, and the control signals are used for changing current and voltage at the power output end; the compensation unit is coupled between the PWM control unit and the power output end, slope compensation is carried out according to the current and the voltage at the power output end and current and voltage at the power input end, and the PWM control unit generates control signals according to the compensated slope; the sampling unit is coupled between the compensation unit and the power output end and samples the current and the voltage at the power output end; and the adjustment unit is respectively connected with the PWM control unit, the compensation unit and the sampling unit, when the current or the voltage at the power output end changes, the sampling unit makes computation on the voltage at the power output end, a voltage change amount is obtained, the adjustment unit reduces the voltage change amount, and the PWM control unit generates control signals according to the reduced voltage change amount.
Description
Technical Field
The invention belongs to the field of direct current-direct current conversion, and particularly relates to a system for improving load transient response performance.
Background
At present, the topology structure of the BUCK DC/DC converter is generally classified into non-isolated BUCK, forward, half bridge, full bridge, and the like, and the topology structure of the BUCK DC/DC converter includes a Pulse Width Modulator (PWM) control loop, so that when the load current changes rapidly, due to the hysteresis effect of the output filter inductor and the control loop, the output voltage generates a large deviation amplitude and needs a long time to recover to an initial set value. In order to solve the problem, a plurality of filter capacitors are used in parallel in the conventional scheme, and although the method can effectively control the deviation amplitude of the output voltage, the reaction speed is slow, and the volume is increased and the cost is increased due to the use of a large number of filter capacitors.
Disclosure of Invention
Aiming at the problems in the prior art, the invention provides a system for improving the transient response performance of a load by a BUCK DC/DC converter, which can quickly respond to the change of load current, reduce the deviation amplitude of output voltage and simultaneously reduce the total required capacity of an external energy storage capacitor.
The invention adopts the following technical scheme:
a system for improving transient response performance of a load, for use in a current mode PWM controlled Buck dc-dc circuit, the system comprising:
a power input terminal and a power output terminal;
the PWM control unit is connected with the power supply input end, generates a control signal and changes the current and the voltage of the power supply output end by using the control signal;
the compensation unit is coupled between the PWM control unit and the power output end, performs slope compensation according to the current and the voltage of the power output end and the current and the voltage of the power input end, and generates the control signal according to the compensated slope;
the sampling unit is coupled between the compensation unit and the power output end and samples the voltage and the current of the power output end;
the adjusting unit is respectively connected with the PWM control unit, the compensating unit and the sampling unit;
when the current or the voltage of the power output end changes, the sampling unit operates the voltage of the power output end to obtain a voltage variation, the adjusting unit reduces the voltage variation, and the PWM control unit generates the control signal according to the reduced voltage variation.
Preferably, the PWM control unit includes:
the first transistor is coupled between the power supply input end and the compensation unit;
a second transistor coupled between the first transistor and a ground terminal;
the MOSFET driving circuit is respectively connected with the grids of the first transistor and the second transistor and controls the on and off of the first transistor and the second transistor according to the control signal;
and the positive end of the PWM generator is connected with the compensation unit, the reverse end of the PWM generator is connected with the adjusting unit, and the output end of the PWM generator is connected with the MOSFET driving circuit to generate the control signal.
Preferably, the MOSFET driving circuit comprises a flip-flop, and/or the PWM generator is a comparator.
Preferably, the compensation unit includes:
the filter inductor is connected with the PWM control unit;
the forward end of the first operational amplifier is connected with the filter inductor, the reverse end of the first operational amplifier is connected with the power supply output end, and the output end of the first operational amplifier is connected with the PWM control unit; and
and calculating compensation voltage of slope to be compensated according to the inductance current of the filter inductor, superposing the compensation voltage and the value output by the output end of the first operational amplifier through a voltage loop to obtain a synthesized signal, and generating the control signal by the PWM control unit according to the synthesized signal.
Preferably, the slope compensated by the compensation unit is greater than one half of the slope of the inductor current reduction.
Preferably, the sampling unit includes:
the first voltage-dividing resistor and the second voltage-dividing resistor are connected in series and then coupled between the power supply output end and a ground end;
the reverse end of the transconductance operational amplifier is respectively connected with the first voltage-dividing resistor and the second voltage-dividing resistor, and the forward end of the transconductance operational amplifier is connected with a reference voltage; and
and the transconductance operational amplifier samples the voltage division of the power output end through the first voltage division resistor and/or the second voltage division resistor, and operates by using the voltage division of the operational amplifier and the reference voltage to obtain the voltage variation.
Preferably, the adjusting unit includes:
the source electrode of the MOS tube is connected with a power supply, the grid electrode of the MOS tube is connected with the sampling unit, and the drain electrode of the MOS tube is connected with the PWM control unit through a third resistor;
the source electrode of the first PMOS tube is connected with the power supply, and the grid electrode of the first PMOS tube is connected with the drain electrode of the first PMOS tube;
a source electrode of the second PMOS tube is connected with the power supply, a grid electrode of the second PMOS tube is connected with a grid electrode of the first PMOS tube, and a drain electrode of the second PMOS tube is connected with the PWM control unit;
the source electrode of the NMOS tube is connected with the drain electrode of the first PMOS tube, and the drain electrode of the NMOS tube is connected with a grounding end through a fourth resistor;
the in-phase end of the second operational amplifier is connected with the compensation unit, the reverse end of the second operational amplifier is connected with the grounding end through the fourth resistor, and the output end of the second operational amplifier is connected with the grid electrode of the NMOS tube;
and a current source is connected with the source electrode of one transistor in the cascode current mirror, and the source electrode of the other transistor in the cascode current mirror is respectively connected with the third resistor, the PWM control unit and the drain electrode of the second PMOS tube.
Preferably, when the current at the power supply output end is Iout1Change to Iout2Then, the formula of the voltage variation △ VC is:
；
wherein VC2 represents that the current at the power output end is Iout2When the voltage of the grid electrode of the MOS tube is equal to VC1, the current of the power output end is equal to Iout1When the voltage of the grid electrode of the MOS tube is larger than the voltage of the grid electrode of the MOS tube, the current of the VCO2, which is the power output end, is Iout2When the voltage output by the regulating unit to the PWM control unit is larger than the voltage output by the PWM control unit, the current of the VCO1 at the power output end is Iout1When the voltage is output to the PWM control unit by the adjusting unit, K is a constant associated with the second operational amplifier and the compensating unit, and R3 is a resistance value of the third resistor.
The invention has the beneficial effects that:
the invention reduces the variable quantity of the load current by adding an adjusting unit, even has no influence to improve the transient response performance of the load in the PWM DC-DC conversion circuit.
Drawings
The invention and its features, aspects and advantages will become more apparent from reading the following detailed description of non-limiting embodiments with reference to the accompanying drawings. Like reference symbols in the various drawings indicate like elements. The drawings are not necessarily to scale, emphasis instead being placed upon illustrating the principles of the invention.
Fig. 1 is a topology diagram of a current mode PWM BUCK DC-DC conversion circuit according to a first embodiment of the invention;
FIGS. 2a-2c are schematic diagrams of the slope compensation of the present invention;
fig. 3 is a topology diagram of an improved PWM BUCK DC-DC conversion circuit according to a second embodiment of the present invention.
Detailed Description
In the following embodiments, the technical features may be combined with each other without conflict.
The invention provides a system for improving load transient response performance, wherein the following systems of the embodiments are exemplified by Buck-type DC-DC conversion circuits, and a PWM feedback control mode is usually adopted in the Buck-type DC-DC conversion circuit design to regulate output voltage or current. The PWM control method of this embodiment adopts current mode control, which may be dual-loop control of current inner loop and voltage outer loop, and the change of input voltage and load will be reflected on the filter inductor current first, and has faster response speed when the input voltage or load changes. The current mode control mode includes two modes of peak inductor current control and average inductor current control.
The peak inductor current control described in this embodiment is widely used because of its advantages, but it has an inherent open loop instability phenomenon, which raises the speed and also raises the stability problem. When the input voltage drops to a value close to the output voltage, the duty cycle is increased towards the maximum on-time, and further reduction of the input voltage will keep the main switch on for a period of time exceeding one cycle until the duty cycle reaches 100%, at which time sub-harmonic oscillation may occur in the circuit, and it is necessary to maintain the stability of the constant architecture by a slope compensation circuit, which is implemented by adding a compensation slope to the inductor current signal in case of a large duty cycle.
The invention will be further described with reference to the following drawings and specific examples, which are not intended to limit the invention thereto.
Example one
The system for improving the transient response performance of the load according to the present embodiment may include a power input terminal IN, a power output terminal OUT, a PWM control unit, a compensation unit, and a sampling unit, and is exemplified by a current-type PWM BUCK direct current-direct current (DC-DC) conversion circuit.
As shown in fig. 1, the PWM control unit includes a circuit that usually internally integrates a PWM generator (shown as PWM in fig. 1), a MOSFET Driver circuit (Driver circuit), and other auxiliary functions such as a reference voltage source, soft start, etc.; the first transistor Q1 and the second transistor Q2 are a control switch transistor and a freewheel switch transistor, typically MOSFETs, respectively, and the first transistor Q1 and the second transistor Q2 are turned on and off according to a driving signal of the MOSFET driving circuit.
The compensation unit includes: the inductor L is an output filter inductor and can be equivalent to an ideal inductor which is connected with an equivalent direct current resistor in series; a slope compensation loop (not shown) for performing slope compensation by using the inductor current IL and the inductor voltage; the first operational amplifier OPAMP1, two input ends of the first operational amplifier OPAMP1 are connected in parallel to the first resistor Rs, the inductance voltage and the output end voltage are used as input values of the two input ends of the first operational amplifier OPAMP1, the first operational amplifier OPAMP1 obtains an output value Vsense through amplification operation, and the output value Vsense of the first operational amplifier OPAMP1 and a slope compensation voltage Vslope of the compensation slope Mc are used as two inputs of the voltage loop to be superposed to obtain an input value Vsum of the positive input end of the PWM generator.
The sampling unit comprises a first voltage-dividing resistor R1 and a second voltage-dividing resistor R2, wherein the first voltage-dividing resistor R1 is generally called as an upper voltage-dividing resistor, and the second voltage-dividing resistor R2 is a lower voltage-dividing resistor; the transconductance operational amplifier OTA is characterized in that a divided voltage FB of a sampling divided voltage resistor at the reverse end of the transconductance operational amplifier OTA is used as an input value of the reverse input end of the transconductance operational amplifier OTA, a reference voltage VREF is input at the forward end of the transconductance operational amplifier OTA, the transconductance operational amplifier OTA compares the reference voltage VREF with the sampled divided voltage FB, the output end of the transconductance operational amplifier OTA is connected with the reverse end of the PWM generator, and the output value of the transconductance operational amplifier OTA is used as a reference voltage of the PWM generator.
Based on the structure of each subunit in the system, the following describes the connection relationship and the operation principle between devices in each subunit:
in the PWM control unit, a first transistor Q1 is coupled between the power input terminal and the filter inductor L, a gate of a Q1 of the first transistor is connected to the MOSFET driving circuit, a second transistor Q2 is coupled between a node formed by the filter inductor L and the first transistor Q1 and the ground terminal, and a gate of the second transistor Q2 is also connected to the MOSFET driving circuit, the MOSFET driving circuit generates a driving signal to control the on and off of the first transistor Q1 and the second transistor Q2, that is, the MOSFET driving circuit adjusts the duty ratio of the output current I1 and the second transistor Q2 of the power output terminal OUT by changing the duty ratio of the first transistor Q1 and the second transistor Q2OUTAnd an output voltage VOUT。
In this embodiment, the PWM generator may be a comparator, an output terminal of the PWM generator is connected to the MOSFET driving circuit, and the driving signal generated by the MOSFET driving circuit is generated according to a value output by the output terminal of the PWM generator.
A filter inductor coupled between the first resistor Rs and the first transistor Q1, a forward terminal of a first operational amplifier OPAMP1 coupled to the filter inductor, and a first operational amplifier OPAMP1 coupled to the filter inductor
The inverting terminal of the first operational amplifier OPAMP1 compares the filter inductance voltage with the power output terminal voltage Vout and then performs amplification operation to obtain an output voltage value Vsense of the first operational amplifier OPAMP1, obtains a compensation slope Mc according to the slopes M1 and M2 of the inductance current IL and the inductance voltage, calculates a slope compensation voltage value Vslope corresponding to the compensation slope Mc, and superimposes the Vsense and the Vslope as two input values of the voltage loop to obtain an input value Vsum of the forward input terminal of the PWM generator.
The output end of the transconductance operational amplifier OTA is connected with the inverting input end of the PWM generator, and the output end of the transconductance operational amplifier OTA is further grounded through a second resistor Rc and a capacitor Cc. The transconductance operational amplifier OTA compares the divided voltage Vout of the power output terminal with a reference voltage VREF to obtain a value Vc, which is used as the input of the PWM generator inverting terminal for the subsequent control of the MOSFET driving circuit.
The term "slope compensation" as used herein refers to the addition of a portion of the sawtooth voltage to the control signal in a current controlled manner to improve the control characteristics, including the elimination of harmonic oscillations. The switching power supply is widely applied by the advantages of high efficiency, small volume and the like, the current type PWM has better voltage regulation rate and load regulation rate, and the stability and the dynamic characteristic of the system are also obviously improved. The current mode BUCK DC-DC converter can generate harmonic oscillation when working under the condition that the duty ratio is larger than 50% and the continuous inductive current is continuous, and the basic compensation principle is analyzed as follows: the reasons for the generation of harmonic oscillations are: as shown in fig. 2a-2 b, at time t0, the first transistor Q1 and the second transistor Q2 turn on, causing the inductor current to rise with a slope m1, which is a function of the output voltage Vc1 at the output of the input transconductance operational amplifier and the current Iout1 at the output of the power supply. At time t1, when the inductor current IL sampled input reaches the threshold established by the control voltage, the first transistor Q1 and the second transistor Q2 turn off, at which time the current decreases with a slope m2 that is a function of the output voltage Vc2 at the output of the transconductance operational amplifier and the current Iout2 at the output of the power supply, until the start of the next oscillation cycle.
Because the current inner loop control is added, after the inductive current is sampled, the synthesized signal Vsum and the output Vc of the transconductance operational amplifier OTA are sent to the PWM generator for comparison, the voltage of the transconductance operational amplifier OTA enters the PWM generator to participate in the duty ratio regulation, and the stability of the output end Vout of the output power supply is effectively ensured through MOSFET driving units such as an RS trigger. The duty ratio D = Vout/Vin, and Vin is the voltage of the power supply input end. Peak inductor current regulation systems have inherent limitations, for example, one output control voltage of an oscillator may correspond to a change in duty cycle.
After N cycles, if the slope m2 is less than m1, namely the duty ratio is less than 50%, the disturbance of the peak inductive current is converged, and if m2 is greater than m1, namely the duty ratio is greater than 50%, the disturbance of the peak inductive current is dispersed, and after the disturbance is amplified in each cycle, the system is extremely unstable, so that the anti-interference performance of the system power supply without slope compensation is extremely poor. After adding the inductor current I L after compensating the current, as shown in fig. 2c, when mc > 0.5 m2, i.e. the slope of the ramp compensation must be greater than one-half of the falling slope of the inductor current, the slope compensation can make the inductor current converge significantly, which can stabilize the system well, otherwise, the sub-harmonic oscillation will occur when the duty ratio of the system is greater than 50%.
Example two
Based on the first embodiment, the system of the present embodiment adds an adjusting unit, and the adjusting unit can reduce the variation of the output voltage Vc of the transconductance operational amplifier OTA, greatly improve the load transient response performance of the current mode PWM DC-DC conversion circuit, completely avoid the problem of reducing subharmonic oscillation caused by ramp compensation, and make the circuit implementation simpler.
As shown in FIG. 2a, the larger the load current Iout, the larger the value of the output voltage VC of the OTA, when the load current is IOUT1Change to IOUT2From time to time, the variation of the output voltage VC of the corresponding transconductance operational amplifier OTA is △ VC., and it is obvious that when the load current Iout varies, the smaller the value of the corresponding variation △ VC is, the better the load transient response performance of the DC-DC conversion circuit is.
As shown in fig. 3, the adjusting unit of this embodiment is connected between the output terminal of the transconductance operational amplifier OTA and the PWM generator, that is, the output terminal of the transconductance operational amplifier OTA and the PWM generator of the embodiment are disconnected, and an adjusting unit is introduced to connect between the output terminal of the transconductance operational amplifier OTA and the PWM generator.
In the embodiment, a variable positively correlated to the load current is introduced, and the variable is operated with the output of the transconductance operational amplifier OTA, so that the variation quantity delta VC of VC is greatly reduced when the load current is changed, and the load transient response performance of the system is greatly improved.
The above-mentioned regulating unit includes: the power supply circuit comprises a first PMOS tube PM1 and a second PMOS tube PM2, wherein the source electrode of the first PMOS tube PM1 is connected with a power supply VDD, the grid electrode of the first PMOS tube PM1 is connected with the drain electrode of the first PMOS tube PM1, the source electrode of the second PMOS tube PM2 is connected with the power supply VDD, the grid electrode of the second PMOS tube PM2 is connected with the grid electrode of the first PMOS tube PM1, and the drain electrode of the second PMOS tube PM2 is connected with the reverse end of the PWM generator.
The adjusting unit further includes: a second operational amplifier OPAMP2, the non-inverting terminal of the second operational amplifier OPAMP2 being connected to the output terminal of the first operational amplifier; the regulating unit further comprises an NMOS transistor N1, a source electrode of the NMOS transistor N1 is connected to the drain electrode of the first PMOS transistor PM1, a gate electrode of the NMOS transistor is connected to the output end of the second operational amplifier OPAMP2, a source electrode of the NMOS transistor is connected to the unidirectional section of the second operational amplifier OPAMP2, and a drain electrode of the NMOS transistor is further grounded through a fourth resistor R4.
The regulating unit further comprises an MOS tube, the grid electrode of the MOS tube is connected with the output end of the transconductance operational amplifier OTA, the source electrode of the MOS tube is connected with a power supply VDD, and the drain electrode of the MOS tube is connected with the reverse end of the PWM generator through a third resistor R3.
The adjusting unit further comprises a cascode current mirror, a current source Ib is connected to the drain electrode of the cascode current mirror transistor, and an output transistor of the cascode current mirror is connected with the third resistor.
The working principle of the adjusting unit is as follows:
because of the fact thatWherein Is the drain current of the second PMOS transistor, and K Is an amplification factor determined by the first operational amplifier OPAMP1 and the second operational amplifier OMAMP 2.
By means ofWhereinthe voltage between the gate and the source of the MOS transistor M1 can be derived by the above two equations:
；
when the load current is from IOUT1Becomes larger to IOUT2When the temperature of the water is higher than the set temperature,
(ii) a Wherein,as the values before and after the change in Vc,before and after the change in Vco.
Similarly, when the load current is from IOUT1Is reduced to IOUT2The method comprises the following steps:
；
it can be seen from the above formula that the value of △ VC becomes smaller when the load current Iout changes, and the appropriate R is selected3And k value, the value of △ VC can be connectedClose to 0, the method can greatly improve the transient response of the load and completely neglect the influence of the ramp compensation. Thus, when the load changes, the VC value has little fluctuation, and the performance of the load transient response of the system is greatly improved.
In summary, the present invention reduces the variation of the load current by adding an adjusting unit, and even improves the load transient response performance in the PWM DC-DC conversion circuit without any influence.
The above description is of the preferred embodiment of the invention. It is to be understood that the invention is not limited to the particular embodiments described above, in that devices and structures not described in detail are understood to be implemented in a manner common in the art; those skilled in the art can make many possible variations and modifications to the disclosed embodiments, or modify equivalent embodiments to equivalent variations, without departing from the spirit of the invention, using the methods and techniques disclosed above. Therefore, any simple modification, equivalent change and modification made to the above embodiments according to the technical essence of the present invention are still within the scope of the protection of the technical solution of the present invention, unless the contents of the technical solution of the present invention are departed.
Claims (8)
1. A system for improving transient response performance of a load, the system being used in a current mode PWM controlled Buck dc-dc circuit, the system comprising:
a power input terminal and a power output terminal;
the PWM control unit is connected with the power supply input end, generates a control signal and changes the current and the voltage of the power supply output end by using the control signal;
the compensation unit is coupled between the PWM control unit and the power output end, performs slope compensation according to the current and the voltage of the power output end and the current and the voltage of the power input end, and generates the control signal according to the compensated slope;
the sampling unit is coupled between the compensation unit and the power output end and samples the voltage and the current of the power output end;
the adjusting unit is respectively connected with the PWM control unit, the compensating unit and the sampling unit;
when the current or the voltage of the power output end changes, the sampling unit operates the voltage of the power output end to obtain a voltage variation, the adjusting unit reduces the voltage variation, and the PWM control unit generates the control signal according to the reduced voltage variation.
2. The system for improving load transient response performance of claim 1, wherein said PWM control unit comprises:
the first transistor is coupled between the power supply input end and the compensation unit;
a second transistor coupled between the first transistor and a ground terminal;
the MOSFET driving circuit is respectively connected with the grids of the first transistor and the second transistor and controls the on and off of the first transistor and the second transistor according to the control signal;
and the positive end of the PWM generator is connected with the compensation unit, the reverse end of the PWM generator is connected with the adjusting unit, and the output end of the PWM generator is connected with the MOSFET driving circuit to generate the control signal.
3. The system of claim 2, wherein the MOSFET driver circuit comprises a flip-flop and/or the PWM generator is a comparator.
4. The system for improving load transient response performance of claim 1, wherein said compensation unit comprises:
the filter inductor is connected with the PWM control unit;
the forward end of the first operational amplifier is connected with the filter inductor, the reverse end of the first operational amplifier is connected with the power supply output end, and the output end of the first operational amplifier is connected with the PWM control unit; and
and calculating compensation voltage of slope to be compensated according to the inductance current of the filter inductor, superposing the compensation voltage and the value output by the output end of the first operational amplifier through a voltage loop to obtain a synthesized signal, and generating the control signal by the PWM control unit according to the synthesized signal.
5. The system for improving the transient response performance of a load according to claim 4, wherein the slope of the compensation unit is greater than one-half of the slope of the decrease of the inductor current.
6. The system for improving load transient response performance of claim 1, wherein said sampling unit comprises:
the first voltage-dividing resistor and the second voltage-dividing resistor are connected in series and then coupled between the power supply output end and a ground end;
the reverse end of the transconductance operational amplifier is respectively connected with the first voltage-dividing resistor and the second voltage-dividing resistor, and the forward end of the transconductance operational amplifier is connected with a reference voltage; and
and the transconductance operational amplifier samples the voltage division of the power output end through the first voltage division resistor and/or the second voltage division resistor, and operates by using the voltage division of the operational amplifier and the reference voltage to obtain the voltage variation.
7. The system for improving load transient response performance of claim 1, wherein said regulating unit comprises:
the source electrode of the MOS tube is connected with a power supply, the grid electrode of the MOS tube is connected with the sampling unit, and the drain electrode of the MOS tube is connected with the PWM control unit through a third resistor;
the source electrode of the first PMOS tube is connected with the power supply, and the grid electrode of the first PMOS tube is connected with the drain electrode of the first PMOS tube;
a source electrode of the second PMOS tube is connected with the power supply, a grid electrode of the second PMOS tube is connected with a grid electrode of the first PMOS tube, and a drain electrode of the second PMOS tube is connected with the PWM control unit;
the source electrode of the NMOS tube is connected with the drain electrode of the first PMOS tube, and the drain electrode of the NMOS tube is connected with a grounding end through a fourth resistor;
the in-phase end of the second operational amplifier is connected with the compensation unit, the reverse end of the second operational amplifier is connected with the grounding end through the fourth resistor, and the output end of the second operational amplifier is connected with the grid electrode of the NMOS tube;
and a current source is connected with the source electrode of one transistor in the cascode current mirror, and the source electrode of the other transistor in the cascode current mirror is respectively connected with the third resistor, the PWM control unit and the drain electrode of the second PMOS tube.
8. The system of claim 7, wherein the current at the output of the power supply is controlled by Iout1Change to Iout2Then, the formula of the voltage variation △ VC is:
；
wherein VC2 is the power of the power supply output terminalThe flow is Iout2When the voltage of the grid electrode of the MOS tube is equal to VC1, the current of the power output end is equal to Iout1When the voltage of the grid electrode of the MOS tube is larger than the voltage of the grid electrode of the MOS tube, the current of the VCO2, which is the power output end, is Iout2When the voltage output by the regulating unit to the PWM control unit is larger than the voltage output by the PWM control unit, the current of the VCO1 at the power output end is Iout1When the voltage is output to the PWM control unit by the adjusting unit, K is a constant associated with the second operational amplifier and the compensating unit, and R3 is a resistance value of the third resistor.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN2016103733060 | 2016-05-30 | ||
| CN201610373306 | 2016-05-30 |
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| CN107659151A (en) * | 2017-04-24 | 2018-02-02 | 深圳市华芯邦科技有限公司 | Buck load current detection circuits and method without external sampling resistance |
| CN109639119A (en) * | 2018-08-29 | 2019-04-16 | 厦门元顺微电子技术有限公司 | Driving circuit applied to DC-DC converter |
| CN110391735A (en) * | 2018-04-16 | 2019-10-29 | 恩智浦有限公司 | PWM mode step-up switching regulator with programmable pulse frequency-hopping mode |
| CN111446865A (en) * | 2020-05-08 | 2020-07-24 | 深圳威迈斯新能源股份有限公司 | Slope compensation control circuit and slope compensation control method |
| CN111628646A (en) * | 2019-02-28 | 2020-09-04 | 通嘉科技股份有限公司 | Power supply controller and related control method |
| CN112965003A (en) * | 2021-02-01 | 2021-06-15 | 佛山市博顿光电科技有限公司 | Power supply aging load circuit |
| WO2021115146A1 (en) * | 2019-12-13 | 2021-06-17 | 北京集创北方科技股份有限公司 | Voltage regulation apparatus, chip and electronic device |
| WO2021238572A1 (en) * | 2020-05-29 | 2021-12-02 | 北京集创北方科技股份有限公司 | Voltage adjustment apparatus, chip, power source, and electronic device |
| CN115113674A (en) * | 2022-06-15 | 2022-09-27 | 陕西半导体先导技术中心有限公司 | Controllable magnetic field generating device |
| CN116131571A (en) * | 2022-12-01 | 2023-05-16 | 芯合电子(上海)有限公司 | Method and system for accelerating DC-DC conversion voltage regulation speed |
| WO2024055408A1 (en) * | 2022-09-13 | 2024-03-21 | 深圳英集芯科技股份有限公司 | Dc-dc converter, switch power supply, and electronic device |
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| CN107659151B (en) * | 2017-04-24 | 2023-07-07 | 深圳市华芯邦科技有限公司 | Buck load current detection circuit and method without external sampling resistor |
| CN107659151A (en) * | 2017-04-24 | 2018-02-02 | 深圳市华芯邦科技有限公司 | Buck load current detection circuits and method without external sampling resistance |
| CN110391735A (en) * | 2018-04-16 | 2019-10-29 | 恩智浦有限公司 | PWM mode step-up switching regulator with programmable pulse frequency-hopping mode |
| CN110391735B (en) * | 2018-04-16 | 2023-10-17 | 恩智浦有限公司 | PWM mode boost switching regulator with programmable pulse hopping mode |
| CN109639119A (en) * | 2018-08-29 | 2019-04-16 | 厦门元顺微电子技术有限公司 | Driving circuit applied to DC-DC converter |
| CN111628646A (en) * | 2019-02-28 | 2020-09-04 | 通嘉科技股份有限公司 | Power supply controller and related control method |
| CN111628646B (en) * | 2019-02-28 | 2021-07-20 | 通嘉科技股份有限公司 | Power supply controller and related control method |
| WO2021115146A1 (en) * | 2019-12-13 | 2021-06-17 | 北京集创北方科技股份有限公司 | Voltage regulation apparatus, chip and electronic device |
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| CN111446865B (en) * | 2020-05-08 | 2021-06-25 | 深圳威迈斯新能源股份有限公司 | Slope compensation control circuit and slope compensation control method |
| CN111446865A (en) * | 2020-05-08 | 2020-07-24 | 深圳威迈斯新能源股份有限公司 | Slope compensation control circuit and slope compensation control method |
| WO2021238572A1 (en) * | 2020-05-29 | 2021-12-02 | 北京集创北方科技股份有限公司 | Voltage adjustment apparatus, chip, power source, and electronic device |
| CN112965003A (en) * | 2021-02-01 | 2021-06-15 | 佛山市博顿光电科技有限公司 | Power supply aging load circuit |
| CN112965003B (en) * | 2021-02-01 | 2024-04-30 | 佛山市博顿光电科技有限公司 | Power supply aging load circuit |
| CN115113674A (en) * | 2022-06-15 | 2022-09-27 | 陕西半导体先导技术中心有限公司 | Controllable magnetic field generating device |
| WO2024055408A1 (en) * | 2022-09-13 | 2024-03-21 | 深圳英集芯科技股份有限公司 | Dc-dc converter, switch power supply, and electronic device |
| CN116131571A (en) * | 2022-12-01 | 2023-05-16 | 芯合电子(上海)有限公司 | Method and system for accelerating DC-DC conversion voltage regulation speed |
| CN116131571B (en) * | 2022-12-01 | 2024-08-23 | 芯合电子(上海)有限公司 | Method and system for accelerating DC-DC conversion voltage regulation speed |
| CN118100599A (en) * | 2024-04-25 | 2024-05-28 | 深圳市微源半导体股份有限公司 | Transient detection circuit, voltage converter and power supply device |
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