CN105553249A - Current injection type three-phase power factor correction circuit having wide voltage range and low voltage stress - Google Patents
Current injection type three-phase power factor correction circuit having wide voltage range and low voltage stress Download PDFInfo
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- CN105553249A CN105553249A CN201610001646.0A CN201610001646A CN105553249A CN 105553249 A CN105553249 A CN 105553249A CN 201610001646 A CN201610001646 A CN 201610001646A CN 105553249 A CN105553249 A CN 105553249A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4233—Arrangements for improving power factor of AC input using a bridge converter comprising active switches
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention relates to a current injection type three-phase power factor correction circuit having a wide voltage range and low voltage stress. According to an input voltage working range, the circuit can work in a boost mode and also can work in a buck mode; the voltage stress of a switch tube is less than the voltage stress due to direct adoption of typical boost-buck topology (buck-boost, cuk, sepic, zeta); and the circuit has the relatively high conversion efficiency. A convertor in the invention separatelycontrols phase voltage corresponding to current tracking of the maximal phase and the minimal phase of an input voltage instantaneous value; according to three-phase symmetry, another one-phase current also follows the phase voltage thereof, such that sine control of the three-phase current is realized; by means of the staged working modes, the output voltage can be increased and decreased; the working range of input and output voltage is wide; therefore, the circuit is applied to an application occasion having a wide input and output voltage change range; complex vector control is unnecessary in the invention; sine of the three-phase input current can be realized only by adopting a DC/DC PWM control technology; and the circuit is easy to realize.
Description
Technical field
The present invention relates to a kind of wide-voltage range low voltage stress current-injecting three-phase power factor correcting circuit.
Background technology
The stable operation that the harmonic current of net side input can cause that power-supply system utilance is low, loss is large, normal work that is that affect power consumption equipment even jeopardizes whole electrical network, harmonic wave control more and more obtains the attention of academia and national governments, has put into effect the harmonic content that many harmonic limit standards carry out specification power consumption equipment.As standards such as IEC61000-3-2, GB17625.1, the Harmonic Current Limits of clear stipulaties electronic equipment, only has the electronic equipment meeting code requirement just to allow listing.
More than 5 kilowatts power power consumption equipments adopt the large power-consuming equipment of three phase supply usually, the harmonic pollution produced is large, and PFC technology does not but obtain general application, and the development mainly coming from three-phase PFC technology is not mature enough, in practical application, system configuration and control complexity, realize difficulty.Modal three-phase pfc circuit structure is PWM rectifier, can be divided into two large classes: voltage type PWM rectifier and current-type PWM converter.The former is boost type arrangement, and output dc voltage need be greater than the peak value of three-phase input line voltage, and device voltage stress is large.For domestic Ull=380V(Europe 400V) commercial power, output dc voltage generally reaches 700 ~ 800V; 480V(or 600V of north America region) power powers, and output voltage is higher.Current-type PWM converter is voltage-dropping type structure, output voltage
.The VIENNA rectifier occurred in recent years is boost configuration, SWISS rectifier is buck configuration, most three-phase pfc circuits known are at present single boosting or buck configuration, and the three-phase pfc circuit device voltage stress that part has stepping functions is excessive, control complicated, practical application difficulty.At output voltage not in above-mentioned scope, or the application scenario that input and output voltage excursion is large, single boosting or the circuit of buck functionality cannot meet the demands.
Summary of the invention
In view of this, the object of the present invention is to provide a kind of wide-voltage range low voltage stress current-injecting three-phase power factor correcting circuit, solve liter that output voltage can only be single or fall the problem excessive with available circuit device voltage stress.
For achieving the above object, the present invention adopts following technical scheme: a kind of wide-voltage range low voltage stress current-injecting three-phase power factor correcting circuit, is characterized in that: comprise three-phase alternating current input power Uin, three-phase commutation bridge DB1, power MOSFET tube S1, power MOSFET tube S2, power MOSFET tube S3, power MOSFET tube S4, diode D1, diode D2, diode D3, harmonic current injection network, inductance L 1, inductance L 2, output filter capacitor Cf and load; Described harmonic current injection network comprises bidirectional switch Sy1, bidirectional switch Sy2 and bidirectional switch Sy3; Three of described three-phase alternating current input power Uin input phase voltages are connected with three inputs of three-phase commutation bridge DB1 respectively, and three of described three-phase alternating current input power Uin input phase voltages and are also connected with one end of bidirectional switch Sy1, one end of bidirectional switch Sy2, one end of bidirectional switch Sy3 respectively; The other end of the other end of described bidirectional switch Sy1, the other end of bidirectional switch Sy2 and bidirectional switch Sy3 is connected in decanting point Y; The positive output end of described three-phase commutation bridge DB1 is connected with the drain electrode of power MOSFET tube S1, and the negative output terminal of described three-phase commutation bridge DB1 is connected with the source electrode of power MOSFET tube S2; The source electrode of power MOSFET tube S1 is connected with one end of the negative electrode of diode D1 and inductance L 1, and the drain electrode of power MOSFET tube S2 is connected with one end of the anode of diode D2 and inductance L 2; The other end of inductance L 1 is connected with the anode of the drain electrode of power MOSFET tube S3 and diode D3, the other end of inductance L 2 is connected with the negative pole of the source electrode of power MOSFET tube S4, output filter capacitor Cf and one end of load RL, and the negative electrode of diode D3 is connected with the other end of the positive pole of output filter capacitor Cf and load RL; The source electrode of the anode of diode D1, the negative electrode of diode D2, power MOSFET tube S3 and the drain electrode of power MOSFET tube S4 are connected and described decanting point Y.
Further, described power MOSFET tube S1 and power MOSFET tube S2 or be IGBT power switch pipe.
Further, described power MOSFET tube S3 and power MOSFET tube S4 or recover the IGBT power switch pipe of power diode soon for inverse parallel.
Further, described diode D1, diode D2, diode D3 recover power diode soon.
Further, described bidirectional switch Sy1, bidirectional switch Sy2 and bidirectional switch Sy3 are formed by two power MOSFET tubes or two IGBT pipe differential concatenations.
Further, the mode of operation of described inductance L 1 and inductance L 2 is continuous current mode CCM, discontinuous current mode DCM or critical current mode BCM.
Further, described output filter capacitor Cf is energy storage electrochemical capacitor.
The present invention compared with prior art has following beneficial effect:
1, the present invention passes through different circuit working stage by stage, and output voltage can rise and can fall, and input and output voltage working range is large, is more suitable for the application scenario that input and output voltage excursion is large;
2, switch tube voltage stress of the present invention is little, and any stage, only have two switching tubes to be operated in high frequency state, switching loss is less, is conducive to improved efficiency;
3, the present invention is without the need to the vector control of complexity, as long as adopt DC/DCPWM control technology, just can realize three-phase input current positizing string, is easy to realize.
Accompanying drawing explanation
Fig. 1 is specific embodiment of the invention circuit diagram.
Fig. 2 is the drive singal of three bidirectional switchs of the present invention and the sequential chart of three-phase input power.
Fig. 3 is the voltage and current waveform of the present invention when steady operation.
Fig. 4 be the present invention in interval 1., equivalent circuit diagram during boost mode of operation.
Fig. 5 is the simplified electrical circuit diagram of Fig. 4.
Fig. 6 a be the present invention in interval 1., the current path figure in stage 1 during boost mode of operation.
Fig. 6 b be the present invention in interval 1., the current path figure in stage 2 during boost mode of operation.
Fig. 6 c be the present invention in interval 1., the current path figure in stage 3 during boost mode of operation.
Fig. 6 d be the present invention in interval 1., the current path figure in stage 4 during boost mode of operation.
Fig. 7 be the present invention in interval 1., equivalent circuit diagram during buck mode of operation.
Fig. 8 is the simplified electrical circuit diagram of Fig. 7.
Fig. 9 a be the present invention in interval 1., the current path figure in stage 1 during buck mode of operation.
Fig. 9 b be the present invention in interval 1., the current path figure in stage 2 during buck mode of operation.
Fig. 9 c be the present invention in interval 1., the current path figure in stage 3 during buck mode of operation.
Fig. 9 d be the present invention in interval 1., the current path figure in stage 4 during buck mode of operation.
Embodiment
Below in conjunction with drawings and Examples, the present invention will be further described.
Please refer to Fig. 1, the invention provides a kind of wide-voltage range low voltage stress current-injecting three-phase power factor correcting circuit, it is characterized in that: comprise three-phase alternating current input power Uin, three-phase commutation bridge DB1, power MOSFET tube S1, power MOSFET tube S2, power MOSFET tube S3, power MOSFET tube S4, diode D1, diode D2, diode D3, harmonic current injection network, inductance L 1, inductance L 2, output filter capacitor Cf and load; Described harmonic current injection network comprises bidirectional switch Sy1, bidirectional switch Sy2 and bidirectional switch Sy3; Three of described three-phase alternating current input power Uin input phase voltages are connected with three inputs of three-phase commutation bridge DB1 respectively, and three of described three-phase alternating current input power Uin input phase voltages and are also connected with one end of bidirectional switch Sy1, one end of bidirectional switch Sy2, one end of bidirectional switch Sy3 respectively; The other end of the other end of described bidirectional switch Sy1, the other end of bidirectional switch Sy2 and bidirectional switch Sy3 is connected in decanting point Y; The positive output end of described three-phase commutation bridge DB1 is connected with the drain electrode of power MOSFET tube S1, and the negative output terminal of described three-phase commutation bridge DB1 is connected with the source electrode of power MOSFET tube S2; The source electrode of power MOSFET tube S1 is connected with one end of the negative electrode of diode D1 and inductance L 1, and the drain electrode of power MOSFET tube S2 is connected with one end of the anode of diode D2 and inductance L 2; The other end of inductance L 1 is connected with the anode of the drain electrode of power MOSFET tube S3 and diode D3, the other end of inductance L 2 is connected with the negative pole of the source electrode of power MOSFET tube S4, output filter capacitor Cf and one end of load RL, and the negative electrode of diode D3 is connected with the other end of the positive pole of output filter capacitor Cf and load RL; The source electrode of the anode of diode D1, the negative electrode of diode D2, power MOSFET tube S3 and the drain electrode of power MOSFET tube S4 are connected and described decanting point Y.
Power MOSFET tube S1, power MOSFET tube S2, diode D1, diode D2 in Fig. 1, inductance L 1, inductance L 2, output filter capacitor Cf form two buck circuit; Power MOSFET tube S3, power MOSFET tube S4, diode D3, inductance L 1, inductance L 2, output filter capacitor Cf form two boost circuit.
In the present embodiment, described power MOSFET tube S1 and power MOSFET tube S2 or be IGBT power switch pipe.
In the present embodiment, described power MOSFET tube S3 and power MOSFET tube S4 or recover the IGBT power switch pipe of power diode soon for inverse parallel.
In the present embodiment, described diode D1, diode D2, diode D3 recover power diode soon.
In the present embodiment, described bidirectional switch Sy1, bidirectional switch Sy2 and bidirectional switch Sy3 are formed by two power MOSFET tubes or two IGBT pipe differential concatenations.
In the present embodiment, the mode of operation of described inductance L 1 and inductance L 2 is continuous current mode CCM, discontinuous current mode DCM or critical current mode BCM.
In the present embodiment, described output filter capacitor Cf is energy storage electrochemical capacitor.
The drive singal of the switching tube of harmonic current injection network of the present invention and the sequential chart of three-phase input power as shown in Figure 2.The control signal of three bidirectional switchs Sy1, Sy2, Sy3 and the relation of three-phase input voltage instantaneous value, the bidirectional switch of injection branch works in twice supply frequency, belongs to low frequency operation power switch pipe.An AC mains cycle is divided into 6 intervals, and each interval is 60 °, in each interval, and that corresponding bidirectional switch conducting that three-phase input voltage absolute value is minimum.Voltage current waveform when Fig. 3 is steady operation, u
pY, u
ynfor the piecewise combination of line voltage, be similar to triangular wave.For interval 1. analysis below, analyzes the detailed operation of boost pattern and buck pattern respectively.This interval c phase voltage absolute value is minimum, bidirectional switch Sy3 conducting, and Sy1, Sy2 turn off.Positive maximum of a phase voltage, u
pN=u
aN, it is minimum that b phase voltage is born, u
nN=u
bN.It can thus be appreciated that u
pn=u
ab, u
pY=u
ac, u
yn=u
cb, u
pn=u
ab.
One: boost pattern
As three phase rectifier output voltage u
pn<U
otime, circuit working is in boost pattern.With reference to accompanying drawing 4, now power MOSFET tube S1, S2 keeps conducting, and power MOSFET tube S3, S4 HF switch works, and as shown in Figure 5, arrow represents the reference positive direction of each state variable to simple equivalent circuit.S3, S4 control signal adopts trailing edge modulation, and namely each switch periods initial time, simultaneously open-minded.
(1) S3, S4 conducting simultaneously, equivalent electric circuit is as Fig. 6 a.Voltage u
pY=u
ac, be added on L1; Voltage u
yn=u
cb, be added on L2; i
l1, i
l2increase.D3 is reverse-biased, and load RL is all by electric capacity C
fpower supply.
(2) S3 conducting, S4 turn off, and equivalent electric circuit is as Fig. 6 b.S3 conducting, i
l1increase; i
l2i is worked as by S3(
l2>i
l1time, by S3 parasitic diode), D3 continuous current discharge electricity, at back-pressure (U
o-u
yn) the lower reduction of effect.
(3) S3 shutoff, S4 conducting, equivalent electric circuit is as Fig. 6 c.S4 conducting, i
l2increase; i
l1i is worked as by S4(
l1>i
l2time, by S4 parasitic diode), D3 continuous current discharge electricity, at back-pressure (U
o-u
pY) the lower reduction of effect.
(4) S3, S4 turn off simultaneously, and equivalent electric circuit is as Fig. 6 d.Three kinds of situations are divided in actual conducting loop, and a) S3, S4 turn off the moment simultaneously, i
l1>i
l2, then i
y<0, S4 parasitic diode Ds4 conducting, i
l2at u
yncontinue under effect to increase, i
l1at back-pressure (U
o-u
pY) the lower reduction of effect.If i before next switch periods arrives
l1=i
l2, then S3, S4 parasitic diode is all obstructed, i
y=0, i
l1, i
l2afterflow reduces together.B) S3, S4 turn off the moment simultaneously, i
l1<i
l2, then i
y>0, S3 parasitic diode Ds3 conducting, i
l1at u
pYcontinue under effect to increase, i
l2at back-pressure (U
o-u
yn) the lower reduction of effect.If i before next switch periods arrives
l1=i
l2, then S3, S4 parasitic diode is all obstructed, i
y=0, i
l1, i
l2afterflow reduces together.C) S3, S4 turn off the moment simultaneously, i
l1=i
l2, then S3, S4 parasitic diode is directly proceeded to all obstructed, i
y=0, i
l1, i
l2the state of afterflow reduction together.
During power MOSFET tube S3 conducting, the current i of inductance L 1
l1increase; When S3 turns off, i
l1reduce; The current i of inductance L 1 can be controlled by the break-make of control S3
l1, now the electric current of inductance L 1 is a phase current, i
p=ia=i
l1.Therefore, i can be made by the break-make controlling power MOSFET tube S3
afollow the tracks of a phase voltage u
a.In like manner, i can be made by the break-make controlling power MOSFET tube S4
bfollow the tracks of b phase voltage u
b, i
n=i
b=-i
l2.According to the node current equation of Y point, c phase current i
c=i
y=i
l2-i
l1=-(i
a+ i
b), during three-phase symmetrical, if i
a, i
bfollow the tracks of respective phase voltage u
a, u
b, then i
calso phase voltage u is followed the tracks of
c, thus realize three-phase input current tracking three-phase input voltage.Can find out, power MOSFET tube S3, S4 voltage stress is output voltage U
o.
Two: buck pattern
As three phase rectifier output voltage u
pn>U
otime, circuit working is in buck pattern.With reference to accompanying drawing 7, now power MOSFET tube S3, S4 keeps turning off, and power MOSFET tube S1, S2 HF switch works, and as shown in Figure 8, arrow represents the reference positive direction of each state variable to simple equivalent circuit, because L1, L2 connect all the time, so i
l1=i
l2=i
l.S1, S2 control signal adopts trailing edge modulation, and namely each switch periods initial time, simultaneously open-minded.
(1) S1, S2 conducting simultaneously, current path is as Fig. 9 a.Voltage (u
pn-U
o) be added on L1, L2, i
lrise, simultaneously to storage capacitor C
f, load RL powers.
(2) S1 conducting, S2 turn off, and current path is as Fig. 9 b.If u
pY>U
o, then i
lincrease; Otherwise, i
lreduce.
(3) S1 shutoff, S2 conducting, current path is as Fig. 9 c.If u
nY>U
o, then i
lincrease; Otherwise, i
lreduce.
(4) S1, S2 turn off simultaneously, and current path is as Fig. 9 d.Back-pressure U
obe added on L1, L2, i
lafterflow reduces.
During power MOSFET tube S1 conducting, power MOSFET tube S1 current i
s1=i
l; When S1 turns off, i
s1=0; Can control S1 current i by the break-make of control S1
s1, now i
s1=i
p=i
a, therefore can make i by the break-make controlling power MOSFET tube S1
afollow the tracks of a phase voltage u
a.In like manner, i can be made by the break-make controlling power MOSFET tube S2
bfollow the tracks of b phase voltage u
b,-i
s2=i
n=i
b.According to the node current equation of Y point, i
c=i
y=i
s2-i
s1=-(i
a+ i
b), during three-phase symmetrical, if i
a, i
bfollow the tracks of respective phase voltage u
a, u
b, then i
calso phase voltage u is followed the tracks of
c, thus realize three-phase input current tracking three-phase input voltage.Power MOSFET tube S1, S2 voltage stress is three phase rectifier output voltage u
pnmaximum.
The working condition in other interval is similar with interval operating state 1., and from a complete power cycle, three-phase input current follows the tracks of three-phase input voltage.As can be seen from Figure 3, i
pfollow the tracks of the voltage u between three-phase commutation bridge positive output end and mains neutral line
pN, i
nfollow the tracks of the voltage u between three-phase commutation bridge negative output terminal and mains neutral line
nN, i
yit is the approximate triangular wave of three times of supply frequencies.
The foregoing is only preferred embodiment of the present invention, all equalizations done according to the present patent application the scope of the claims change and modify, and all should belong to covering scope of the present invention.
Claims (7)
1. a wide-voltage range low voltage stress current-injecting three-phase power factor correcting circuit, is characterized in that: comprise three-phase alternating current input power Uin, three-phase commutation bridge DB1, power MOSFET tube S1, power MOSFET tube S2, power MOSFET tube S3, power MOSFET tube S4, diode D1, diode D2, diode D3, harmonic current injection network, inductance L 1, inductance L 2, output filter capacitor Cf and load; Described harmonic current injection network comprises bidirectional switch Sy1, bidirectional switch Sy2 and bidirectional switch Sy3; Three of described three-phase alternating current input power Uin input phase voltages are connected with three inputs of three-phase commutation bridge DB1 respectively, and three of described three-phase alternating current input power Uin input phase voltages and are also connected with one end of bidirectional switch Sy1, one end of bidirectional switch Sy2, one end of bidirectional switch Sy3 respectively; The other end of the other end of described bidirectional switch Sy1, the other end of bidirectional switch Sy2 and bidirectional switch Sy3 is connected in decanting point Y; The positive output end of described three-phase commutation bridge DB1 is connected with the drain electrode of power MOSFET tube S1, and the negative output terminal of described three-phase commutation bridge DB1 is connected with the source electrode of power MOSFET tube S2; The source electrode of power MOSFET tube S1 is connected with one end of the negative electrode of diode D1 and inductance L 1, and the drain electrode of power MOSFET tube S2 is connected with one end of the anode of diode D2 and inductance L 2; The other end of inductance L 1 is connected with the anode of the drain electrode of power MOSFET tube S3 and diode D3, the other end of inductance L 2 is connected with the negative pole of the source electrode of power MOSFET tube S4, output filter capacitor Cf and one end of load RL, and the negative electrode of diode D3 is connected with the other end of the positive pole of output filter capacitor Cf and load RL; The source electrode of the anode of diode D1, the negative electrode of diode D2, power MOSFET tube S3 and the drain electrode of power MOSFET tube S4 are connected and described decanting point Y.
2. wide-voltage range low voltage stress current-injecting three-phase power factor correcting circuit according to claim 1, is characterized in that: described power MOSFET tube S1 and power MOSFET tube S2 or for IGBT power switch pipe.
3. wide-voltage range low voltage stress current-injecting three-phase power factor correcting circuit according to claim 1, is characterized in that: described power MOSFET tube S3 and power MOSFET tube S4 or recover the IGBT power switch pipe of power diode soon for inverse parallel.
4. wide-voltage range low voltage stress current-injecting three-phase power factor correcting circuit according to claim 1, is characterized in that: described diode D1, diode D2, diode D3 recover power diode soon.
5. wide-voltage range low voltage stress current-injecting three-phase power factor correcting circuit according to claim 1, is characterized in that: described bidirectional switch Sy1, bidirectional switch Sy2 and bidirectional switch Sy3 are formed by two power MOSFET tubes or two IGBT pipe differential concatenations.
6. wide-voltage range low voltage stress current-injecting three-phase power factor correcting circuit according to claim 1, is characterized in that: the mode of operation of described inductance L 1 and inductance L 2 is continuous current mode CCM, discontinuous current mode DCM or critical current mode BCM.
7. large step-down no-load voltage ratio harmonic current injection type three-phase power factor correcting circuit according to claim 1, is characterized in that: described output filter capacitor Cf is energy storage electrochemical capacitor.
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| CN107070196A (en) * | 2017-06-15 | 2017-08-18 | 南京航空航天大学 | A kind of three-phase PFC rectification circuits with center line |
| CN108462384A (en) * | 2018-06-09 | 2018-08-28 | 南昌航空大学 | A kind of three-phase step-down type PFC rectification circuits |
| CN110768527A (en) * | 2019-12-03 | 2020-02-07 | 哈尔滨理工大学 | Large-transformation-ratio Buck three-phase PFC circuit based on secondary Buck converter |
| CN110829826A (en) * | 2019-12-03 | 2020-02-21 | 哈尔滨理工大学 | Buck three-phase power factor correction circuit with large direct-current voltage gain |
| CN112003466A (en) * | 2020-07-21 | 2020-11-27 | 西安理工大学 | Three-phase APFC rectifier capable of realizing voltage boosting and reducing and working method thereof |
| CN112671251A (en) * | 2021-01-13 | 2021-04-16 | 茂硕电源科技股份有限公司 | Time-division multiplexing low-ripple buck-boost PFC converter, switching power supply and buck-boost method |
| CN113328620A (en) * | 2021-06-11 | 2021-08-31 | 燕山大学 | Three-phase harmonic current injection type voltage-raising and voltage-dropping converter |
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| 俞鹏飞，徐大林，祝振华: "《一种DSP控制的三相降压型PFC电路的研究》", 《电子测量技术》 * |
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| CN107070196A (en) * | 2017-06-15 | 2017-08-18 | 南京航空航天大学 | A kind of three-phase PFC rectification circuits with center line |
| CN108462384A (en) * | 2018-06-09 | 2018-08-28 | 南昌航空大学 | A kind of three-phase step-down type PFC rectification circuits |
| CN108462384B (en) * | 2018-06-09 | 2024-05-24 | 南昌航空大学 | Three-phase buck PFC rectification circuit |
| US11387730B2 (en) | 2018-11-02 | 2022-07-12 | Prodrive Technologies Innovation Services B.V. | Electrical power converter |
| CN110768527A (en) * | 2019-12-03 | 2020-02-07 | 哈尔滨理工大学 | Large-transformation-ratio Buck three-phase PFC circuit based on secondary Buck converter |
| CN110829826A (en) * | 2019-12-03 | 2020-02-21 | 哈尔滨理工大学 | Buck three-phase power factor correction circuit with large direct-current voltage gain |
| CN112003466A (en) * | 2020-07-21 | 2020-11-27 | 西安理工大学 | Three-phase APFC rectifier capable of realizing voltage boosting and reducing and working method thereof |
| CN112003466B (en) * | 2020-07-21 | 2021-12-17 | 西安理工大学 | Three-phase APFC rectifier capable of realizing voltage boosting and reducing and working method thereof |
| CN112671251A (en) * | 2021-01-13 | 2021-04-16 | 茂硕电源科技股份有限公司 | Time-division multiplexing low-ripple buck-boost PFC converter, switching power supply and buck-boost method |
| CN112671251B (en) * | 2021-01-13 | 2024-05-31 | 茂硕电源科技股份有限公司 | Time-sharing multiplexing low-ripple buck-boost PFC converter, switching power supply and buck-boost method |
| CN113328620A (en) * | 2021-06-11 | 2021-08-31 | 燕山大学 | Three-phase harmonic current injection type voltage-raising and voltage-dropping converter |
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|---|---|
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