CN113489309A - Bridgeless buck power factor correction converter with wide output voltage and control method - Google Patents
Bridgeless buck power factor correction converter with wide output voltage and control method Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1582—Buck-boost converters
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The invention discloses a bridgeless buck power factor correction converter with wide output voltage and a control method, relating to the technical field of converters, and the key points of the technical scheme are as follows: the transformer comprises a first rectifying diode, a second rectifying diode, a first switching tube, a second switching tube, a first inductor, a second inductor, a third inductor, an ideal transformer, a first extra diode, a second extra diode, a first diode, a second diode, a load and an output capacitor. The converter eliminates an input current dead zone by sharing a switching tube with the buck-boost conversion unit, realizes simplification of control and solves the problem of output voltage limitation caused by input current harmonic waves to a certain extent; in addition, the converter can realize bridgeless operation to relieve the efficiency problem caused by the extra diode needed by the conversion unit; the converter has the characteristics of simple control, high power factor, small input current harmonic wave and wide output voltage.
Description
Technical Field
The invention relates to the technical field of converters, in particular to a bridgeless buck power factor correction converter with wide output voltage and a control method.
Background
The conversion of Alternating Current (AC) to Direct Current (DC) is currently an important electrical energy conversion, i.e. AC-DC conversion. In order to meet the requirements of input current harmonics (THDi) and Power Factor (PF), an AC-DC Power Factor Correction (PFC) converter is generally required. With the great aim of carbon neutral emission and the initiative of energy conservation in 2060 years in China, the high-efficiency bridgeless AC-DC PFC converter is increasingly researched and applied. The key of the bridgeless AC-DC PFC converter is that a diode rectifier bridge is not used, namely, energy loss caused by the fact that two diodes of the diode rectifier bridge are always conducted is avoided, and therefore the efficiency of the converter is improved. On the other hand, with the application of a large number of smart mobile devices, such as patrol electronic robots, electric drones, electric automobiles, electric unmanned submarines, etc., at present, their battery charging devices need to become more intelligent. Different charging modes can actually influence the service life of the battery pack, the service life of the battery pack is prolonged, the inconvenience of battery replacement in the use stage of equipment can be avoided, the reliability and the service life of the equipment are improved, and the popularization and the commercialization of the equipment are facilitated.
Against the two application backgrounds mentioned above, there are two problems at present.
At present, research on bridgeless AC-DC PFC converters mainly focuses on boosting type (Boost), other Buck type (Buck), Buck-Boost type (Buck-Boost), Cuk type and other PFC converters which are relatively less researched. In fact, in some battery charging applications with power of hundreds of watts, the step-down bridgeless AC-DC PFC converter has higher application value. Particularly, the output voltage does not need to be very high, the number and the design complexity of the post-stage DC-DC converter can be reduced by setting lower PFC converter output voltage, and the improvement of the overall system efficiency and the simplification of the overall system complexity are facilitated. However, as shown in fig. 1, the conventional AC-DC buck PFC converter has input current dead band, and requires setting a lower output voltage and adopting a proper control scheme to meet the power factor and input current harmonic requirements. However, limiting the output voltage actually limits the application scenarios of the converter, which is not favorable for the popularization and application of the buck PFC converter.
On the other hand, as shown in fig. 2 (a), although the learners propose the bridgeless buck PFC converter, the bridgeless buck PFC converter still has an input current dead zone, and the problem of the conventional buck PFC converter still exists. As shown in fig. 2 (b), there is a problem that a multi-switching control buck PFC converter without an input current dead zone has a complicated control because it is necessary to check a dead time to control a switching tube to switch the operating state of the converter. In addition, the buck PFC converter topology in the prior document needs to control the switching tube to switch two working states to eliminate the input current dead zone, and in order to avoid the problem of increasing the input current harmonic between the two working state transitions, a fixed switching voltage and an output voltage (130V) need to be set to ensure low input current harmonic and high power factor. I.e. its input current harmonics are still very correlated with the output voltage, and a wide range of regulation of the output voltage cannot be achieved.
Therefore, how to research and design a bridgeless buck power factor correction converter with wide output voltage and a control method thereof are problems which need to be solved urgently at present.
Disclosure of Invention
In order to solve the defects in the prior art, the invention aims to provide a bridgeless buck power factor correction converter with wide output voltage and a control method.
The technical purpose of the invention is realized by the following technical scheme:
in a first aspect, there is provided a bridgeless buck power factor correction converter for wide output voltages, comprising:
first rectifying diode DR1A second rectifying diode DR2A first switch tube S1A second switch tube S2A first inductor L1A second inductor L2A third inductor L3Ideal transformer T1A first extra diode DE1A second extra diode DE2A first diode D1A second diode D2Load RLAn output capacitor Co；
First rectifying diode DR1Anode of and a second rectifying diode DR2The cathodes are all externally connected with an input voltage source vinAt one end of the first and second arms,first inductance L1One terminal of (1), a second inductance L2One end of (1), ideal transformer T1Primary side non-homonymous terminal ideal transformer T1The same-name ends of the secondary sides are all externally connected with an input voltage source vinThe other end of (a);
first rectifying diode DR1The cathode of the first switch tube S1Source electrode of, the second rectifying diode DR2Anode of the first switching tube S is connected with the second switching tube S2A drain electrode of (1);
first switch tube S1The drain electrode of the first inductor L is connected with the drain electrode of the second inductor L in sequence1Another end of (1), ideal transformer T1Primary side dotted terminal of, a second diode D2Cathode of (2), third inductance L3One end of (a);
a second switch tube S2Is connected with a second inductor L in sequence2Another end of (1), ideal transformer T1The secondary side non-dotted terminal of (A), a first extra diode (D)E1Cathode, first diode D1The anode of (1);
second diode D2Is connected to a first extra diode DE1Anode of (2), output capacitor CoNegative terminal of and load RLIs connected with one end of the connecting rod; third inductance L3Is connected to a second extra diode DE2The anode of (1); second extra diode DE2The cathode of the first diode D is connected in turn1Cathode and output capacitor CoAnode and load R ofLAnd the other end of the same.
Further, the first rectifying diode DR1A second rectifying diode DR2A first switch tube S1A second switch tube S2A third inductor L3A first extra diode DE1A second extra diode DE2A second diode D2Load RLAn output capacitor CoA step-down conversion unit is formed;
first rectifying diode DR1A second rectifying diode DR2A first switch tube S1A second switch tube S2A first inductor L1A second inductor L2To do and manageTransformer T1A first diode D1A second diode D2Load RLAn output capacitor CoForming a buck-boost conversion unit;
when the input voltage vinGreater than the output voltage VoWhen the voltage reduction conversion unit and the voltage increase conversion unit are in working states;
when the input voltage vinLess than the output voltage VoAnd only the voltage boosting and reducing conversion unit is in a working state.
Furthermore, the buck conversion unit and the buck-boost conversion unit are both in working states, and the first inductor L1Charging duty cycle d of1Equal to the third inductance L3According to the charging duty cycle of the first inductor L1A third inductor L3The first inductance L is voltage-second balanced1Is always smaller than the third inductance L3The converter comprises the following working modes:
working modes a, [0, d1TS]: first switch tube S1In the on state, an AC input current passes through S1、L1、DR1Is a first inductance L1Charging; at the same time, the AC input voltage vinThrough an ideal transformer T1Second inductance L with primary side as secondary side2Charging; and an alternating input current passes through DR1、S1、L3、DE1、DE2、Co、RL、T1The secondary side of the inductor is a third inductor L3An output capacitor CoCharging energy, also load RLSupplying power; at this stage, the inductor current iL1、iL2、iL3Linear increase, iL1＝iL2；
Working mode b, [ d ]1TS，d1TS+d2L3TS]: first switch tube S1In the off state, the inductor current iL3Through DE2、Co、D2、RLIs a third inductance L3Discharge, also output capacitor CoAnd a load RLEnergy supply; at the same time, the inductor current iL1、iL2Through D1、Co、D2、RLIs an inductance L1、L2Discharge, also output capacitor CoAnd a load RLEnergy supply; at this stage, the inductor current iL1、iL2、iL3Linear decrease, iL1＝iL2；
Working mode c, [ d ]1TS+d2L3TS，d1TS+d2L1TS]: first switch tube S1In the off state, the inductor current iL1、iL2Go on through D1、Co、D2Is an inductance L1、L2Discharge, also output capacitor CoAnd a load RLEnergy supply; at the same time, the inductor current iL3The continued flow is over; at this stage, the inductor current iL1、iL2Continuing to linearly decrease;
working mode d, [ d ]1TS+d2L1TS，TS]: first switch tube S1In the off state, the inductor current iL1、iL2、iL3The continued flow is over; load RLFrom an output capacitor CoAnd (4) supplying power.
Further, the first inductor L1And a second inductor L2The inductance values of (a) and (b) are the same.
Further, when only the buck conversion unit is in an operating state, the converter includes the following operating modes:
Mode of operation 2, [ d ]1TS，d1TS+d2L1TS]: first switch tube S1In the off state, the inductor current iL1、iL2Through D1、Co、D2Is an inductance L1、L2Discharge, also output capacitor CoAnd a load RLEnergy supply; at this stage, the inductor current iL1、iL2A linear decrease;
working mode 3, [ d ]1TS+d2L1TS，TS]: first switch tube S1In the off state, the inductor current iL1、iL2The continued flow is over; load RLFrom an output capacitor CoAnd (4) supplying power.
In a second aspect, a converter control method is provided for controlling the bridgeless buck power factor correction converter with wide output voltage according to any one of the first aspect, including the following steps:
sampling the output voltage of the converter through a sampling circuit to obtain a sampling value;
inputting the sampling value into an adder-subtractor, and comparing the sampling value with a reference voltage to obtain a comparison result;
the comparison result is transported through a PI parameter arithmetic unit to obtain an output voltage error feedback signal;
after the output voltage error feedback signal and the triangular wave are compared by the comparator, the output is used for controlling the first switch tube S1A second switch tube S2The drive signal of (1).
Further, the first switch tube S1A second switch tube S2And responding to the same driving signal to realize closed-loop control by adopting the single voltage ring.
Further, the first switch tube S1A second switch tube S2And the on-off control of a single switching tube is controlled by detecting the positive and negative half cycles of the input voltage.
Compared with the prior art, the invention has the following beneficial effects:
1. the buck conversion unit (buck) and the buck-boost unit (buck-boost) in the converter provided by the invention run in parallel and simultaneously, so that the working state of the converter is judged without detecting input voltage, closed-loop control can be realized only by a single voltage ring, the control is simple, and the problems of unstable converter output, PF (pulse frequency) interference, increased design difficulty and the like caused by switching of the working states are solved;
2. the converter provided by the invention realizes bridgeless operation, and can reduce the influence of efficiency reduction caused by adding extra diodes as much as possible;
3. the converter provided by the invention has wider output voltage due to automatic switching of the working state, the converter can not fix the output voltage for ensuring low THDi any more, and the wide output voltage can be set according to the application scene without greatly influencing the THDi and PF values of the converter.
Drawings
The accompanying drawings, which are included to provide a further understanding of the embodiments of the invention and are incorporated in and constitute a part of this application, illustrate embodiment(s) of the invention and together with the description serve to explain the principles of the invention. In the drawings:
FIG. 1 is a schematic circuit diagram of a conventional buck PFC converter, with topology shown in FIG. 1(a), and input current dead time determined by input and output voltages shown in FIG. 1 (a);
fig. 2 is a schematic diagram of two bridgeless buck PFC converters in the prior art, wherein (a) is a bridgeless topology in which an input current dead zone still exists, and (b) is a bridgeless topology in which a flyback (flyback) is adopted to eliminate the input current dead zone for a parallel conversion unit;
FIG. 3 is a circuit schematic of a converter in an embodiment of the invention;
FIG. 4 is a control schematic of the converter in an embodiment of the present invention;
FIG. 5 shows an input voltage v according to an embodiment of the present inventioninGreater than the output voltage VoThe equivalent circuit diagram is shown, wherein a is a working mode a, b is a working mode b, c is a working mode c, and d is a working mode d;
FIG. 6 is an input in an embodiment of the present inventionVoltage vinGreater than the output voltage VoA theoretical waveform diagram of a key device in a time-switching period;
FIG. 7 shows an input voltage v according to an embodiment of the present inventioninLess than the output voltage VoThe equivalent circuit diagram is shown, wherein a is a working mode 1, b is a working mode 2, and c is a working mode 3;
FIG. 8 shows an input voltage v according to an embodiment of the present inventioninLess than the output voltage VoA theoretical waveform diagram of a key device in a time-switching period;
FIG. 9 is a theoretical waveform diagram of input voltage, input current, and output voltage over a half power frequency cycle in an embodiment of the present invention;
FIG. 10 is a simulation of the key waveforms of the device during the AC input power frequency cycle in an embodiment of the present invention;
FIG. 11 is a diagram of simulation results of the transducers THDi and PF in the embodiment of the present invention, a: the output is 90V, b: the output is 120V, c: output 150V, d: the output is 180V;
FIG. 12 shows an input voltage v according to an embodiment of the present inventioninGreater than the output voltage VoA device key waveform simulation diagram under the time scale of the switching period;
FIG. 13 shows an input voltage v according to an embodiment of the present inventioninLess than the output voltage VoAnd (3) a device key waveform simulation diagram under the time scale of the switching period.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention is further described in detail below with reference to examples and accompanying drawings, and the exemplary embodiments and descriptions thereof are only used for explaining the present invention and are not meant to limit the present invention.
Example 1: a bridgeless buck power factor correction converter with wide output voltage, as shown in FIG. 3, includes a first rectifying diode DR1A second rectifying diode DR2A first switch tube S1A second switch tube S2A first inductor L1A second inductor L2A third inductor L3To do and manageTransformer T1A first extra diode DE1A second extra diode DE2A first diode D1A second diode D2Load RLAn output capacitor Co。
Wherein the first rectifying diode DR1Anode of and a second rectifying diode DR2The cathodes are all externally connected with an input voltage source vinOne end of (1), a first inductance L1One terminal of (1), a second inductance L2One end of (1), ideal transformer T1Primary side non-homonymous terminal ideal transformer T1The same-name ends of the secondary sides are all externally connected with an input voltage source vinAnd the other end of the same. First rectifying diode DR1The cathode of the first switch tube S1Source electrode of, the second rectifying diode DR2Anode of the first switching tube S is connected with the second switching tube S2Of the substrate. First switch tube S1The drain electrode of the first inductor L is connected with the drain electrode of the second inductor L in sequence1Another end of (1), ideal transformer T1Primary side dotted terminal of, a second diode D2Cathode of (2), third inductance L3To one end of (a). A second switch tube S2Is connected with a second inductor L in sequence2Another end of (1), ideal transformer T1The secondary side non-dotted terminal of (A), a first extra diode (D)E1Cathode, first diode D1Of (2) an anode. Second diode D2Is connected to a first extra diode DE1Anode of (2), output capacitor CoNegative terminal of and load RLIs connected with one end of the connecting rod; third inductance L3Is connected to a second extra diode DE2The anode of (1); second extra diode DE2The cathode of the first diode D is connected in turn1Cathode and output capacitor CoAnode and load R ofLAnd the other end of the same.
First rectifying diode DR1A second rectifying diode DR2A first switch tube S1A second switch tube S2A third inductor L3A first extra diode DE1A second extra diode DE2A second diode D2Load RLAn output capacitor CoForm a pressure reducing conversion sheetAnd (5) Yuan. First rectifying diode DR1A second rectifying diode DR2A first switch tube S1A second switch tube S2A first inductor L1A second inductor L2Ideal transformer T1A first diode D1A second diode D2Load RLAn output capacitor CoAnd forming a buck-boost conversion unit. When the input voltage vinGreater than the output voltage VoWhen the voltage reduction conversion unit and the voltage increase conversion unit are in working states; when the input voltage vinLess than the output voltage VoAnd only the voltage boosting and reducing conversion unit is in a working state.
When the input voltage v is as shown in FIG. 5inGreater than the output voltage VoDuring the process, the buck conversion unit and the buck-boost conversion unit are both in working states, the buck conversion unit and the buck-boost conversion unit of the converter can operate, and the converter has 4 equivalent working modes. And according to the first inductance L1A third inductor L3The first inductance L is voltage-second balanced1Is always smaller than the third inductance L3Discharge duty cycle of (d).
FIG. 6 is a graph when v isin>VoIn a switching period T of the converter of the inventionSThe key device comprises a first switch tube S1Drive signal vS1A second switch tube S2Drive signal vS2Current i of the first switching tubeS1First inductance L1Current i ofL1And its current peak value IL1,pkCurrent i of the second inductorL2And its current peak value IL2,pkCurrent i of the third inductorL3And its current peak value IL3,pkCurrent i of the first extra diodeDE1Current i of the second diodeD2. In FIG. 6, d1Is a first inductance L1A second inductor L2A third inductor L3Duty ratio during charging, d2L1Is a first inductance L1Duty ratio at discharge, d2L3Is the third inductance L3Duty cycle at discharge. The specific working mode is described as follows:
working modes a, [0, d1TS]: first switch tube S1In the on state, an AC input current passes through S1、L1、DR1Is a first inductance L1Charging; at the same time, the AC input voltage vinThrough an ideal transformer T1Second inductance L with primary side as secondary side2Charging; and an alternating input current passes through DR1、S1、L3、DE1、DE2、Co、RL、T1The secondary side of the inductor is a third inductor L3An output capacitor CoCharging energy, also load RLSupplying power; at this stage, the inductor current iL1、iL2、iL3Linear increase, iL1＝iL2，iT1＝-iT2；
Working mode b, [ d ]1TS，d1TS+d2L3TS]: first switch tube S1In the off state, the inductor current iL3Through DE2、Co、D2、RLIs a third inductance L3Discharge, also output capacitor CoAnd a load RLEnergy supply; at the same time, the inductor current iL1、iL2Through D1、Co、D2、RLIs an inductance L1、L2Discharge, also output capacitor CoAnd a load RLEnergy supply; at this stage, the inductor current iL1、iL2、iL3Linear decrease, iL1＝iL2；
Working mode c, [ d ]1TS+d2L3TS，d1TS+d2L1TS]: first switch tube S1In the off state, the inductor current iL1、iL2Go on through D1、Co、D2Is an inductance L1、L2Discharge, also output capacitor CoAnd a load RLEnergy supply; at the same time, the inductor current iL3The continued flow is over; at this stage, the inductor current iL1、iL2Continuing to linearly decrease;
working mode d, [ d ]1TS+d2L1TS，TS]: first switch tube S1In the off state, the inductor current iL1、iL2、iL3The continued flow is over; load RLFrom an output capacitor CoAnd (4) supplying power.
In the positive half period of the AC input, the above 4 working modes will cycle until the input voltage vinLess than the output voltage VoWhen the converter enters into another working state, namely buck-boost working state.
In the present embodiment, the first inductor L1And a second inductor L2The inductance values of the two capacitors are the same, and the symmetry of positive and negative half-cycle input waveforms is effectively kept.
As shown in fig. 7, when the voltage v is inputtedinLess than the output voltage VoIn time, the buck conversion unit of the converter does not operate any more, but only the buck-boost conversion unit operates, and the converter has 3 equivalent circuits. At this time, since the buck-boost conversion unit is still running, the converter input current is not 0, i.e., there is no input current dead zone.
FIG. 8 is a graph when v isin<VoTime converter in a switching period TSThe waveform schematic diagram of the key device. Since the buck converter unit is not operating, the inductor current iL4Is 0. The specific working mode is described as follows:
working mode 1, [0, d1TS]: first switch tube S1In the on state, an AC input current passes through S1、L1、DR1Is an inductance L1Charging; at the same time, the AC input voltage vinThrough an ideal transformer T1Second inductance L with primary side as secondary side2Charging; output capacitor CoIs a load RLEnergy supply; at this stage, the inductor current iL1、iL2Linearly increase, and iL1＝iL2，iT1＝-iT2；
Mode of operation 2, [ d ]1TS，d1TS+d2L1TS]: first switch tube S1In the off state, the inductor current iL1、iL2Through D1、Co、D2Is an inductance L1、L2Discharge, also output capacitor CoAnd a load RLEnergy supply; at this stage, the inductor current iL1、iL2A linear decrease;
working mode 3, [ d ]1TS+d2L1TS，TS]: first switch tube S1In the off state, the inductor current iL1、iL2The continued flow is over; load RLFrom an output capacitor CoAnd (4) supplying power.
In the positive half period of the AC input, the above 3 working modes will cycle until the input voltage vinGreater than the output voltage VoWhen the converter is in the buck and buck-boost working state.
FIG. 9 shows the input current i of the converterinInput voltage vinAnd an output voltage VoThe theoretical relationship diagram of (1). It can be seen in FIG. 9 that when v isin<VoIn time, due to the operation of the buck-boost conversion unit, the dead zone of the original input current of the converter does not exist any more. And because the converter always runs in the buck-boost conversion unit, when the buck conversion unit does not run any more, the working state of the converter is automatically switched without additional switching action, thereby simplifying the control requirement of the converter. The converter does not need to fix the output voltage and the switching voltage to maintain the PF value and the THDi value when the working state of the converter is switched.
One, single voltage ring closed loop control
Fig. 4 is a schematic diagram of a single voltage loop closed-loop control circuit adopted by two bridgeless buck PFC converters, which includes an output voltage sampling, an adder-subtractor, a PI parameter arithmetic unit, an output voltage reference signal, a sawtooth wave signal and a comparator. The closed-loop control is realized as follows: sampling the output voltage of the converter through a sampling circuit to obtain a sampling value; inputting the sampling value into an adder-subtractor, and comparing the sampling value with a reference voltage to obtain a comparison result; comparing the results by PI parameter arithmetic unitTransporting to obtain an output voltage error feedback signal; after the output voltage error feedback signal and the triangular wave are compared by the comparator, the output is used for controlling the first switch tube S1A second switch tube S2The drive signal of (1).
The first switch tube S1A second switch tube S2And responding to the same driving signal to realize closed-loop control by adopting the single voltage ring. Or, the first switch tube S1A second switch tube S2The on-off control of a single switching tube is controlled by detecting the positive and negative half cycles of the input voltage, so that the driving loss of the switching tube can be avoided.
Second, simulation result of converter
The principle and the control mode of the converter are verified by adopting PSIM simulation software. The main circuit parameters are as follows: the AC input voltage is 220Vac, the output DC voltage is 90-180V, the output capacitance is 990uF, and the inductance L1＝L2100uH, inductance L3380uH, the switching frequency is 50kHz, and the output power is 200W.
FIG. 10 is a waveform simulation diagram of key components of the converter on the time scale of the AC power frequency cycle. It can be seen that each waveform of the converter conforms to the theoretical analysis waveform, and the operation is stable without input current iinDead time, switching tube S1、S2Alternatively works in a half power frequency period, and realizes bridgeless operation.
FIGS. 11(a) - (d) show the PF value, THDi at different output voltages V of the bridgeless buck PFC converter of the present inventionoSimulated measurements of the situation. It can be seen that the value of PF of the converter of the invention can be maintained above 0.99 under different output voltage conditions, and the value of THDi is about 5% or below.
FIG. 12 is a graph of the time scale when v is on the switching cyclein>VoA waveform simulation diagram of key devices of a time-varying converter. It can be seen that the waveform diagram of the key components of the converter is consistent with the theoretical waveform diagram shown in fig. 6, which illustrates that the working mode of the converter is consistent with the theoretical analysis.
FIG. 13 shows the time scale when v is on the switching cyclein<VoA waveform simulation diagram of key devices of a time-varying converter. It can be seen that the waveform diagram of the key components of the converter is consistent with the theoretical waveform diagram shown in fig. 8, which illustrates that the working mode of the converter is consistent with the theoretical analysis.
According to the theoretical analysis and simulation results, the bridgeless buck PFC converter with the high power factor and the wide output voltage can realize a higher PF value and a lower THDi value in a wider output voltage range, and can realize elimination of an input current dead zone and bridgeless operation by adopting a simple single voltage loop. The invention has simple control, has the performance characteristics of high power factor and low input current harmonic wave in a wider output voltage range, and can be suitable for wider application scenes by setting higher output voltage, thereby having obvious technical advantages compared with the prior technical scheme.
The working principle is as follows: the converter eliminates an input current dead zone by sharing a switching tube with the buck conversion unit and the buck-boost conversion unit, realizes simplification of control and solves the problem of output voltage limitation caused by input current harmonic waves to a certain extent. In addition, the converter can realize bridgeless operation to relieve the efficiency problem caused by the additional diode needed by the conversion unit. The converter has the characteristics of simple control, high power factor, small input current harmonic wave and wide output voltage.
The above-mentioned embodiments are intended to illustrate the objects, technical solutions and advantages of the present invention in further detail, and it should be understood that the above-mentioned embodiments are merely exemplary embodiments of the present invention, and are not intended to limit the scope of the present invention, and any modifications, equivalent substitutions, improvements and the like made within the spirit and principle of the present invention should be included in the scope of the present invention.
Claims (8)
1. A bridgeless buck power factor correction converter with wide output voltage is characterized by comprising:
first rectifying diode DR1A second rectifying diode DR2A first switch tube S1A second switch tube S2A first inductor L1A second inductor L2A third inductor L3Ideal transformer T1A first extra diode DE1A second extra diode DE2A first diode D1A second diode D2Load RLAn output capacitor Co；
First rectifying diode DR1Anode of and a second rectifying diode DR2The cathodes are all externally connected with an input voltage source vinOne end of (1), a first inductance L1One terminal of (1), a second inductance L2One end of (1), ideal transformer T1Primary side non-homonymous terminal ideal transformer T1The same-name ends of the secondary sides are all externally connected with an input voltage source vinThe other end of (a);
first rectifying diode DR1The cathode of the first switch tube S1Source electrode of, the second rectifying diode DR2Anode of the first switching tube S is connected with the second switching tube S2A drain electrode of (1);
first switch tube S1The drain electrode of the first inductor L is connected with the drain electrode of the second inductor L in sequence1Another end of (1), ideal transformer T1Primary side dotted terminal of, a second diode D2Cathode of (2), third inductance L3One end of (a);
a second switch tube S2Is connected with a second inductor L in sequence2Another end of (1), ideal transformer T1The secondary side non-dotted terminal of (A), a first extra diode (D)E1Cathode, first diode D1The anode of (1);
second diode D2Is connected to a first extra diode DE1Anode of (2), output capacitor CoNegative terminal of and load RLIs connected with one end of the connecting rod; third inductance L3Is connected to a second extra diode DE2The anode of (1); second extra diode DE2The cathode of the first diode D is connected in turn1Cathode and output capacitor CoAnode and load R ofLAnd the other end of the same.
2. The wide output voltage of claim 1The bridgeless buck power factor correction converter is characterized in that the first rectifier diode DR1A second rectifying diode DR2A first switch tube S1A second switch tube S2A third inductor L3A first extra diode DE1A second extra diode DE2A second diode D2Load RLAn output capacitor CoA step-down conversion unit is formed;
first rectifying diode DR1A second rectifying diode DR2A first switch tube S1A second switch tube S2A first inductor L1A second inductor L2Ideal transformer T1A first diode D1A second diode D2Load RLAn output capacitor CoForming a buck-boost conversion unit;
when the input voltage vinGreater than the output voltage VoWhen the voltage reduction conversion unit and the voltage increase conversion unit are in working states;
when the input voltage vinLess than the output voltage VoAnd only the voltage boosting and reducing conversion unit is in a working state.
3. The bridgeless buck-type power factor correction converter with wide output voltage according to claim 2, wherein the buck conversion unit and the buck-boost conversion unit are both in working states, and the first inductor L is1Charging duty cycle d of1Equal to the third inductance L3According to the charging duty cycle of the first inductor L1A third inductor L3The first inductance L is voltage-second balanced1Is always smaller than the third inductance L3The converter comprises the following working modes:
working modes a, [0, d1TS]: first switch tube S1In the on state, an AC input current passes through S1、L1、DR1Is a first inductance L1Charging; at the same time, the AC input voltage vinThrough an ideal transformer T1Primary side of isSecond inductance L of secondary side2Charging; and an alternating input current passes through DR1、S1、L3、DE1、DE2、Co、RL、T1The secondary side of the inductor is a third inductor L3An output capacitor CoCharging energy, also load RLSupplying power; at this stage, the inductor current iL1、iL2、iL3Linear increase, iL1＝iL2；
Working mode b, [ d ]1TS，d1TS+d2L3TS]: first switch tube S1In the off state, the inductor current iL3Through DE2、Co、D2、RLIs a third inductance L3Discharge, also output capacitor CoAnd a load RLEnergy supply; at the same time, the inductor current iL1、iL2Through D1、Co、D2、RLIs an inductance L1、L2Discharge, also output capacitor CoAnd a load RLEnergy supply; at this stage, the inductor current iL1、iL2、iL3Linear decrease, iL1＝iL2；
Working mode c, [ d ]1TS+d2L3TS，d1TS+d2L1TS]: first switch tube S1In the off state, the inductor current iL1、iL2Go on through D1、Co、D2Is an inductance L1、L2Discharge, also output capacitor CoAnd a load RLEnergy supply; at the same time, the inductor current iL3The continued flow is over; at this stage, the inductor current iL1、iL2Continuing to linearly decrease;
working mode d, [ d ]1TS+d2L1TS，TS]: first switch tube S1In the off state, the inductor current iL1、iL2、iL3The continued flow is over; load RLFrom an output capacitor CoAnd (4) supplying power.
4. The wide output voltage bridgeless buck power factor correction converter according to claim 1, wherein the first inductor L1And a second inductor L2The inductance values of (a) and (b) are the same.
5. The bridgeless buck power factor correction converter according to claim 2, wherein the converter comprises the following modes of operation only when the buck conversion unit is in operation:
working mode 1, [0, d1TS]: first switch tube S1In the on state, an AC input current passes through S1、L1、DR1Is an inductance L1Charging; at the same time, the AC input voltage vinThrough an ideal transformer T1Second inductance L with primary side as secondary side2Charging; output capacitor CoIs a load RLEnergy supply; at this stage, the inductor current iL1、iL2Linearly increase, and iL1＝iL2，iL2＝-iT2；
Mode of operation 2, [ d ]1TS，d1TS+d2L1TS]: first switch tube S1In the off state, the inductor current iL1、iL2Through D1、Co、D2Is an inductance L1、L2Discharge, also output capacitor CoAnd a load RLEnergy supply; at this stage, the inductor current iL1、iL2A linear decrease;
working mode 3, [ d ]1TS+d2L1TS，TS]: first switch tube S1In the off state, the inductor current iL1、iL2The continued flow is over; load RLFrom an output capacitor CoAnd (4) supplying power.
6. A converter control method for controlling a bridgeless buck power factor correction converter with wide output voltage according to any one of claims 1 to 5, comprising the steps of:
sampling the output voltage of the converter through a sampling circuit to obtain a sampling value;
inputting the sampling value into an adder-subtractor, and comparing the sampling value with a reference voltage to obtain a comparison result;
the comparison result is transported through a PI parameter arithmetic unit to obtain an output voltage error feedback signal;
after the output voltage error feedback signal and the triangular wave are compared by the comparator, the output is used for controlling the first switch tube S1A second switch tube S2The drive signal of (1).
7. The inverter control method according to claim 6, wherein the first switching tube S1A second switch tube S2And responding to the same driving signal to realize closed-loop control by adopting the single voltage ring.
8. The inverter control method according to claim 6, wherein the first switching tube S1A second switch tube S2And the on-off control of a single switching tube is controlled by detecting the positive and negative half cycles of the input voltage.
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