CMOS reference voltage source circuit
Technical field
The present invention relates to CMOS transistor circuit engineering field, particularly relate to CMOS reference voltage source circuit.
Background technology
In simulation, numerical model analysis, and often can use reference voltage source in digital circuit, its stability is directly connected to the performance of whole circuit.General conventional reference voltage source adopts BiCMOS technique, as a kind of traditional bandgap reference voltage source circuit that Fig. 1 provides, comprises triode transistor Q
1and Q
2, error amplifier OP, feedback resistance R
1and R
2, adjusting resistance R
3; Transistor Q
1and Q
2emitter analogue ground AVSS, amplifier two input ends are connected node A and B respectively, and output terminal exports V
rEF, contact resistance R simultaneously
1and R
2.Amplifier operation is in profound and negative feedbck, and two input end connected node A and B respectively, make two point voltages equal, connect the identical resistance R of two resistances simultaneously
1and R
2, make to flow through Q
1and Q
2two-way electric current equal, thus to obtain:
V
BE1-V
BE2=I
2R
3=V
TlnN (1)
And then obtain output voltage VO UT:
There is following two problems in this circuit, first, and usual V
rEFfor about 1.25V, can not be applied in low-voltage circuit; Secondly, the method needs to use transistor and metal-oxide-semiconductor jointly to realize, and proposes requirement to technique.
Fig. 2 gives a kind of improved plan, M in band-gap circuit
1, M
2and M
3composition current mirror, amplifier OP
1be in .0 profound and negative feedbck state, making AB two point voltage equal, is V
bE, namely flow through R
2electric current be V
bE/ R
2, there is negative temperature coefficient, and by resistance R
1electric current be the electric current with VT direct proportionality, two-way electric current sum flows through M
2, be copied to I
3, then resistance R3 both end voltage is:
Suitably choose N, R
1, R
2and R
3the output voltage V of zero-temperature coefficient can be obtained
rEF, and the temperature coefficient of output voltage and R
3independent mutually, the bandgap voltage reference namely exported can regulate.But this circuit is same with technology one employs transistor, need to use BiCMOS technique, this reference circuit cannot be used under CMOS technology.
Fig. 3 gives a kind of band-gap reference circuit of CMOS technology, M in this band-gap circuit
1and M
3be operated in sub-threshold region, namely flow through M
1and M
3electric current be respectively
M
2and M
4pipe connects into current mirror form, and breadth length ratio is equal, namely
I
1=I
2(6)
Warp (4), (5), (6) obtain
Knownly flow through resistance R
1electric current be
I
2temperature coefficient and V
tproportional, i.e. I
2for positive temperature coefficient (PTC) electric current.
M
6pipe and M
4pipe forms current mirror, is M
5there is provided stable drain-source current, M
7the clamped M of gate source voltage of pipe
5drain-gate voltage, make M
5steady operation is in sub-threshold region.Flow through resistance R
2electric current I
4for
The gate source voltage of sub-threshold region metal-oxide-semiconductor has negative temperature coefficient, i.e. electric current I
4for negative temperature parameter current.M
9and M
4, M
10and M
8form current mirror respectively, i.e. I
5, I
6copy positive temperature coefficient (PTC) electric current and negative temperature parameter current respectively, superposition and resistance R
3, form the output voltage V of zero-temperature coefficient
rEF.
The shortcoming of this circuit is M
1, M
3all be operated in sub-threshold region, gate source voltage is less, but R
1need to get a part of pressure drop, so M
1, M
3gate source voltage have significant difference.By process deviation influence, M in side circuit
1gate source voltage likely exceed threshold voltage, cannot ensure to be operated in sub-threshold region, produce estimate positive temperature coefficient (PTC) electric current, therefore reliability is poor.
In order to improve the processing compatibility of the band-gap reference circuit shown in Fig. 1,2, cmos circuit structure must be adopted.In addition, in order to improve the dirigibility of the output voltage of reference circuit shown in Fig. 1, improve the stability of reference circuit shown in Fig. 3 simultaneously, then need to adopt new circuit structure.
Summary of the invention
For the problems referred to above, the object of the invention is to design and be suitable for realizing in CMOS technology, the reference voltage source circuit of high reliability and dirigibility.
The present invention adopts following technical scheme: a kind of CMOS reference voltage source circuit, comprising: start-up circuit, and it, after connection direct supply, provides trigger voltage; First bias current generating circuit, for receiving the trigger voltage that start-up circuit provides, producing the first bias current, and providing output voltage, and the temperature coefficient direction of the first bias current is first direction; Second bias current generating circuit, for receiving output voltage that the first bias current generating circuit provides as input, produce the second bias current, the temperature coefficient direction of the second bias current is second direction; Reference voltage generating circuit, for receiving the first bias current and the second bias current as input, obtains reference voltage by adjusting first, second bias current.
The present invention adopts standard CMOS process to realize, and circuit structure does not need triode transistor; Adopt mode electric currents different for two-way temperature characterisitic being superimposed on same resistance, using the reference voltage that the voltage at resistance two ends goes to zero as temperature coefficient, therefore reference voltage value can flexible, to be applicable to different circuit requirements simultaneously; In addition, the MOS device being operated in sub-threshold region of employing, add coupling and negative feedback design, therefore this circuit structure is not subject to the impact of process deviation and voltage dithering, ensure that the reliability of whole reference voltage source circuit.The circuit realizing this bandgap voltage reference produces the contrary electric current of two-way temperature coefficient variation tendency, and two-way electric current is superimposed on same resistance, suitably regulates the ratio of two-way electric current, and being formed can the bandgap voltage reference of flexible.
CMOS reference voltage source of the present invention, has obvious advantage and positive effect, and due to reference voltage source circuit conventional at present in a lot.
(1) do not contain triode in circuit of the present invention, only comprise NMOS tube, PMOS, resistance three kinds of devices, therefore, have the simple advantage of technique, it is convenient, effective, compatible good that CMOS technology line realizes;
(2) the present invention adopts new sub-threshold region CMOS reference circuit structure, add the structural parameters of the metal-oxide-semiconductor being operated in sub-threshold region and the coupling of duty, compared to traditional reference circuit containing sub-threshold region device, reduce the impact that process deviation normally realizes circuit function, improve the stability of sub-threshold region devices function in circuit, ensure that the reliability of CMOS reference voltage source;
(3) the present invention adopts mode electric currents different for two-way temperature characterisitic being superimposed on same resistance, using the reference voltage that the voltage at resistance two ends goes to zero as temperature coefficient, therefore reference voltage value can flexible, to be applicable to different circuit requirements.
Accompanying drawing explanation
By reading the detailed description done non-limiting example done with reference to the following drawings, other features, objects and advantages of the present invention will become more obvious, and in accompanying drawing, same or analogous Reference numeral represents same or analogous parts.
Figure 1 shows that prior art 1, for adopting BiCMOS technique band gap reference voltage source circuit;
Figure 2 shows that prior art 2, for adopting BiCMOS technique band gap reference voltage source circuit;
Figure 3 shows that prior art 3, is a kind of sub-threshold region CMOS reference voltage source circuit;
Figure 4 shows that CMOS reference voltage source circuit modular structure schematic diagram of the present invention;
Figure 5 shows that CMOS reference voltage source circuit figure of the present invention.
Embodiment
Below by way of specific embodiments of the invention also by reference to the accompanying drawings, object of the present invention, circuit structure and advantage are further described.
Fig. 4 is CMOS reference voltage source circuit modular structure schematic diagram, and this circuit comprises start-up circuit 101, the first bias current generating circuit 102, first bias current generating circuit 103, reference voltage generating circuit 104, start-up circuit 101, first bias current generating circuit 102, first bias current generating circuit 103, the direct current input end of reference voltage generating circuit 104 connects direct supply VDD respectively, the input end of the first bias current generating circuit 102 connects the output terminal of start-up circuit 101, the output terminal of the first bias current generating circuit 102 is connected to the first input end of reference voltage generating circuit 104 and the input end of the first bias current generating circuit 103, the output terminal of the first bias current generating circuit 103 is connected to the second input end of reference voltage generating circuit 104, the reference voltage output end output reference voltage of reference voltage generating circuit 104.
Fig. 5 is CMOS reference voltage source circuit figure.Start-up circuit 101 is by PMOS M
s1, M
s2with NMOS tube M
s3composition, PMOS M
s1source electrode, PMOS M
s2source electrode and NMOS tube M
s3grid as the direct current input end of start-up circuit 101, PMOS M
s1drain electrode respectively with PMOS M
s2grid and NMOS tube M
s3drain electrode be connected, NMOS tube M
s3source electrode connect common, PMOS M
s1grid and PMOS M
s2drain electrode respectively as first, second output terminal of start-up circuit 101;
First bias current generating circuit 102 is by 4 PMOS M
3, M
4, M
5and M
6, 2 NMOS tube M
7and M
8and 2 resistance R
1and R
2composition, PMOS M
1and M
3source electrode as direct current input end, the first output terminal of start-up circuit 101 and PMOS M
1and M
3grid, and M
3drain electrode connect altogether, and as the first output terminal of the first bias current generating circuit 102 and the first input end of the first bias current generating circuit 103, and the first input end of reference voltage generating circuit 104 is connected, PMOS M
1drain electrode and PMOS M
2source electrode be connected, PMOS M
3drain electrode and PMOS M
4source electrode be connected, PMOS M
2grid and PMOS M
4grid and drain electrode connect altogether, and as the second output terminal of the first bias current generating circuit 102 and the second input end of the first bias current generating circuit 103, and the second input end of reference voltage generating circuit 104 be connected, start-up circuit 101 second output terminal respectively with PMOS M
2drain electrode, NMOS tube M
5drain and gate, and NMOS tube M
6grid connects altogether, PMOS M
4drain electrode and NMOS tube M
6drain electrode be connected, NMOS tube M
5source electrode and resistance R
1be connected, resistance R
1another termination common, NMOS tube M
6source electrode and resistance R
2be connected, resistance R
2another termination common.
First bias current generating circuit 103 is by 6 PMOS M
7, M
8, M
11, M
12, M
13and M
14, 2 NMOS tube M
9and M
10and a resistance R
3composition, PMOS M
7, PMOS
13with PMOS M
11source electrode as direct current input end, the first output terminal of the first bias current generating circuit 102 and PMOS M
7grid be connected, PMOS M
7drain electrode and PMOS M
8source electrode be connected, PMOS M
8grid be connected with the second output terminal of the first bias current generating circuit 102, PMOS M
8drain electrode and NMOS tube M
9drain electrode and NMOS tube M
10grid connect altogether, NMOS tube M
9source electrode connect common, PMOS M
13grid and drain electrode, and PMOS M
11grid connect altogether, and to be connected with the first input end of reference voltage generating circuit 104 as the first output terminal of the first bias current generating circuit 103, PMOS M
13drain electrode and PMOS M
14source electrode be connected, PMOS M
11drain electrode and PMOS M
12source electrode be connected, PMOS M
14grid and drain electrode, and PMOS M
12grid connect altogether, and to be connected with the second input end of reference voltage generating circuit 104 as the second output terminal of the first bias current generating circuit 103, PMOS M
14drain electrode and NMOS tube M
10drain electrode be connected, NMOS tube M
10source electrode connect common, PMOS M
12drain electrode and NMOS tube M
9grid and resistance R
3connect altogether, resistance R
3another termination common.
Reference voltage generating circuit 104 is by 4 PMOS M
15, M
16, M
17and M
18, a resistance R
4composition, PMOS M
15source electrode and PMOS M
17source electrode as direct current input end, PMOS M
15grid be connected with the first output terminal of the first bias current generating circuit 102, PMOS M
17grid be connected with the first output terminal of the first bias current generating circuit 103, PMOS M
15drain electrode and PMOS M
16source electrode be connected, PMOS M
17drain electrode and PMOS M
18source electrode be connected, PMOS M
16grid be connected with the second output terminal of the first bias current generating circuit 102, PMOS M
18grid be connected with the second output terminal of the first bias current generating circuit 103, PMOS M
16drain electrode and PMOS M
18drain electrode be connected to resistance R altogether
4, and as reference voltage output end, resistance R
4another termination common.
The course of work of circuit of the present invention: as connection direct current power source voltage V
dDtime, NMOS tube M
s3open, by PMOS M
s2grid voltage be pulled down to close to common voltage, M
s2pipe is opened, and for start-up circuit 101 second output terminal provides enough voltage, is PMOS M
5and M
6gate charges, ensure metal-oxide-semiconductor open, circuit working depart from off state.
PMOS M in first bias current generating circuit 102
1, M
2, M
3and M
4for common-source common-gate current mirror, wherein M
1, M
3and M
2, M
4breadth length ratio equal, make I
1=I
2, resistance R simultaneously
1=R
2, make NMOS tube M
5and M
6gate source voltage equal, M
5and M
6be operated in sub-threshold region, and duty is similar to identical, namely
Wherein NMOS tube M
5source voltage V
gS5=I
1r
1, (10) are obtained with Taylor function approximate expansion
Thus obtain I
1expression formula
Known wherein relevant with temperature variable is V
tand V
g5.PMOS M
1, M
2, M
3and M
4be operated in saturation region, its source gate voltage has positive temperature coefficient (PTC) character, V when temperature raises
sGincrease, saturation depth increases, V
sD1, V
sD2reduce, therefore V
g5increase; Know V again
tfor positive temperature coefficient (PTC) parameter, therefore I
1raise with temperature and increase.Through the emulation of 0.18um 3.3v SOI CMOS technology,--in 50-150 degree temperature ranges, electric current I
1temperature curve be approximately first order linear curve.
In the first bias current generating circuit 103, PMOS M
7and M
8form current mirror and copy I
2, be NMOS tube M
9bias current is provided; Resistance R simultaneously
3two sections meet M respectively
9grid and source electrode, therefore flow through R
3electric current be
M
9be operated in sub-threshold region, V
gS9there is negative temperature coefficient, therefore I
4for negative temperature parameter current.Wherein M
9, M
10, M
11, M
12, M
13, M
14and R
3for negative feedback connects, feedback regulation M
9gate source voltage keep steady state (SS), do not change with the shake of voltage or electric current.
In reference voltage generating circuit, Positive and Negative Coefficient Temperature electric current superposes; PMOS M
15and M
16copy positive temperature coefficient (PTC) electric current I
1, PMOS M
17and M
18copy negative temperature parameter current I
4, two-way replica current I
6and I
7jointly flow through resistance R
4, obtain reference voltage V
rEF, namely
V
REF=(I
6+I
7)R
4=(AI
1+BI
4)R
4(14)
Can find out, by suitable adjustment factor A, B, the i.e. ratio of Positive and Negative Coefficient Temperature electric current, the reference voltage of zero-temperature coefficient can be produced.Meanwhile, by regulating R
4resistance, can the value of flexible reference voltage, be applicable to different circuit requirements.
In this circuit design, two-way current generating circuit is negative feedback structure, stability under working conditions is good, and the duty being in the metal-oxide-semiconductor of sub-threshold region is consistent, the impact of process deviation on it can be reduced, in addition, this circuit can be compatible with CMOS technology completely, and the reference voltage that circuit exports can according to different demand, by regulating R
4resistance carry out flexible.